General Description
The MAX8667/MAX8668 dual step-down converters
with dual low-dropout (LDO) linear regulators are
intended to power low-voltage microprocessors or
DSPs in portable devices. They feature high efficiency
with small external component size. The step-down
converters are adjustable from 0.6V to 3.3V (MAX8668)
or factory preset (MAX8667) with guaranteed output
current of 600mA for OUT1 and 1200mA for OUT2. The
1.5MHz hysteretic-PWM control scheme allows for tiny
external components and reduces no-load operating
current to 100µA with all outputs enabled. Dual low-qui-
escent-current, low-noise LDOs operate down to 1.7V
supply voltage. The MAX8667/MAX8668 have individ-
ual enables for each output, maximizing flexibility.
The MAX8667/MAX8668 are available in the space-
saving, 3mm x 3mm, 16-pin thin QFN package.
Applications
Cell Phones/Smartphones
PDA and Palmtop Computers
Portable MP3 and DVD Players
Digital Cameras, Camcorders
PCMCIA Cards
Handheld Instruments
Features
oTiny, Thin QFN 3mm x 3mm Package
oIndividual Enables
oStep-Down Converters
600mA Guaranteed Output Current on OUT1
1200mA Guaranteed Output Current on OUT2
Tiny Size 2.2µH Chip Inductor (0805)
Output Voltage from 0.6V to 3.3V (MAX8668)
Ultra-Fast Line and Load Transients
Low 25µA Supply Current Each
oLDOs
300mA Guaranteed
Low 1.7V Minimum Supply Voltage
Low Output Noise
MAX8667/MAX8668
1.5MHz Dual Step-Down DC-DC Converters
with Dual LDOs and Individual Enables
________________________________________________________________
Maxim Integrated Products
1
15
16
14
13
5
6
7
IN34
OUT4
8
EN3
LX2
PGND2
LX1
13
OUT1 (FB1)
4
12 10 9
EN1
EN2
OUT2 (FB2)
REF
GND
EN4
MAX8667
MAX8668
OUT3 IN12
2
11
PGND1
THIN QFN
(3mm x 3mm)
TOP VIEW
( ) ARE FOR THE MAX8668
Pin Configuration
IN34
LX2
LX1
OUT2
OUT1
2.6V TO 5.5V
OUT3
OUT4
REF
GND
IN12
300mA
300mA
EN1
EN2
EN3
EN4
600mA 1.2A
PGND1 PGND2
10µF 4.7µF
4.7µF4.7µF
0.01µF
2.2µH2.2µH
2.2µF2.2µF
MAX8667
Typical Operating Circuit
19-0784; Rev 1; 7/07
For pricing, delivery, and ordering information, please contact Maxim/Dallas Direct! at
1-888-629-4642, or visit Maxim’s website at www.maxim-ic.com.
EVALUATION KIT
AVAILABLE
Ordering Information continued at the end of data sheet.
Selector Guide appears at the end of data sheet.
Ordering Information
Note: All MAX8667/MAX8668 parts are in a 16-pin, thin QFN,
3mm x 3mm package and operate in the -40°C to +85°C
extended temperature range.
+
Denotes a lead-free package.
PART PKG CODE TOP MARK
MAX8667ETEAA+
T1633-4 AEQ
MAX8667ETEAB+
T1633-4 AFI
MAX8667ETEAC+
T1633-4 AFM
MAX8667ETECQ+
T1633-4 AFN
MAX8667/MAX8668
1.5MHz Dual Step-Down DC-DC Converters
with Dual LDOs and Individual Enables
2 _______________________________________________________________________________________
ABSOLUTE MAXIMUM RATINGS
ELECTRICAL CHARACTERISTICS
(VIN34 = VIN12 = 3.6V, TA = -40°C to +85°C, unless otherwise noted. Typical values are at TA= +25°C.) (Note 1)
Stresses beyond those listed under “Absolute Maximum Ratings” may cause permanent damage to the device. These are stress ratings only, and functional
operation of the device at these or any other conditions beyond those indicated in the operational sections of the specifications is not implied. Exposure to
absolute maximum rating conditions for extended periods may affect device reliability.
IN12, IN34, FB1, FB2, EN1, EN2, EN3, EN4, OUT1,
OUT2, REF to GND............................................-0.3V to +6.0V
OUT3,
OUT4 to GND.....-0.3V to the lesser of + 6V or (VIN34 + 0.3V)
PGND1, PGND2 to GND .......................................-0.3V to +0.3V
LX1, LX2 Current ..........................................................1.5A RMS
LX1, LX2 to GND (Note 1) .......................-0.3V to (VIN12 + 0.3V)
Continuous Power Dissipation (TA= +70°C)
16-Pin, 3mm x 3mm Thin QFN
(derate 20.8mW/°C above +70°C).............................1667mW
Operating Temperature Range ...........................-40°C to +85°C
Junction Temperature..................................................... +150°C
Storage Temperature Range .............................-65°C to +150°C
Lead Temperature (soldering, 10s) .................................+300°C
PARAMETER CONDITIONS MIN TYP MAX UNITS
IN34 Supply Range VIN12 VIN34 1.7 5.5 V
IN12 Supply Range MAX8668, VIN12 VIN34 2.6 5.5 V
IN12 Suppy Range MAX8667, VIN12 VIN34 2.8 5.5 V
TA = +25°C 1 µA
Shutdown Supply Current,
IIN12 + IIN34 VIN12 = VIN34 = 4.2V VEN_ = 0V TA = +85°C 0.05 µA
No Load Supply Current,
IIN12 + IIN34 MAX8667ETEJS+, all regulators enabled 100 150 µA
UNDERVOLTAGE LOCKOUT
VIN12 rising 2.4 2.5 2.6 V
IN12 UVLO VIN12 hysteresis 0.1 V
VIN34 rising 1.5 1.6 1.7 V
IN34 UVLO VIN34 hysteresis 0.1 V
THERMAL SHUTDOWN
Threshold TA rising +160 °C
Hysteresis 15 °C
REFERENCE
Reference Bypass Output
Voltage 0.591 0.600 0.609 V
REF Supply Rejection 2.6V (VIN12 = VIN34) 5.5V 0.15 mV/V
LOGIC AND CONTROL INPUTS
EN_ Input Low Level 1.7V VIN34 5.5V
2.6V VIN12 5.5V 0.4 V
EN_ Input High Level 1.7V VIN34 5.5V
2.6V VIN12 5.5V 1.44 V
TA = +25°C -1 +1
EN_ Input Leakage Current VIN12 = VIN34 = 5.5V TA = +85°C 0.001 µA
STEP-DOWN CONVERTERS
Minimum Adjustable Output
Voltage MAX8668 0.6 V
Note 1: LX_ has internal clamp diodes to GND and IN12. Applications that forward bias these diodes should take care not to exceed
the IC’s package-dissipation limits.
MAX8667/MAX8668
1.5MHz Dual Step-Down DC-DC Converters
with Dual LDOs and Individual Enables
_______________________________________________________________________________________ 3
Note 1: All devices are 100% production tested at TA= +25°C. Limits over the operating temperature range are guaranteed by design.
PARAMETER CONDITIONS MIN TYP MAX UNITS
Maximum Adjustable Output
Voltage MAX8668 3.3 V
TA = +25°C 0.588 0.600 0.612
FB1, FB2 Regulation Voltage MAX8668, no load,
VFB_ falling TA = -40°C to +85°C 0.582 0.600 0.618 V
TA = +25°C 1.274 1.300 1.326
OUT1, OUT2 Regulation Voltage MAX8667ETEJS+, no load, VOUT_
falling TA = -40°C to +85°C 1.261 1.300 1.339 V
FB1, FB2 Line Regulation MAX8668, VIN12 = 2.6V to 5.5V 0.01 %/V
OUT1, OUT2 Line Regulation MAX8667, VIN12 = 2.8V to 5.5V 0.05 %/V
MAX8668, shutdown mode 0.1
FB1, FB2 Bias Current MAX8668, VFB1 = 0.5V 0.01 µA
pMOSFET switch (ILIMP1) 700 900 1100
OUT1 Current Limit nMOSFET rectifier (valley current) 500 750 1000 mA
pMOSFET switch (ILIMP2) 1333 1667 2000
OUT2 Current Limit nMOSFET rectifier (valley current) 1200 1500 1800 mA
pMOSFET switch, ILX1 = -400mA 0.3 0.6
OUT1 On-Resistance nMOSFET rectifier, ILX1 = 400mA 0.3 0.6
pMOSFET switch, ILX2 = -400mA 0.12 0.27
OUT2 On-Resistance nMOSFET rectifier, ILX2 = 400mA 0.12 0.27
Rectifier-Off Current Threshold
(ILXOFF)60 120 mA
TA = +25°C -1 +1
LX Leakage Current LX_ = 5.5V TA = +85°C 0.1 µA
Minimum On-Time 100 ns
Minimum Off-Time 50 ns
LDO REGULATORS
Supply Current Each LDO 20 µA
1mA load, TA = +25°C -1.5 +1.5
Output-Voltage Accuracy 1mA to 300mA load -3.0 +3.0 %
Line Regulation VIN34 = 3.6V to 5.5V, 1mA load 0.003 %/V
Dropout Voltage VIN34 = 1.8V, 300mA load 130 250 mV
Current Limit VOUT3, VOUT4 90% of nominal value 375 420 465 mA
Soft-Start Ramp Time To 90% of final value 0.1 ms
Output Noise 100Hz to 100kHz, 30mA load, VOUT3 and VOUT4 = 2.8V 75 µVRMS
Power-Supply Rejection Ratio f < 1kHz, 30mA load 57 dB
Shutdown Output Resistance 1k
TIMING (See Figure 2)
OUT1, OUT2 25
Power-On Time (tPWRON)OUT3, OUT4 45 µs
OUT1, OUT2 15
Enable Time (tEN)OUT3, OUT4 35 µs
ELECTRICAL CHARACTERISTICS (continued)
(VIN34 = VIN12 = 3.6V, TA = -40°C to +85°C, unless otherwise noted. Typical values are at TA= +25°C.) (Note 1)
MAX8667/MAX8668
1.5MHz Dual Step-Down DC-DC Converters
with Dual LDOs and Individual Enables
4 _______________________________________________________________________________________
Typical Operating Characteristics
(VIN12 = VIN34 = 3.6V, circuit of Figure 4, VOUT1 = 1.2V, VOUT2 = 1.8V, VOUT3 = 2.8V, VOUT4 = 2.8V, TA = +25°C, unless otherwise noted.)
OUT1 EFFICIENCY vs. LOAD CURRENT
(VOUT1 = 1.2V)
MAX8667/88 toc01
LOAD CURRENT (mA)
EFFICIENCY (%)
101
10
20
30
40
50
60
70
80
90
0
0.1 1000100
ONLY OUT1 ENABLED
OUT2 EFFICIENCY vs. LOAD CURRENT
(VOUT2 = 1.8V)
MAX8667/88 toc02
LOAD CURRENT (mA)
EFFICIENCY (%)
1000100101
10
20
30
40
50
60
70
80
90
0
0.1 10000
ONLY OUT2 ENABLED
0.80
0.90
0.85
1.05
1.00
0.95
1.20
1.15
1.10
1.25
0 200100 300 400 500 600
OUT1 LOAD REGULATION
MAX8667/88 toc03
LOAD CURRENT (mA)
OUTPUT VOLTAGE (V)
1.20
1.40
1.30
1.60
1.50
1.80
1.70
1.90
0 400 600200 800 1000 1200
OUT2 LOAD REGULATION
MAX8667/88 toc04
LOAD CURRENT (mA)
OUTPUT VOLTAGE (V)
1.00
1.05
1.10
1.15
1.20
1.25
1.30
1.35
1.40
2.5 3.53.0 4.0 4.5 5.0 5.5
OUT1 OUTPUT VOLTAGE
vs. INPUT VOLTAGE (600mA LOAD)
MAX8667/88 toc05
INPUT VOLTAGE (V)
OUTPUT VOLTAGE (V)
1.60
1.65
1.70
1.75
1.80
1.85
1.90
1.95
2.00
2.5 3.53.0 4.0 4.5 5.0 5.5
OUT2 OUTPUT VOLTAGE
vs. INPUT VOLTAGE (1200mA LOAD)
MAX8667/88 toc06
INPUT VOLTAGE (V)
OUTPUT VOLTAGE (V)
0
1000
500
2000
1500
3000
2500
3500
0 600 900300 1200 1500 1800
SWITCHING FREQUENCY
vs. LOAD CURRENT
MAX8667/88 toc07
LOAD CURRENT (mA)
SWITCHING FREQUENCY (kHz)
OUT2
OUT1
0
20
40
60
80
100
120
1.5 2.52.0 3.0 3.5 4.0 4.5 5.0 5.5
NO-LOAD SUPPLY CURRENT vs. SUPPLY
VOLTAGE ALL REGULATOR ENABLED
MAX8667/88 toc08
SUPPLY VOLTAGE (V)
SUPPLY CURRENT (µA)
SUPPLY VOLTAGE
RISING
SUPPLY VOLTAGE
FALLING
0
20
40
60
80
100
120
1.5 2.52.0 3.0 3.5 4.0 4.5 5.0 5.5
NO-LOAD SUPPLY CURRENT
vs. SUPPLY VOLTAGE OUT1 AND OUT2 ONLY
MAX8667/88 toc09
SUPPLY VOLTAGE (V)
SUPPLY CURRENT (µA)
SUPPLY VOLTAGE
RISING
SUPPLY VOLTAGE
FALLING
MAX8667/MAX8668
1.5MHz Dual Step-Down DC-DC Converters
with Dual LDOs and Individual Enables
_______________________________________________________________________________________
5
0
40
20
80
60
100
120
012345
NO-LOAD SUPPLY CURRENT vs. SUPPLY
VOLTAGE OUT3 AND OUT4 ONLY
MAX8667/88 toc10
SUPPLY VOLTAGE (V)
IIN34 (µA)
VIN12 = 5.5V
VIN34 VOLTAGE
RISING
VIN34 VOLTAGE
FALLING
2.50
2.65
2.60
2.55
2.70
2.75
2.80
2.85
2.90
2.95
3.00
2.5 3.53.0 4.0 4.5 5.0 5.5
OUT3 OUTPUT VOLTAGE
vs. INPUT VOLTAGE (300mA LOAD)
MAX8667/88 toc11
INPUT VOLTAGE (V)
OUTPUT VOLTAGE (V)
0
10
20
30
40
50
60
70
80
0 100 200 300
OUT3 DROPOUT VOLTAGE
vs. LOAD CURRENT
MAX8667/88 toc12
LOAD CURRENT (mA)
DROPOUT VOLTAGE (mV)
0
300
200
100
400
500
600
700
800
900
1000
2.5 3.53.0 4.0 4.5 5.0 5.5
SUPPLY CURRENT vs. SUPPLY VOLTAGE
MAX8667/88 toc13
SUPPLY VOLTAGE (V)
SUPPLY CURRENT (mA)
IN12 = IN34
2.4 LOAD ON OUT1
3.6 LOAD ON OUT2
NO LOAD ON OUT3
NO LOAD ON OUT4
40µs/div
ENABLE WAVEFORMS
EN1/EN2/
EN3/EN4
VOUT1
VOUT2
5V/div
2V/div
2V/div
2V/div
2V/div
2A/div
2A/div
2A/div
MAX8667/88 toc14
VOUT4
IL1
VOUT3
IL2
IIN12 + IIN34
40µs/div
SHUTDOWN WAVEFORMS
EN1/EN2/
EN3/EN4
VOUT1
VOUT2
5V/div
1V/div
1V/div
1V/div
1V/div
MAX8667/88 toc15
VOUT4
VOUT3
Typical Operating Characteristics (continued)
(VIN12 = VIN34 = 3.6V, circuit of Figure 4, VOUT1 = 1.2V, VOUT2 = 1.8V, VOUT3 = 2.8V, VOUT4 = 2.8V, TA = +25°C, unless otherwise noted.)
10µs/div
OUT1 LOAD TRANSIENT
VOUT1
IOUT1
100mV/div
(AC-COUPLED)
200mA/div
200mA/div
MAX8667/88 toc16
IL1
300mA
10mA
10mA
MAX8667/MAX8668
1.5MHz Dual Step-Down DC-DC Converters
with Dual LDOs and Individual Enables
6 _______________________________________________________________________________________
10µs/div
OUT2 LOAD TRANSIENT
VOUT2
IOUT2
200mV/div
(AC-COUPLED)
500mA/div
500mA/div
MAX8667/88 toc17
IL2
600mA
10mA10mA
10µs/div
OUT3 LOAD TRANSIENT
VOUT3
IOUT3
50mV/div
(AC-COUPLED)
200mA/div
MAX8667/88 toc18
300mA
0mA 0mA
10µs/div
OUT4 LOAD TRANSIENT
VOUT4
IOUT4
50mV/div
(AC-COUPLED)
200mA/div
MAX8667/88 toc19
300mA
0mA 0mA
10µs/div
OUT1 LIGHT-LOAD SWITCHING
WAVEFORMS
VOUT1
VLX1
IL1
20mV/div
MAX8667/88 toc20
2V/div
100mA/div
500µA LOAD
40µs/div
OUT2 LIGHT-LOAD SWITCHING
WAVEFORMS
VOUT2
VLX2
IL2
20mV/div
MAX8667/88 toc21
2V/div
500mA/div
500µA LOAD
400ns/div
OUT1 HEAVY-LOAD SWITCHING
WAVEFORMS
VOUT1
VLX1
IL1
20mV/div
MAX8667/88 toc22
2V/div
500mA/div
500mA LOAD
Typical Operating Characteristics (continued)
(VIN12 = VIN34 = 3.6V, circuit of Figure 4, VOUT1 = 1.2V, VOUT2 = 1.8V, VOUT3 = 2.8V, VOUT4 = 2.8V, TA = +25°C, unless otherwise noted.)
MAX8667/MAX8668
Typical Operating Characteristics (continued)
(VIN12 = VIN34 = 3.6V, circuit of Figure 4, VOUT1 = 1.2V, VOUT2 = 1.8V, VOUT3 = 2.8V, VOUT4 = 2.8V, TA = +25°C, unless otherwise noted.)
1.5MHz Dual Step-Down DC-DC Converters
with Dual LDOs and Individual Enables
_______________________________________________________________________________________
7
1ms/div
OUT3 NOISE
MAX8667/88 toc25
100µV/div
VOUT3 = 2.80V
ILOAD = 100
1ms/div
OUT4 NOISE
MAX8667/88 toc26
100µV/div
VOUT4 = 3.30V
ILOAD = 100
400ns/div
OUT2 HEAVY-LOAD SWITCHING
WAVEFORMS
VOUT2
VLX2
IL2
20mV/div
MAX8667/88 toc23
2V/div
500mA/div
500mA LOAD
0
20
10
40
30
60
50
70
0.01 10.1 10 100 1000
POWER-SUPPLY REJECTION RATIO
vs. FREQUENCY
MAX8667/88 toc24
FREQUENCY (kHz)
PSRR (dB)
VOUT3 = 2.80V
ILOAD = 100
COUT3 = 4.7µF
MAX8667/MAX8668
1.5MHz Dual Step-Down DC-DC Converters
with Dual LDOs and Individual Enables
8 _______________________________________________________________________________________
Pin Description
NAME
PIN MAX8667 MAX8668 FUNCTION
1 EN3 EN3 Enable Input for Regulator 3. Drive EN3 high or connect to IN34 to turn on regulator 3. Drive low
to turn off regulator 3 and reduce input quiescent current.
2 OUT3 OUT3 Output of Regulator 3. Bypass OUT3 with a 4.7µF ceramic capacitor to GND. OUT3 is
discharged to GND through an internal 1k in shutdown.
3 IN34 IN34
Input Voltage for LDO Regulators 3 and 4. Supply voltage range is from 1.7V to 5.5V. This
supply voltage must not exceed VIN12. Connect a 4.7µF or larger ceramic capacitor from IN34
to ground.
4 OUT4 OUT4 Output of Regulator 4. Bypass OUT4 with a 4.7µF ceramic capacitor to GND. OUT4 is
discharged to GND through an internal 1k in shutdown.
5 EN4 EN4 Enable Input for Regulator 4. Drive EN4 high or connect to IN34 to turn on regulator 4. Drive low
to turn off regulator 4 and reduce input quiescent current.
6 GND GND Ground
7 REF REF Reference Output. Bypass REF with a 0.01µF ceramic capacitor to GND.
8 OUT2 Feedback Input for Regulator 2. Connect OUT2 directly to the output of step-down regulator 2.
FB2
Feedback Input for Regulator 2. Connect FB2 to the center of a resistor feedback divider
between the output of regulator 2 and ground to set the output voltage. See the Setting the
Output Voltages and Voltage Positioning section.
9 PGND2 PGND2 Power Ground for Step-Down Regulator 2
10 LX2 LX2 Inductor Connection for Regulator 2
11 IN12 IN12
Input Voltage for Step-Down Regulators 1 and 2. Supply voltage range is from 2.6V to 5.5V. This
supply voltage must not be less than VIN34. Connect a 10µF or larger ceramic capacitor from
IN12 to ground.
12 LX1 LX1 Inductor Connection for Regulator 1
13 PGND1 PGND1 Power Ground for Step-Down Regulator 1
14 OUT1 Feed b ack Inp ut for Reg ul ator 1. C onnect OU T1 d i r ectl y to the outp ut of step - d ow n r eg ul ator 1.
FB1
Feedback Input for Regulator 1. Connect FB1 to the center of a resistor feedback divider
between the output of regulator 1 and ground to set the output voltage. See the Setting the
Output Voltages and Voltage Positioning section.
15 EN1 EN1 E nab l e Inp ut for Reg ul ator 1. D r i ve E N 1 hi g h or connect to IN 12 to tur n on step - d ow n r eg ul ator 1.
D r i ve l ow to tur n off the r eg ul ator and r ed uce i np ut q ui escent cur r ent.
16 EN2 EN2 E nab l e Inp ut for Reg ul ator 2. D r i ve E N 2 hi g h or connect to IN 12 to tur n on step - d ow n r eg ul ator 2.
D r i ve l ow to tur n off the r eg ul ator and r ed uce i np ut q ui escent cur r ent.
EP EP Exposed Paddle. Connect to GND, PGND1, PGND2, and circuit ground.
MAX8667/MAX8668
1.5MHz Dual Step-Down DC-DC Converters
with Dual LDOs and Individual Enables
_______________________________________________________________________________________ 9
IN
REF
EN
UVLO
REF AND BIAS
GND
IN
EN
OUT
GND
IN
EN
GND
IN
EN
OUT
GND
IN34
1.7V TO 5.5V IN12
2.8V TO 5.5V
(2.6V TO 5.5V)
GND
LX1
LX2
REF
OUT3
OUT4
PWRON LOGIC
AND ENABLES
EN3
EN4
EN1
EN2
PGND2
OUT1
(FB1)
OUT2
(FB2)
FB
FB
PGND1
EN
OUT1
OUT2
OUT3
OUT4
LDO
LDO
STEP-DOWN
STEP-DOWN
() ARE FOR THE MAX8668
Figure 1. Functional Diagram
MAX8667/MAX8668
1.5MHz Dual Step-Down DC-DC Converters
with Dual LDOs and Individual Enables
10 ______________________________________________________________________________________
Detailed Description
The MAX8667/MAX8668 dual step-down converters
with dual low-dropout (LDO) linear regulators are
intended to power low-voltage microprocessors or
DSPs in portable devices. They feature high efficiency
with small external component size. The step-down out-
puts are adjustable from 0.6V to 3.3V (MAX8668) or
factory preset (MAX8667) with guaranteed output cur-
rent of 600mA for OUT1 and 1200mA for OUT2. The
1.5MHz hysteretic-PWM control scheme allows for tiny
external components and reduces no-load operating
current to 100µA (typ) with all regulators enabled. Dual,
low-quiescent-current, low-noise LDOs operate down to
1.7V supply voltage. The MAX8667/MAX8668 have
individual enable inputs for each output to facilitate any
supply sequencing.
Step-Down DC-DC Regulators
(OUT1, OUT2)
Step-Down Regulator Architecture
The MAX8667/MAX8668 step-down regulators are opti-
mized for high-efficiency voltage conversion over a
wide load range, while maintaining excellent transient
response, minimizing external component size, and
minimizing output voltage ripple. The DC-DC convert-
ers (OUT1, OUT2) also feature an optimized on-resis-
tance internal MOSFET switch and synchronous
rectifier to maximize efficiency. The MAX8667/
MAX8668 utilize a proprietary hysteretic-PWM control
scheme that switches with nearly fixed frequency at up
to 1.5MHz allowing for ultra-small external components.
The step-down converter output current is guaranteed
up to 600mA for OUT1 and 1200mA for OUT2.
When the step-down converter output voltage falls below
the regulation threshold, the error comparator begins a
switching cycle by turning the high-side p-channel
MOSFET switch on. This switch remains on until the mini-
mum on-time (tON) expires and the output voltage is in
regulation or the current-limit threshold (ILIMP_) is
exceeded. Once off, the high-side switch remains off
until the minimum off-time (tOFF) expires and the output
voltage again falls below the regulation threshold.
During this off period, the low-side synchronous rectifi-
er turns on and remains on until either the high-side
switch turns on or the inductor current reduces to the
rectifier-off current threshold (ILXOFF = 60mA typ). The
internal synchronous rectifier eliminates the need for an
external Schottky diode.
Input Supply and Undervoltage Lockout
The input voltage range of step-down regulators OUT1
and OUT2 is 2.6V to 5.5V. This supply voltage must be
greater than or equal to the LDO supply voltage (VIN34).
A UVLO circuit prevents step-down regulators OUT1
and OUT2 from switching when the supply voltage is
too low to guarantee proper operation. When VIN12 falls
below 2.4V (typ), OUT1 and OUT2 are shut down.
OUT1 and OUT2 turn on and begin soft-start when
VIN12 rises above 2.5V (typ).
Soft-Start
When initially powered up, or enabled with EN_, the
step-down regulators soft-start by gradually ramping
up the output voltage. This reduces inrush current dur-
ing startup. See the startup waveforms in the
Typical
Operating Characteristics
section.
Current Limit
The MAX8667/MAX8668 limit the peak inductor current
of the p-channel MOSFET (ILIMP_). A valley current limit
is used to protect the step-down regulators during
severe overload and output short-circuit conditions.
When the peak current limit is reached, the internal
p-channel MOSFET turns off and remains off until the
output drops below regulation, the inductor current falls
below the valley current-limit threshold, and the mini-
mum off-time has expired.
Voltage Positioning
The OUT1 and OUT2 output voltages and voltage posi-
tioning of the MAX8668 are set by a resistor network
connected to FB_. With this configuration, a portion of
the feedback signal is sensed on the switched side of
the inductor, and the output voltage droops slightly as
the load current is increased due to the DC resistance
of the inductor. This output voltage droop is known as
voltage positioning. Voltage positioning allows the load
regulation to be set to match the voltage droop during
a load transient, reducing the peak-to-peak output volt-
age deviation during a load transient, and reducing the
output capacitance requirements.
Dropout
As the input voltage approaches the output voltage, the
duty cycle of the p-channel MOSFET reaches 100%. In
this state, the p-channel MOSFET is turned on con-
stantly (not switching), and the dropout voltage is the
voltage drop due to the output current across the on-
resistance of the internal p-channel MOSFET (RPCH)
and the inductor’s DC resistance (RL):
LDO Linear Regulators (OUT3, OUT4)
The MAX8667/MAX8668 contain two low-dropout linear
regulators (LDOs), OUT3 and OUT4. The LDO output
voltages are factory preset, and each LDO supplies
VI R R
DO LOAD PCH L
=+
()
MAX8667/MAX8668
1.5MHz Dual Step-Down DC-DC Converters
with Dual LDOs and Individual Enables
______________________________________________________________________________________ 11
loads up to 300mA. The LDOs include an internal refer-
ence, error amplifier, p-channel pass transistor, and
internal voltage-dividers. Each error amplifier compares
the reference voltage to the output voltage (divided by
the internal voltage-divider) and amplifies the differ-
ence. If the divided feedback voltage is lower than the
reference voltage, the pass-transistor gate is pulled
lower, allowing more current to pass to the outputs and
increasing the output voltage. If the divided feedback
voltage is too high, the pass-transistor gate is pulled
up, allowing less current to pass to the output.
Input Supply and Undervoltage Lockout
The input voltage range of LDO regulators OUT3 and
OUT4 is 1.7V to 5.5V. This supply voltage must be less
than or equal to the voltage applied to IN12 (VIN34
VIN12).
An undervoltage lockout circuit turns off the LDO regula-
tors when the input supply voltage is too low to guarantee
proper operation. When VIN34 falls below 1.5V (typ),
OUT3 and OUT4 are shut down. OUT3 and OUT4 turn
on and begin soft-start when VIN34 rises above 1.6V (typ).
Soft-Start
When initially powered up, or enabled with EN_, the
LDOs soft-start by gradually ramping up the output
voltage. This reduces inrush current during startup. The
soft-start ramp time is typically 100µs from the start of
the soft-start ramp to the output reaching its nominal
regulation voltage.
Current Limit
The OUT3 and OUT4 output current is limited to 375mA
(min). If the output current exceeds the current limit, the
corresponding LDO output voltage drops.
Dropout
The maximum dropout voltage for the linear regulators
is 250mV at 300mA load. To avoid dropout, make sure
the IN34 supply voltage is at least 250mV higher than
the highest LDO output voltage.
Thermal-Overload Protection
Thermal-overload protection limits the total power dissi-
pation in the MAX8667/MAX8668. Thermal-protection
circuits monitor the die temperature. If the die tempera-
ture exceeds +160°C, the IC is shut down, allowing the
IC to cool. Once the IC has cooled by 15°C, the IC is
enabled again. This results in a pulsed output during
continuous thermal-overload conditions. The thermal-
overload protection protects the MAX8667/MAX8668 in
the event of fault conditions. For continuous operation,
do not exceed the absolute maximum junction temper-
ature of +150°C. See the
Thermal Considerations
sec-
tion for more information.
IN12
ENx
tPWRON
tPWRON IS THE PERIOD REQUIRED TO ENABLE FROM SHUTDOWN
ENy
tEN
tEN IS THE ENABLE TIME FOR SUBSEQUENT ENABLE
SIGNALS FOLLOWING THE FIRST ENABLE
ENx, ENy ARE ANY COMBINATION OF EN1–EN4.
OUTx
OUTy
Figure 2. Timing Diagram
MAX8667/MAX8668
1.5MHz Dual Step-Down DC-DC Converters
with Dual LDOs and Individual Enables
12 ______________________________________________________________________________________
IN34
1.7V TO 5.5V
LX1
LX2
OUT1
OUT2
INPUT
2.8V TO 5.5V
OUT3
OUT4
REF
GND
IN12
300mA
300mA
EN1
EN2
EN3
EN4
OUT2
1.2A
OUT1
600mA
PGND2 PGND1
C2
10µF
C3
4.7µF
C8
4.7µF
C9
4.7µF
C1
0.01µF
L2
2.2µH
L1
2.2µH
C7
2.2µF
C6
2.2µF
MAX8667
Figure 3. MAX8667 Typical Application Circuit
IN34
LX1
LX2
FB1
FB2
INPUT
2.6V TO 5.5V
OUT3
OUT4
REF
GND
IN12
OUT3, 300mA
OUT4, 300mA
EN1
EN2
EN3
EN4
OUT2
0.6V TO 3.3V, 1.2A
OUT1
0.6V TO 3.3V, 600mA
PGND1 PGND2
C2
10µF
C8
4.7µF
C9
4.7µF
C1
0.01µF
L2
2.2µH
L1
2.2µH
C7
2.2µF for VOUT2 1.8V
4.7µF for VOUT2 > 1.8V
C6
2.2µF
R1
R2
*C10, R5, AND R6 ARE OPTIONAL
R6*
C4
MAX8668
R3
R4
R5*
C5
C10*
Figure 4. MAX8668 Typical Application Circuit
MAX8667/MAX8668
1.5MHz Dual Step-Down DC-DC Converters
with Dual LDOs and Individual Enables
______________________________________________________________________________________ 13
Applications Information
Setting the Output Voltages
and Voltage Positioning
The LDO output voltages of the MAX8667/MAX8668,
and the step-down outputs of the MAX8667 are factory
preset. See the
Selector Guide
to find the part number
corresponding to the desired output voltages.
The OUT1 and OUT2 output voltages of the MAX8668
are set by a resistor network connected to FB_ as
shown in Figure 5. With this configuration, a portion of
the feedback signal is sensed on the switched side of
the inductor (LX), and the output voltage droops slightly
as the load current is increased due to the DC resis-
tance of the inductor (DCR). This allows the load regu-
lation to be set to match the voltage droop during a
load transient (voltage positioning), reducing the peak-
to-peak output-voltage deviation during a load tran-
sient, and reducing the output capacitance
requirements.
For the simplest method of setting the output voltage,
R6 is not installed. Choose the value of R2 (a good
starting value is 100k), and then calculate the value of
R1 as follows:
where VFB is the feedback regulation voltage (0.6V).
With the voltage set in this manner, the voltage posi-
tioning depends only on the DCR, and the maximum
output voltage droop is:
Setting the Output Voltages with
Reduced Voltage Positioning
To obtain less voltage positioning than described in the
previous section, use the following procedure for set-
ting the output voltages. The OUT1 and OUT2 output
voltages and voltage positioning of the MAX8668 are
set by a resistor network connected to FB_ as shown in
Figure 5.
To set the output voltage (VOUT), first select a value for
R2 (a good starting value is 100k). Then calculate the
value of REQ (the equivalent parallel resistance of R1
and R6) as follows:
where VFB is the feedback-regulation voltage (0.6V).
Calculate the factor m based on the desired load-regu-
lation improvement:
where IOUT(MAX) is the maximum output current, DCR is
the inductor series resistance, and VOUT(DESIRED) is the
maximum allowable droop in the output voltage at full
load. The calculated value for m must be between 1.1 and
2; m = 2 results in a 2x improvement in load regulation.
Now calculate the values of R1 and R6 as follows:
The value of R1 should always be lower than the value
of R6.
Power-Supply Sequencing
The MAX8667/MAX8668 have individual enable inputs
for each regulator to allow complete control over the
power sequencing. When all EN_ inputs are low, the IC
is in low-power shutdown mode, reducing the supply
current to less than 1µA. After one of the EN_ inputs
asserts high, the corresponding regulator begins soft-
start after a delay of tEN (see Figure 2). The first output
enabled from shutdown mode or initially powering up
the IC has a longer delay (tPWRON) as the IC exits the
low-power shutdown mode.
Inductor Selection
The MAX8667/MAX8668 step-down converters operate
with inductors between 2.2µH and 4.7µH. Low induc-
tance values are physically smaller, but require faster
switching, resulting in some efficiency loss. The induc-
tor’s DC current rating must be high enough to account
RR m
RR
EQ
EQ m
m
1
61
mI DCR
V
OUT MAX
OUT DESIRED
=×
()
()
RV
VR
EQ OUT
FB
=−
×12
V DCR I
OUT MAX OUT MAX() ()
RR V
V
OUT
FB
12 1
L1 DCR
LX_
FB_
OUT
ESR
C6
RLOAD
R1 R6
(OPTIONAL)
R2
C4
Figure 5. MAX8668 Feedback Network
MAX8667/MAX8668
1.5MHz Dual Step-Down DC-DC Converters
with Dual LDOs and Individual Enables
14 ______________________________________________________________________________________
for peak ripple current and load transients. The step-
down converter’s unique architecture has minimal cur-
rent overshoot during startup and load transients and in
most cases, an inductor capable of 1.3x the maximum
load current is acceptable.
For output voltages above 2V, when light-load efficiency
is important, the minimum recommended inductor is
2.2µH. For optimum voltage-positioning load transients,
choose an inductor with DC series resistance in the
50mto 150mrange. For higher efficiency at heavy
loads (above 200mA) and minimal load regulation,
keep the inductor resistance as small as possible. For
light-load applications (up to 200mA), higher resistance
is acceptable with very little impact on performance.
Capacitor Selection
Input Capacitors
The input capacitor for the step-down converters (C2 in
Figures 3 and 4) reduces the current peaks drawn from
the battery or input power source and reduces switch-
ing noise in the IC. The impedance of C2 at the switch-
ing frequency should be very low. Surface-mount
ceramic capacitors are a good choice due to their
small size and low ESR. Make sure the capacitor main-
tains its capacitance over temperature and DC bias.
Ceramic capacitors with X5R or X7R temperature char-
acteristics generally perform well. A 10µF ceramic
capacitor is recommended.
A 4.7µF ceramic capacitor is recommended for the
LDO input capacitor (C3 in Figure 3).
Step-Down Output Capacitors
The step-down output capacitors (C6 and C7 in Figures
3 and 4) are required to keep the output-voltage ripple
small and to ensure regulation loop stability. These
capacitors must have low impedance at the switching
frequency. Surface-mount ceramic capacitors are a
good choice due to their small size and low ESR. Make
sure the capacitor maintains its capacitance over tem-
perature and DC bias. Ceramic capacitors with X5R or
X7R temperature characteristics generally perform well.
The output capacitance can be very low. For most appli-
cations, a 2.2µF ceramic capacitor is sufficient. For C7 of
the MAX8668, a 2.2µF (VOUT2 1.8V) or a 4.7µF (VOUT2
> 1.8V) ceramic capacitor is recommended. For opti-
mum load-transient performance and very low output rip-
ple, the output capacitor value in µF should be equal to
or greater than the inductor value in µH.
Feed-Forward Capacitor
The feed-forward capacitors on the MAX8668 (C4 and
C5 in Figure 4) set the feedback loop response, control
the switching frequency, and are critical in obtaining
the best efficiency possible. Small X7R and C0G
ceramic capacitors are recommended.
For OUT1, calculate the value of C4 as follows:
C4 = 1.2 x 10-5(s/V) x (VOUT / R1)
For OUT2, calculate the value of C5 and C10 as fol-
lows:
Cff = 1.2 x 10-5(s/V) x (VOUT / R3)
Cff = C5 + (C10 / 2)
(C10 / C5) + 1 = (VOUT / VFB), where VFB is 0.6V.
Rearranging the formulas:
C10 = 2 x Cff x (VOUT - VFB)/(VOUT + VFB)
C5 = Cff – (C10 / 2)
MANUFACTURER INDUCTOR L (µH) RL (m) CURRENT RATING (A) L x W x H (mm)
FDK MIPF2016 2.2 110 1.1 2.0 x 1.6 x 1.0
FDK MIPF2520D 2.2 80 1.3 2.5 x 2.0 x 1.0
LQH32CN2R2M5 2.2 97 0.79 3.2 x 2.5 x 1.55
Murata LQM31P 2.2 220 0.9 3.2 x 1.6 x 0.95
Sumida CDRH2D09 2.2 120 0.44 3.2 x 3.2 x 1.0
TDK GLF251812T 2.2 200 0.6 2.5 x 1.8 x 1.35
TOKO D2812C 2.2 140 0.77 2.8 x 2.8 x 1.2
TOKO MDT2520-CR 2.2 80 0.7 2.5 x 2.0 x 1.0
TPC Series 2.2 55 1.8 4.0 x 4.0 x 1.1
Wurth TPC Series 4.7 124 1.35 4.0 x 4.0 x 1.1
Taiyo Yuden CB2518T 2.2 90 0.51 2.5 x 1.8 x 2.0
Table 1. Recommended Inductors
MAX8667/MAX8668
1.5MHz Dual Step-Down DC-DC Converters
with Dual LDOs and Individual Enables
______________________________________________________________________________________ 15
C10 is needed if VOUT > 1.5V or VIN12 can be less than
VOUT / 0.65.
LDO Output Capacitor and Stability
Connect a 4.7µF ceramic capacitor between OUT3 and
GND, and a second 4.7µF ceramic capacitor from
OUT4 to GND. For a constant loading above 10mA, the
output capacitors can be reduced to 2.2µF. The equiv-
alent series resistance (ESR) of the LDO output capaci-
tors affects stability and output noise. Use output
capacitors with an ESR of 0.1or less to ensure stable
operation and optimum transient response. Surface-
mount ceramic capacitors have very low ESR and are
commonly available. Connect these capacitors as
close as possible to the IC’s pins to minimize PCB trace
inductance.
Thermal Considerations
The maximum package power dissipation of the
MAX8667/MAX8668 is 1667mW. Make sure the power
dissipated by the MAX8667/MAX8668 does not exceed
this rating. The total IC power dissipation is the sum of
the power dissipation of the four regulators:
Estimate the OUT1 and OUT2 power dissipations as
follows:
where RLis the inductor’s DC resistance, and ηis the
efficiency (see the
Typical Operating Characteristics
section).
Calculate the OUT3 and OUT4 power dissipations as
follows:
The maximum junction temperature of the MAX8667/
MAX8668 is +150°C. The junction-to-case thermal
resistance (θJC) of the MAX8667/MAX8668 is 6.9°C/W.
When mounted on a single-layer PCB, the junction to
ambient thermal resistance (θJA) is about 64°C/W.
Mounted on a multilayer PCB, θJA is about 48°C/W.
Calculate the junction temperature of the
MAX8667/MAX8668 as follows:
where TAis the maximum ambient temperature. Make
sure the calculated value of TJdoes not exceed the
+150°C maximum.
PCB Layout
High switching frequencies and relatively large peak
currents make PCB layout a very important aspect of
design. Good design minimizes excessive EMI on the
feedback paths and voltage gradients in the ground
plane, both of which can result in instability or regula-
tion errors. Connect the input capacitors as close as
possible to the IN_ and PGND_ pins. Connect the
inductor and output capacitors as close as possible to
the IC and keep the traces short, direct, and wide.
The feedback network traces are sensitive to inductor
magnetic field interference. Route these traces away
from the inductors and noisy traces such as LX. Keep
the feedback components close to the FB_ pin.
Connect GND and PGND_ to the ground plane.
Connect the exposed paddle to the ground plane with
one or more vias to help conduct heat away from the
IC.
Refer to the MAX8668 evaluation kit for a PCB layout
example.
TTP
JADJA
=+×
θ
PI V V
D OUT IN OUT 4434 4
()
PI V V
D OUT IN OUT 3334 3
()
PI V
D OUT OUT 22 2
1
×
−η
η
PI V
D OUT OUT 11 1
1
×
−η
η
PPPPP
DDDDD
=+++
1234
MAX8667/MAX8668
1.5MHz Dual Step-Down DC-DC Converters
with Dual LDOs and Individual Enables
16 ______________________________________________________________________________________
Chip Information
PROCESS: BiCMOS
Ordering Information (continued)
All MAX8667/MAX8668 parts are in a 16-pin, thin QFN, 3mm x
3mm package and operate in the -40°C to = +85°C extended
temperature range.
+
Denotes a lead-free package.
PART PKG CODE TOP MARK
MAX8667ETEHR+
T1633-4 AFJ
MAX8667ETEJS+
T1633-4 AFQ
MAX8668ETEA+
T1633-4 AER
MAX8668ETEP+
T1633-4 AFK
MAX8668ETEQ+
T1633-4 AFR
MAX8668ETET+ T1633-4 AFS
MAX8668ETEU+
T1633-4 AFL
MAX8668ETEV+
T1633-4 AFT
MAX8668ETEW+
T1633-4 AFU
MAX8668ETEX+
T1633-4 AFV
Selector Guide
PART
OUT1
(V)
OUT2
(V)
OUT3
(V)
OUT4
(V)
MAX8667ETEAA+
1.20 1.80 2.80 2.80
MAX8667ETEAB+
1.20 1.80 2.85 2.85
MAX8667ETEAC+
1.20 1.80 1.20 1.20
MAX8667ETECQ+
1.60 1.80 2.80 1.20
MAX8667ETEHR+
1.80 1.20 2.60 2.80
MAX8667ETEJS+
1.30 1.30 3.30 2.70
MAX8668ETEA+ ADJ ADJ 2.80 2.80
MAX8668ETEP+ ADJ ADJ 3.30 1.80
MAX8668ETEQ+
ADJ ADJ 2.80 1.20
MAX8668ETET+ ADJ ADJ 3.30 3.30
MAX8668ETEU+ ADJ ADJ 3.30 2.80
MAX8668ETEV+ ADJ ADJ 3.30 2.50
MAX8668ETEW+
ADJ ADJ 3.30 3.00
MAX8668ETEX+ ADJ ADJ 2.80 1.80
MAX8667/MAX8668
1.5MHz Dual Step-Down DC-DC Converters
with Dual LDOs and Individual Enables
______________________________________________________________________________________ 17
Package Information
(The package drawing(s) in this data sheet may not reflect the most current specifications. For the latest package outline information
go to www.maxim-ic.com/packages.)
12x16L QFN THIN.EPS
0.10 C0.08 C
0.10 M C A B
D
D/2
E/2
E
A1
A2
A
E2
E2/2
L
k
e
(ND - 1) X e
(NE - 1) X e
D2
D2/2
b
L
e
L
C
L
e
C
L
L
C
L
C
PACKAGE OUTLINE
21-0136
2
1
I
8, 12, 16L THIN QFN, 3x3x0.8mm
MARKING
AAAA
MAX8667/MAX8668
1.5MHz Dual Step-Down DC-DC Converters
with Dual LDOs and Individual Enables
Maxim cannot assume responsibility for use of any circuitry other than circuitry entirely embodied in a Maxim product. No circuit patent licenses are
implied. Maxim reserves the right to change the circuitry and specifications without notice at any time.
18
____________________Maxim Integrated Products, 120 San Gabriel Drive, Sunnyvale, CA 94086 408-737-7600
© 2007 Maxim Integrated Products is a registered trademark of Maxim Integrated Products. Inc.
Package Information (continued)
(The package drawing(s) in this data sheet may not reflect the most current specifications. For the latest package outline information
go to www.maxim-ic.com/packages.)
EXPOSED PAD VARIATIONS
CODES
PKG.
T1233-1
MIN.
0.95
NOM.
1.10
D2
NOM.
1.10
MAX.
1.25
MIN.
0.95
MAX.
1.25
E2
12N
k
A2
0.25
NE
A1
ND
0
0.20 REF
--
3
0.02
3
0.05
L
e
E
0.45
2.90
b
D
A
0.20
2.90
0.70
0.50 BSC.
0.55
3.00
0.65
3.10
0.25
3.00
0.75
0.30
3.10
0.80
16
0.20 REF
0.25 -
0
4
0.02
4
-
0.05
0.50 BSC.
0.30
2.90
0.40
3.00
0.20
2.90
0.70
0.25
3.00
0.75
3.10
0.50
0.80
3.10
0.30
PKG
REF. MIN.
12L 3x3
NOM. MAX. NOM.
16L 3x3
MIN. MAX.
0.35 x 45°
PIN ID JEDEC
WEED-1
T1233-31.10 1.25 0.95 1.10 0.35 x 45°1.25 WEED-1
0.95
T1633F-3 0.65
T1633-4 0.95
0.80 0.95 0.65 0.80
1.10 1.25 0.95 1.10
0.225 x 45°
0.95 WEED-2
0.35 x 45°
1.25 WEED-2
T1633-2 0.95 1.10 1.25 0.95 1.10 0.35 x 45°
1.25 WEED-2
PACKAGE OUTLINE
21-0136 2
2
I
8, 12, 16L THIN QFN, 3x3x0.8mm
WEED-11.25
1.100.95 0.35 x 45°
1.251.10
0.95
T1233-4
T1633FH-3 0.65 0.80 0.95 0.225 x 45°
0.65 0.80 0.95 WEED-2
NOTES:
1. DIMENSIONING & TOLERANCING CONFORM TO ASME Y14.5M-1994.
2. ALL DIMENSIONS ARE IN MILLIMETERS. ANGLES ARE IN DEGREES.
3. N IS THE TOTAL NUMBER OF TERMINALS.
4. THE TERMINAL #1 IDENTIFIER AND TERMINAL NUMBERING CONVENTION SHALL CONFORM TO
JESD 95-1 SPP-012. DETAILS OF TERMINAL #1 IDENTIFIER ARE OPTIONAL, BUT MUST BE LOCATED
WITHIN THE ZONE INDICATED. THE TERMINAL #1 IDENTIFIER MAY BE EITHER A MOLD OR
MARKED FEATURE.
5. DIMENSION b APPLIES TO METALLIZED TERMINAL AND IS MEASURED BETWEEN 0.20 mm AND 0.25 mm
FROM TERMINAL TIP.
6. ND AND NE REFER TO THE NUMBER OF TERMINALS ON EACH D AND E SIDE RESPECTIVELY.
7. DEPOPULATION IS POSSIBLE IN A SYMMETRICAL FASHION.
8. COPLANARITY APPLIES TO THE EXPOSED HEAT SINK SLUG AS WELL AS THE TERMINALS.
9. DRAWING CONFORMS TO JEDEC MO220 REVISION C.
10. MARKING IS FOR PACKAGE ORIENTATION REFERENCE ONLY.
11. NUMBER OF LEADS SHOWN ARE FOR REFERENCE ONLY.
12. WARPAGE NOT TO EXCEED 0.10mm.
0.25 0.30 0.35
2
0.25
0
0.20 REF
--
0.02 0.05
0.35
8
2
0.55 0.75
2.90
2.90 3.00 3.10
0.65 BSC.
3.00 3.10
8L 3x3
MIN.
0.70 0.75 0.80
NOM. MAX.
TQ833-1 1.250.25 0.70 0.35 x 45° WEEC1.250.700.25
T1633-5 0.95 1.10 1.25 0.35 x 45° WEED-20.95 1.10 1.25
Revision History
Pages changed at Rev 1: 1, 12, 14, 18
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MAX8667ETEAA+ MAX8667ETEAA+T MAX8667ETEAB+ MAX8667ETEAB+T MAX8668ETET+ MAX8668ETET+T
MAX8668ETEA+ MAX8668ETEP+ MAX8668ETEQ+ MAX8668ETEU+ MAX8668ETEV+ MAX8668ETEW+
MAX8668ETEX+ MAX8667ETEHR+T MAX8667ETEAC+T MAX8667ETECQ+T MAX8667ETEHR+
MAX8667ETEJS+ MAX8667ETEJS+T MAX8668ETEA+T MAX8668ETEV+T MAX8668ETEW+T MAX8667ETEAC+
MAX8667ETECQ+ MAX8668ETEP+T MAX8668ETEQ+T MAX8668ETEU+T MAX8668ETEX+T