MT9V022IA7ATCH-GEVB - ON Semiconductor

October, 2018 − Rev. 7

1Publication Order Number:

MT9V022/D

MT9V022

MT9V022 1/3‐Inch Wide

VGA CMOS Digital Image

Sensor

Table 1. KEY PERFORMANCE PARAMETERS

Parameter Value

Optical Format 1/3-inch

Active Imager Size 4.51 mm (H) × 2.88 mm (V)

5.35 mm Diagonal

Active Pixels 752H × 480 V

Pixel Size 6.0 mm × 6.0 mm

Color Filter Array Monochrome or Color RGB Bayer

Pattern

Shutter Type Global Shutter − TrueSNAP

Maximum Data Rate / Master Clock 26.6 MPS/26.6 MHz

Full Resolution 752 x 480

Frame Rate 60 fps (at Full Resolution)

ADC Resolution 10−bit Column−Parallel

Responsivity 4.8 V/lux−sec (550 nm)

Dynamic Range >55 dB;

>80 dB−100dB in HiDy Mode

Supply Voltage 3.3 V ±0.3 V (All Supplies)

Power Consumption <320 mW at Maximum Data Rate;

100 mW Standby Power

Operating Temperature −40°C to + 85°C

Packaging 52−Ball IBGA, Automotive−Qualified;

Wafer or Die

Features

•ON Semiconductor DigitalClarity CMOS Imaging

Technology

•Array Format: Wide−VGA, Active 752-H x 480 V

(360,960 pixels)

•Global Shutter Photodiode Pixels; Simultaneous

Integration and Readout

•Monochrome or Color: Near_IR Enhanced

Performance for Use With Non−Visible NIR

Illumination

•Readout Modes: Progressive or Interlaced

•Shutter Efficiency: >99%

•Simple Two−Wire Serial Interface

•Register Lock Capability

•Window Size: User Programmable to Any Smaller

Format (QVGA, CIF, QCIF, etc.). Data Rate Can Be

Maintained Independent of Window Size

•Binning: 2 x 2 and 4 x 4 of the Full Resolution

•ADC: On−chip, 10−bit Column−Parallel (Option to

Operate in 12−bit to 10−bit Companding Mode)

•Automatic Controls: Auto Exposure Control (AEC) and

Auto Gain Control (AGC); Variable Regional and

Variable Weight AEC/AGC

•Support for Four Unique Serial Control Register IDs to

Control Multiple Imagers On the Same Bus

•Data Output Formats:

−Single Sensor Mode:¨

10−bit Parallel/Stand−Alone 8−bit or 10−bit Serial

LVDS

−Stereo Sensor Mode: Interspersed 8−bit Serial LVDS

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See detailed ordering information on page 2 of this data

sheet.

ORDERING INFORMATION

Applications

•Automotive

•Unattended Surveillance

•Stereo Vision

•Security

•Smart Vision

•Automation

•Video as Input

•Machine Vision

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ORDERING INFORMATION

Table 2. AVAILABLE PART NUMBERS

Part Number Description

MT9V022177ATM 52−Ball IBGA (monochrome)

MT9V0221A7ATM 52−Ball IBGA (lead−free monochrome)

MT9V022177ATMC 52−Ball IBGA (color)

MT9V0221A7ATC 52−Ball IBGA (lead−free color)

GENERAL DESCRIPTION

The ON Semiconductor MT9V022 is a 1/3−inch

wide−VGA format CMOS active−pixel digital image sensor

with global shutter and high dynamic range (HDR)

operation. The sensor has specifically been designed to

support the demanding interior and exterior automotive

imaging needs, which makes this part ideal for a wide

variety of imaging applications in real−world environments.

This wide−VGA CMOS image sensor features

DigitalClarity↓ON Semiconductor breakthrough low−

noise CMOS imaging technology that achieves CCD image

quality (based on signal−to− noise ratio and low−light

sensitivity) while maintaining the inherent size, cost, and

integration advantages of CMOS.

The active imaging pixel array is 752H x 480V. It

incorporates sophisticated camera functions on−chip—such

as binning 2 x 2 and 4 x 4, to improve sensitivity when

operating in smaller resolutions−as well as windowing,

column and row mirroring. It is programmable through a

simple two−wire serial interface.

The MT9V022 can be operated in its default mode or be

programmed for frame size, exposure, gain setting, and

other parameters. The default mode outputs a wide−VGA−

size image at 60 frames per second (fps).

An on−chip analog−to−digital converter (ADC) provides

10 bits per pixel. A 12−bit resolution companded for 10 bits

for small signals can be alternatively enabled, allowing more

accurate digitization for darker areas in the image.

In addition to a traditional, parallel logic output the

MT9V022 also features a serial low− voltage differential

signaling (LVDS) output. The sensor can be operated in a

stereo− camera, and the sensor, designated as a

stereo−master, is able to merge the data from itself and the

stereo−slave sensor into one serial LVDS stream.

The sensor is designed to operate in a wide temperature

range (–40°C to + 85°C).

Control Register

Timing and Control

Digital Processing

Analog Processing

ADCs

Active−Pixel

Sensor (APS)

Array

752H x 480 V

Slave Video LVDS in

(for stereo applications only)

Serial Video

LVDS Out

Parallel

Video

Data Out

Serial

I/O

Figure 1. Block Diagram

MT9V022

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Figure 2. 52−Ball IBGA Package

SURE

ADR0

OUT

SER_

GND

PIXCLK DOUT1

SHFT_

SER_

VDD

BALL DESCRIPTIONS

Table 3. BALL DESCRIPTIONS (Only pins DOUT0 through DOUT9 may be tri−stated)

52−Ball IBGA

Numbers Symbol Type Description Note

H7 RSVD Input Connect to DGND.1

D2 SER_DATAIN_N Input Serial data in for stereoscopy (differential negative). Tie to 1K∧ pull−

up (to 3.3 V) in non−stereoscopy mode.

D1 SER_DATAIN_P Input Serial data in for stereoscopy (differential positive). Tie to DGND in

non−stereoscopy mode.

C2 BYPASS_CLKIN_N Input Input bypass shift−CLK (differential negative). Tie to 1K∧ pull− up (to

3.3 V) in non−stereoscopy mode.

C1 BYPASS_CLKIN_P Input Input bypass shift−CLK (differential positive). Tie to DGND in non−

stereoscopy mode.

H3 EXPOSURE Input Rising edge starts exposure in slave mode.

H4 SCLK Input Two−wire serial interface clock. Connect to VDD with 1.5 K resistor

even when no other two−wire serial interface peripheral is attached.

H6 OE Input DOUT enable pad, active HIGH. 2

G7 S_CTRL_ADR0 Input Two−wire serial interface slave address bit 3.

H8 S_CTRL_ADR1 Input Two−wire serial interface slave address bit 5.

G8 RESET# Input Asynchronous reset. All registers assume defaults.

F8 STANDBY Input Shut down sensor operation for power saving.

A5 SYSCLK Input Master clock (26.6 MHz).

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Table 3. BALL DESCRIPTIONS (Only pins DOUT0 through DOUT9 may be tri−stated)

52−Ball IBGA

Numbers NoteDescriptionTypeSymbol

G4 SDATA I/O Two−wire serial interface data. Connect to VDD with 1.5 K resistor

even when no other two−wire serial interface peripheral is attached.

G3 STLN_OUT I/O Output in master mode−start line sync to drive slave chip

in−phase; input in slave mode.

G5 STFRM_OUT I/O Output in master mode−start frame sync to drive a slave

chip in−phase; input in slave mode.

H2 LINE_VALID Output Asserted when DOUT data is valid.

G2 FRAME_VALID Output Asserted when DOUT data is valid.

E1 DOUT5 Output Parallel pixel data output 5.

F1 DOUT6 Output Parallel pixel data output 6.

F2 DOUT7 Output Parallel pixel data output 7.

G1 DOUT8 Output Parallel pixel data output 8

H1 DOUT9 Output Parallel pixel data output 9.

H5 ERROR Output Error detected. Directly connected to STEREO ERROR FLAG.

G6 LED_OUT Output LED strobe output.

B7 DOUT4 Output Parallel pixel data output 4.

A8 DOUT3 Output Parallel pixel data output 3.

A7 DOUT2 Output Parallel pixel data output 2.

B6 DOUT1 Output Parallel pixel data output 1.

A6 DOUT0Output Parallel pixel data output 0.

B5 PIXCLK Output Pixel clock out. DOUT is valid on rising edge of this clock.

B3 SHFT_CLKOUT_N Output Output shift CLK (differential negative).

B2 SHFT_CLKOUT_P Output Output shift CLK (differential positive).

A3 SER_DATAOUT_N Output Serial data out (differential negative).

A2 SER_DATAOUT_P Output Serial data out (differential positive).

B4, E2 VDD Supply Digital power 3.3V.

C8, F7 VAA Supply Analog power 3.3V.

B8 VAAPIX Supply Pixel power 3.3V.

A1, A4 VDDLVDS Supply Dedicated power for LVDS pads.

B1, C3 LVDSGND Ground Dedicated GND for LVDS pads.

C6, F3 DGND Ground Digital GND.

C7, F6 AGND Ground Analog GND.

E7, E8, D7, D8 NC NC No connect. 3

1. Pin H7 (RSVD) must be tied to GND

2. Output Enable (OE) tri−states signals DOUT0–DOUT9. No other signals are tri−stated with OE.

3. No connect. These pins must be left floating for proper operation.

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Master Clock

STANDBY from

Controller or

Digital GND

Two−Wire

Serial Interface

SYSCLK

RESET#

EXPOSURE

STANDBY

S_CTRL_ADR0

S_CTRL_ADR1

SCLK

SDATA

RSVD LVDSGND

DOUT(9:0

)

DGND AGND

LINE_VALID

FRAME_VALID

PIXCLK

LED_OUT

ERROR

To Controller

To LED Output

VDDLVDS VDD

VDD

VAA

VAA VAAPIX

VAAPIX

10KW

1.5KW

0.1mF

Figure 3. Typical Configuration (Connection)−Parallel Output Mode

NOTE: LVDS signals are to be left floating.

VDD

VDD VAA

VAA

VDDLVDS

DOUT(9:0)

Master Clock

STANDBY from

Controller or

Digital GND

Two−Wire

Serial Interface

SYSCLK

RESET#

EXPOSURE

STANDBY

S_CTRL_ADR0

S_CTRL_ADR1

SCLK

SDATA

RSVD LVDSGND

DOUT(9:0

)

DGND AGND

LINE_VALID

FRAME_VALID

PIXCLK

LED_OUT

ERROR

To Controller

To LED Output

VDDLVDS VDD

VDD

VAA

VAA VAAPIX

VAAPIX

10KW

1.5KW

0.1mF

NOTE: LVDS signals are to be left floating.

VDD

VDD VAA

VAA

VDDLVDS

DOUT(9:0)

DGND

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PIXEL DATA FORMAT

Pixel Array Structure

The MT9V022 pixel array is configured as 782 columns

by 492 rows, shown in Figure 4. The left 26 columns and the

top eight rows of pixels are optically black and can be used

to monitor the black level. The black row data is used

internally for the automatic black level adjustment.

However, the middle four black rows can also be read out by

setting the sensor to raw data output mode. There are 753

columns by 481 rows of optically active pixels. The active

area is surrounded with optically transparent dummy

columns and rows to improve image uniformity within the

active area. One additional active column and active row are

used to allow horizontally and vertically mirrored readout to

also start on the same color pixel.

8 dark, 1 light dummy rows

2 dummy rows

2 dummy

columns

26 dark, 1 light

dummy columns

(0.0)

(782,492)

Figure 4. Pixel Array Description

Pixel

(2,9)

Figure 5. Pixel Color Pattern Detail (Top Right Corner)

Column Readout Direction

Row

Readout

Direction

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COLOR DEVICE LIMITATIONS

The color version of the MT9V022 does not support or

offers reduced performance for the following

functionalities.

Pixel Binning

Pixel binning is done on immediate neighbor pixels only,

no facility is provided to skip pixels according to a Bayer

pattern. Therefore, the result of binning combines pixels of

different colors. For more information, see :”Pixel

Binning”.

Interlaced Readout

Interlaced readout yields one field consisting only of red

and green pixels and another consisting only of blue and

green pixels. This is due to the Bayer pattern of the CFA.

Automatic Black Level Calibration

When the color bit is set (R0x0F[2]=1), the sensor uses

GREEN1 pixels black level correction value, which is

applied to all colors. To use calibration value based on all

dark pixels offset values, the color bit should be cleared.

Other Limiting Factors

Black level correction and row−wise noise correction are

applied uniformly to each color. Automatic exposure and

gain control calculations are made based on all three colors,

not just the green luma channel. High dynamic range does

operate; however, ON Semiconductor strongly recommends

limiting use to linear operation if good color fidelity is

required.

OUTPUT DATA FORMAT

The MT9V022 image data can be read out in a progressive

scan or interlaced scan mode. Valid image data is surrounded

by horizontal and vertical blanking, as shown in Figure 6.

The amount of horizontal and vertical blanking is

programmable through R0x05 and R0x06, respectively.

LINE_VALID is HIGH during the shaded region of the

figure. See “Output Data Timing” for the description of

FRAME_VALID timing.

VALID iMAGE HORIZONTAL

BLANKING

VERTICAL/HORIZONTAL

BLANKING

VERTICAL BLANKING

00 00 00 ………… 00 00 00

P0,0 P0,1 P0,2…………P0,n−1 P0,n

P1,0 P1,1 P1,2…………P1,n−1 P1,n

Pm−1,0 Pm−1,1…………Pm−1,n−1 Pm−1,n

Pm,0 Pm,1…………Pm,n−1 Pm,n

Figure 6. Spatial Illustration of Image Readout

Output Data Timing

The data output of the MT9V022 is synchronized with the

PIXCLK output. When LINE_VALID is HIGH, one 10−bit

pixel datum is output every PIXCLK period.

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LINE_VALID

PIXCLK

Blanking Valide Image Data Blanking

(9:0) P1

(9:0) P2

(9:0) P3

(9:0) P4

(9:0)

Pn−1

(9:0)

…

Figure 7. Timing Example of Pixel Data

DOUT(9:0)

The PIXCLK is a nominally inverted version of the master

clock (SYSCLK). This allows PIXCLK to be used as a clock

to latch the data. However, when column bin 2 is enabled, the

PIXCLK is HIGH for one complete master clock master

period and then LOW for one complete master clock period;

when column bin 4 is enabled, the PIXCLK is HIGH for two

complete master clock periods and then LOW for two

complete master clock periods. It is continuously enabled,

even during the blanking period. Setting R0x74 bit[4] = 1

causes the MT9V022 to invert the polarity of the PIXCLK.

The parameters P1, A, Q, and P2 in Figure 8 are defined

in Table 4.

Figure 8. Row Timing and FRAME_VALID/LINE_VALID Signals

P1 A QA QAP2

FRAME_VALID

LINE_VALID

...

Number of master clocks

Table 4. FRAME TIME

Parameter Name Equation Default Timing at 26.66 MHz

AActive data time R0x04 752 pixel clocks

= 752 master = 28.20ms

P1 Frame start blanking R0x05 − 23 71 pixel clocks

= 71master = 2.66ms

P2 Frame end blanking 23 (fixed) 23 pixel clocks

= 23 master = 0.86ms

QHorizontal blanking R0x05 94 pixel clocks

= 94 master = 3.52ms

A+Q Row time R0x04 + R0x05 846 pixel clocks

= 846 master = 31.72ms

VVertical blanking (R0x06) × (A + Q) + 4 38,074 pixel clocks

= 38,074 master = 1.43ms

Nrows × (A + Q) Frame valid time (R0x03) × (A + Q) 406,080 pixel clocks

= 406,080 master = 15.23ms

FTotal frame time V + (Nrows × (A + Q)) 444,154 pixel clocks

= 444,154 master = 16.66ms

Sensor timing is shown above in terms of pixel clock and

master clock cycles (refer to Figure 7). The recommended

master clock frequency is 26.66 MHz. The vertical blanking

and total frame time equations assume that the number of

integration rows (bits 11 through 0 of R0x0B) is less than the

number of active rows plus blanking rows minus overhead

rows (R0x03 + R0x06 − 2). If this is not the case, the number

of integration rows must be used instead to determine the

frame time, as shown in Table 5. In this example it is

assumed that R0x0B is programmed with 523 rows. For

Simultaneous Mode, if the exposure time register (0x0B)

exceeds the total readout time, then vertical blanking is

internally extended automatically to adjust for the additional

integration exposure time required. This extended value is

not written back to R0x06 (vertical blanking). R0x06 can be

used to adjust frame to frame readout time. This register

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does not affect the exposure time but it may extend the

readout time.

Table 5. FRAME TIME − LONG INTEGRATION TIME

Parameter Name

Equation

(Number of Master Clock Cycles) Default Timing at 26.66 MHz

V’ Vertical blanking

(long integration time) (R0x0B + 2 − R0x03) × (A + Q) + 4 38,074 pixel clocks

= 38,074 master = 1.43ms

F” Total frame time

(long integration exposure time) (R0x0B + 2) × (A + Q) + 4 444,154 pixel clocks

= 444,154 master = 16.66ms

4. The MT9V022 uses column parallel analog−to−digital converters, thus short row timing is not possible. The minimum total row time is 660

columns (horizontal width + horizontal blanking). The minimum horizontal blanking is 43. When the window width is set below 617, horizontal

blanking must be increased. The frame rate will not increase for row times less than 660 columns.

SERIAL BUS DESCRIPTION

Registers are written to and read from the MT9V022

through the two−wire serial interface bus. The MT9V022 is

a serial interface slave with four possible IDs (0x90, 0x98,

0xB0,and 0xB8) determined by the S_CTRL_ADR0 and

S_CTRL_ADR1 input pins. Data is transferred into the

MT9V022 and out through the serial data (SDATA) line. The

SDATA line is pulled up to VDD off−chip by a 1.5 KW resistor.

Either the slave or master device can pull the SDATA line

down−the serial interface protocol determines which device

is allowed to pull the SDATA line down at any given time. The

registers are 16−bit wide, and can be accessed through 16−

or 8−bit two−wire serial interface sequences.

Protocol

The two−wire serial interface defines several different

transmission codes, as follows:

•a start bit

•the slave device 8−bit address

•a(n) (no) acknowledge bit

•an 8−bit message

•a stop bit

Sequence

A typical read or write sequence begins by the master

sending a start bit. After the start bit, the master sends the

slave device’s 8−bit address. The last bit of the address

determines if the request is a read or a write, where a “0”

indicates a write and a “1” indicates a read. The slave device

acknowledges its address by sending an acknowledge bit

back to the master.

If the request was a write, the master then transfers the

8−bit register address to which a write should take place. The

slave sends an acknowledge bit to indicate that the register

address has been received. The master then transfers the data

eight bits at a time, with the slave sending an acknowledge

bit after each eight bits. The MT9V022 uses 16−bit data for

its internal registers, thus requiring two 8−bit transfers to

write to one register. After 16 bits are transferred, the register

address is automatically incremented, so that the next 16 bits

are written to the next register address. The master stops

writing by sending a start or stop bit.

A typical read sequence is executed as follows. First the

master sends the write mode slave address and 8−bit register

address, just as in the write request. The master then sends

a start bit and the read mode slave address. The master then

clocks out the register data eight bits at a time. The master

sends an acknowledge bit after each 8−bit transfer. The

transferred. The data transfer is stopped when the master

sends a no−acknowledge bit. The MT9V022 allows for 8−bit

data transfers through the two−wire serial interface by

writing (or reading) the most significant 8 bits to the register

and then writing (or reading) the least significant 8 bits to

R0xF0 (240).

Bus Idle State

The bus is idle when both the data and clock lines are

HIGH. Control of the bus is initiated with a start bit, and the

bus is released with a stop bit. Only the master can generate

the start and stop bits.

Start Bit

The start bit is defined as a HIGH−to−LOW transition of

the data line while the clock line is HIGH.

Stop Bit

The stop bit is defined as a LOW−to−HIGH transition of

the data line while the clock line is HIGH.

Slave Address

The 8−bit address of a two−wire serial interface device

consists of 7 bits of address and 1 bit of direction. A “0” in

the LSB of the address indicates write mode, and a “1”

indicates read mode. As indicated above, the MT9V022

allows four possible slave addresses determined by the two

input pins, S_CTRL_ADR0 and S_CTRL_ADR1.

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Table 6. SLAVE ADDRESS MODES

{S_CTRL_ADR1, S_CTRL_ADR0} Slave Address Write/Read Mode

00 0x90 Write

0x91 Read

01 0x98 Write

0x99 Read

10 0xB0 Write

0xB1 Read

11 0xB8 Write

0xB9 Read

Data Bit Transfer

One data bit is transferred during each clock pulse. The

two−wire serial interface clock pulse is provided by the

master. The data must be stable during the HIGH period of

the serial clock−it can only change when the two−wire serial

interface clock is LOW. Data is transferred 8 bits at a time,

followed by an acknowledge bit.

Acknowledge Bit

The master generates the acknowledge clock pulse. The

transmitter (which is the master when writing, or the slave

when reading) releases the data line, and the receiver

indicates an acknowledge bit by pulling the data line LOW

during the acknowledge clock pulse.

No−Acknowledge Bit

The no−acknowledge bit is generated when the data line

is not pulled down by the receiver during the acknowledge

clock pulse. A no−acknowledge bit is used to terminate a

read sequence.

TWO−WIRE SERIAL INTERFACE SAMPLE READ

AND WRITE SEQUENCES

16−Bit Write Sequence

A typical write sequence for writing 16 bits to a register

is shown in Figure 9. A start bit given by the master, followed

by the write address, starts the sequence. The image sensor

then gives an acknowledge bit and expects the register

address to come first, followed by the 16−bit data. After each

8−bit word is sent, the image sensor gives an acknowledge

bit. All 16 bits must be written before the register is updated.

After 16 bits are transferred, the register address is

automatically incremented, so that the next 16 bits are

written to the next register. The master stops writing by

sending a start or stop bit.

Figure 9. Timing Diagram Showing a Write to R0x09 with Value 0x0284

SCLK

START ACK

0xB8 ADDR 0000 0010

R0x09

ACK ACK ACK

STOP

1000 0100

SDATA

16−Bit Read Sequence

A typical read sequence is shown in Figure 10. First the

master has to write the register address, as in a write

sequence. Then a start bit and the read address specify that

a read is about to happen from the register. The master then

clocks out the register data 8 bits at a time. The master sends

an acknowledge bit after each 8−bit transfer. The register

address is auto−incremented after every 16 bits is

transferred. The data transfer is stopped when the master

sends a no−acknowledge bit.

Figure 10. Timing Diagram Showing a Read from R0x09; Returned Value 0x0284

SCLK

START ACK

0xB8 ADDR 0xB9 ADDR 0000 0010

R0x09

ACK ACK ACK

STOP

1000 0100

NACK

SDATA

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8−Bit Write Sequence

To be able to write 1 byte at a time to the register, a special

writing the upper 8 bits to the desired register and then

writing the lower 8 bits to the special register address

(R0xF0). The register is not updated until all 16 bits have

been written. It is not possible to just update half of a register.

In Figure 11, a typical sequence for 8−bit writing is shown.

The second byte is written to the special register (R0xF0).

Figure 11. Timing Diagram Showing a Bytewise Write to R0x09 with Value 0x0284

STOP

ACKSTART

0xB8 ADDR

ACK

SCLK

ACKACKACKACK

R0x09

0xB8 ADDR 0000 0010 1000 0100

START

SDATA R0xF0

8−Bit Read Sequence

To read one byte at a time the same special register address

is used for the lower byte. The upper 8 bits are read from the

desired register. By following this with a read from the

special register (R0xF1) the lower 8 bits are accessed

(Figure 12). The master sets the no−acknowledge bits

shown.

Figure 12. Timing Diagram Showing a Bytewise Read from R0x09; Returned Value 0x0284

START

0xB9 ADDR

SCLK

STOP

ACKACKACK

R0x09

START

0xB8 ADDR 0000 0010

START

0xB9 ADDR

SCLK

NACKACKACKACKSTART

0xB8 ADDR 1000 0100

SDATA

NACK

R0xF0

Included in the MT9V022 is a register lock (R0xFE)

feature that can be used as a solution to reduce the

probability of an inadvertent noise−triggered two−wire

serial interface write to the sensor. All registers (or read

mode register−register 13 only) can be locked; it is

important to prevent an inadvertent two−wire serial

interface write to register 13 in automotive applications

since this register controls the image orientation and any

unintended flip to an image can cause serious results.

At power−up, the register lock defaults to a value of

0xBEEF, which implies that all registers are unlocked and

any two−wire serial interface writes to the register gets

committed.

Lock All Registers

If a unique pattern (0xDEAD) to R0xFE is programmed,

any subsequent two−wire serial interface writes to registers

(except R0xFE) are NOT committed. Alternatively, if the

user writes a 0xBEEF to the register lock register, all

registers are unlocked and any subsequent two−wire serial

interface writes to the register are committed.

Lock Read More Register Only (R0x0D)

If a unique pattern (0xDEAF) to R0xFE is programmed,

any subsequent two−wire serial interface writes to register

13 are NOT committed. Alternatively, if the user writes a

0xBEEF to register lock register, register 13 is unlocked and

any subsequent two−wire serial interface writes to this

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FEATURE DESCRIPTION

Operational Modes

The MT9V022 works in master, snapshot, or slave mode.

In master mode the sensor generates the readout timing. In

snapshot mode it accepts an external trigger to start

integration, then generates the readout timing. In slave mode

the sensor accepts both external integration and readout

controls. The integration time is programmed through the

two−wire serial interface during master or snapshot modes,

or controlled via externally generated control signal during

slave mode.

Master Mode

There are two possible operation methods for master

mode: simultaneous and sequential. One of these operation

modes must be selected via the two−wire serial interface.

Simultaneous Master Mode

In simultaneous master mode, the exposure period occurs

during readout. The frame synchronization waveforms are

shown in Figure 13 and Figure 14. The exposure and readout

happen in parallel rather than sequential, making this the

fastest mode of operation.

Figure 13. Simultaneous Master Mode Synchronization Waveforms #1

Readout Time > Exposure Time

Readout Time

LED_OUT

FRAME_VALID

XXX

Vertical Blanking

XXX XXX

LINE_VALID

DOUT(9:0)

LED_OUT

FRAME_VALID

XXX XXX XXX

LINE_VALID

DOUT(9:0

)

Vertical Blanking

Exposure Time

Exposure Time > Readout Time

Figure 14. Simultaneous Master Mode Synchronization Waveforms #2

DOUT(9:0)

When exposure time is greater than the sum of vertical

blank and window height, the number of vertical blank rows

is increased automatically to accommodate the exposure

time.

Sequential Master Mode

In sequential master mode the exposure period is followed

by readout. The frame synchronization waveforms for

sequential master mode are shown in Figure 15. The frame

rate changes as the integration time changes.

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Figure 15. Sequential Master Mode Synchronization Waveforms

XXX XXX XXX

Exposure Time

LED_OUT

FRAME_VALID

LINE_VALID

DOUT(9:0)

Snapshot Mode

In snapshot mode the sensor accepts an input trigger

signal which initiates exposure, and is immediately

followed by readout. Figure 16. shows the interface signals

used in snapshot mode. In snapshot mode, the start of the

integration period is determined by the externally applied

EXPOSURE pulse that is input to the MT9V022. The

integration time is preprogrammed via the two−wire serial

interface on R0x0B. After the frame’s integration period is

complete the readout process commences and the syncs and

data are output. Sensor in snapshot mode can capture a single

image or a sequence of images.

The frame rate may only be controlled by changing the

period of the user supplied EXPOSURE pulse train. The

frame synchronization waveforms for snapshot mode are

shown in Figure 17.

CONTROLLER MT9V022

EXPOSURE

SYSCLK

DOUT(9:0

)

PIXCLK

LINE_VALID

FRAME_VALID

Figure 16. Snapshot Mode Interface Signals

DOUT(9:0)

Figure 17. Snapshot Mode Frame Synchronization Waveforms

XXX XXX XXX

DOUT(9:0

)

LINE_VALID

Exposure Time

LED_OUT

FRAME_VALID

EXPOSURE

DOUT(9:0)

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Slave Mode

In slave mode, the exposure and readout are controlled

using the EXPOSURE, STFRM_OUT, and STLN_OUT

pins. When the slave mode is enabled, STFRM_OUT and

STLN_OUT become input pins.

The start and end of integration are controlled by

EXPOSURE and STFRM_OUT pulses, respectively. While

a STFRM_OUT pulse is used to stop integration, it is also

used to enable the readout process.

After integration is stopped, the user provides

STLN_OUT pulses to trigger row readout. A full row of data

is read out with each STLN_OUT pulse. The user must

provide enough time between successive STLN_OUT

pulses to allow the complete readout of one row.

It is also important to provide additional STLN_OUT

pulses to allow the sensors to read the vertical blanking rows.

It is recommended that the user program the vertical blank

vertical blanking between frames by delaying the

application of the STFRM_OUT pulse.

The elapsed time between the rising edge of STLN_OUT

and the first valid pixel data is [horizontal blanking register

(R0x05) + 4] clock cycles.

Figure 18. Slave Mode Operation

Exposure

STFRM_OUT

LED_OUT

STLN_OUT

LINE_VALID

(input)

(output)

1−row

time

1−row

time

98 master

clocks

2 master

clocks

Vertical Blanking

(def=45 lines)

Integration Time

Signal Path

The MT9V022 signal path consists of a programmable

gain, a programmable analog offset, and a 10−bit ADC. See

“Black Level Calibration” for the programmable offset

operation description.

Figure 19. Signal Path

Pixel Output

(reset minus signal)

Offset Correction

Voltage (R0x48 or

result of BLC)

Gain Selection

(R0x35 or

result of AGC)

ADC Data

(9:0)

10 (12) bit ADC

On−Chip Biases

ADC Voltage Reference

The ADC voltage reference is programmed through

R0x2C, bits 2:0. The ADC reference ranges from 1.0 V to

2.1 V. The default value is 1.4 V. The increment size of the

voltage reference is 0.1 V from 1.0 V to 1.6 V (R0x2C[2:0]

values 0 to 6). At R0x2C[2:0] = 7, the reference voltage

jumps to 2.1 V.

The effect of the ADC calibration does not scale with

VREF. Instead it is a fixed value relative to the output of the

analog gain stage. At default, one LSB of calibration equals

two LSB in output data (1LSBOffset = 2 mV, 1LSBADC =

1 mV).

It is very important to preserve the correct values of the

other bits in R0x2C. The default register setting is 0x0004.

V_Step Voltage Reference

This voltage is used for pixel high dynamic range

operations, programmable from R0x31 through R0x34.

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Chip Version

Chip version registers R0x00 and R0xFF are read−only.

Window Control

Registers R0x01 column start, R0x02 Row Start, R0x03

window height (row size), and R0x04 Window Width

(column size) control the size and starting coordinates of the

window.

The values programmed in the window height and width

registers are the exact window height and width out of the

sensor. The window start value should never be set below

four.

To read out the dark rows set bit 6 of R0x0D. In addition,

bit 7 of R0x0D can be used to display the dark columns in

the image.

Blanking Control

Horizontal blanking and vertical blanking registers

R0x05 and R0x06 respectively control the blanking time in

a row (horizontal blanking) and between frames (vertical

blanking).

•Horizontal blanking is specified in terms of pixel

clocks.

•Vertical blanking is specified in terms of numbers of

rows.

The actual imager timing can be calculated using Table 4

and Table 5 which describe “Row Timing and

FRAME_VALID/LINE_VALID signals.” The minimum

number of vertical blank rows is 4.

Pixel Integration Control

Total Integration

R0x0B Total Shutter Width (In Terms of Number of Rows)

This register (along with the window width and horizontal

blanking registers) controls the integration time for the

pixels.

The actual total integration time, tINT, is:

tINT = (Number of rows of integration × row time) +

Overhead, where:

The number of rows integration is equal to the result of

automatic exposure control (AEC) which may vary from

frame to frame, or, if AEC is disabled, the value in R0x0B

Row time = (R0x04 + R0x05) master clock periods

Overhead = (R0x04 + R0x05 – 255) master clock periods

Typically, the value of R0x0B (total shutter width) is

limited to the number of rows per frame (which includes

vertical blanking rows), such that the frame rate is not

affected by the integration time. If R0x0B is increased

beyond the total number of rows per frame, it is required to

add additional blanking rows using R0x06 as needed. A

second constraint is that tINT must be adjusted to avoid

banding in the image from light flicker. Under 60 Hz flicker,

this means frame time must be a multiple of 1/120 of a

second. Under 50 Hz flicker, frame time must be a multiple

of 1/100 of a second.

Changes to Integration Time

With automatic exposure control disabled (R0xAF, bit 0

is cleared to LOW), and if the total integration time (R0x0B)

is changed via the two−wire serial interface while

FRAME_VALID is asserted for frame n, the first frame

output using the new integration time is frame (n + 2).

Similarly, when automatic exposure control is enabled, any

change to the integration time for frame n first appears in

frame (n + 2) output.

The sequence is as follows:

1. During frame n, the new integration time is held in

the R0x0B live register.

2. At the start of frame (n + 1), the new integration

time is transferred to the exposure control module.

Integration for each row of frame (n + 1) has been

completed using the old integration time. The

earliest time that a row can start integrating using

the new integration time is immediately after that

row has been read for frame (n + 1). The actual

time that rows start integrating using the new

integration time is dependent on the new value of

the integration time.

3. When frame (n + 1) is read out, it is integrated

using the new integration time. If the integration

time is changed (R0x0B written) on successive

frames, each value written is applied to a single

frame; the latency between writing a value and it

affecting the frame readout remains at two frames.

However, when automatic exposure control is

disabled, if the integration time is changed through

the two−wire serial interface after the falling edge

of FRAME_VALID for frame n, the first frame

output using the new integration time becomes

frame (n+ 3).

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FRAME_VALID

LED_OUT

New Integration

Programmed

Actual

Integration

Image Data

Frame Start

Figure 20. Latency When Changing Integration

Int = 200 rows Int = 300 rows

Output Image with

Int = 200 rows Output

Image with

Int = 300 rows

Exposure Indicator

The exposure indicator is controlled by:

•R0x1B LED_OUT Control

The MT9V022 provides an output pin, LED_OUT, to

indicate when the exposure takes place. When R0x1B bit 0

is clear, LED_OUT is HIGH during exposure. By using

R0x1B, bit 1, the polarity of the LED_OUT pin can be

inverted.

High Dynamic Range

High dynamic range is controlled by:

•R0x08 Shutter Width 1

•R0x09 Shutter Width 2

•R0x0A Shutter Width Control

•R0x31–R0x34 V_Step Voltages

In the MT9V022, high dynamic range (that is, R0x0F, bit

6 = 1) is achieved by controlling the saturation level of the

pixel (HDR or high dynamic range gate) during the exposure

period. The sequence of the control voltages at the HDR gate

is shown in Figure 21. After the pixels are reset, the step

voltage, V_Step, which is applied to HDR gate, is setup at

V1 for integration time t1 then to V2 for time t2, then V3 for

time t3, and finally it is parked at V4, which also serves as an

antiblooming voltage for the photodetector. This sequence

of voltages leads to a piecewise linear pixel response,

illustrated (in approximates) in Figure 21.

VAA(3.3V)

Figure 21. Sequence of Control Voltages at the HDR Gate

Exposure

HDR

Voltage

V1~1.4V V2~1.2V V3~1.0V

V4~0.8V

t1t2t3

VAA(3.3V)

V1~1.4V V2~1.2V V3~1.0V

t1t2t3

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Output

Light Intensity

dV1

dV2

dV3

1/t 11/t 22 1/t 3

Figure 22. Sequence of Voltages in a Piecewise Linear Pixel Response

The parameters of the step voltage V_Step which takes

values V1, V2, and V3 directly affect the position of the knee

points in Figure 22.

Light intensities work approximately as a reciprocal of the

partial exposure time. Typically, t1 is the longest exposure,

t2 shorter, and so on. Thus the range of light intensities is

shortest for the first slope, providing the highest sensitivity.

The register settings for V_Step and partial exposures are:

V1 = R0x31, bits 4:0

V2 = R0x32, bits 4:0

V3 = R0x33, bits 4:0

V4 = R0x34, bits 4:0

TINT = t1 + t2 + t3

There are two ways to specify the knee points timing, the

first by manual setting (default) and the second by automatic

knee point adjustment.

When the auto adjust enabler is set to HIGH (LOW by

default), the MT9V022 calculates the knee points

automatically using the following equations:

t1+tINT *t2*t3(eq. 1)

t2+tINT ǒ1ń2ǓR0x0A,bits3:0 (eq. 2)

t3+tINT ǒ1ń2ǓR0x0A,bits7:4 (eq. 3)

As a default for auto exposure, t2 is 1/16 of tINT, t3 is 1/64

of tINT.

When the auto adjust enabler is disabled (default), t1, t2,

and t3 may be programmed through the two−wire serial

interface:

t1+R0x08, bits14 : 0 (eq. 4)

t2+(R0x09, bits 14 : 0) *(R0x08, bits 14 : 0) (eq. 5)

t3+tINT *t1*t2(eq. 6)

tINT may be based on the manual setting of R0x0B or the

result of the AEC. If the AEC is enabled then the auto knee

adjust must also be enabled.

Variable ADC Resolution

By default, ADC resolution of the sensor is 10−bit.

Additionally, a companding scheme of 12−bit into 10−bit is

enabled by the R0x1C (28). This mode allows higher ADC

resolution which means less quantization noise at low−light,

and lower resolution at high light, where good ADC

quantization is not so critical because of the high level of the

photon’s shot noise.

10−bit

Codes

1,024

768

512

256

256 512 1,024 2,048 4,096

12−bit

Codes

8 to 1 Companding (2,048 256)

4 to 1 Companding (1,536 384)

2 to 1 Companding (256 128)

No companding (256 256)

Figure 23. 12−to 10−Bit Companding Chart

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GAIN SETTINGS

Changes to Gain Settings

When the digital gain settings (R0x80–R0x98) are

changed, the gain is updated on the next frame start.

However, the latency for an analog gain change to take effect

depends on the automatic gain control.

If automatic gain control is enabled (R0xAF, bit 1 is set to

HIGH), the gain changed for frame n first appears in frame

(n + 1); if the automatic gain control is disabled, the gain

changed for frame n first appears in frame (n + 2).

Both analog and digital gain change regardless of whether

the integration time is also changed simultaneously.

New Gain

Programmed

Actual

Gain

Image Data

Frame Start

FRAME_VALID

Gain = 3.5X

Gain = 3.0X Gain = 3.5X

Gain = 3.0X

Output Image with

Gain = 3.0X

Output

Image with

Gain = 3.5X

Figure 24. Latency of Analog Gain Change When AGC Is Disabled

Analog Gain

Analog gain is controlled by:

•R0x35 Global Gain

The formula for gain setting is:

Gain +Bits[6 : 0] x 0.0625 (eq. 7)

The analog gain range supported in the MT9V022 is

1X–4X with a step size of 6.25 percent. To control gain

manually with this register, the sensor must NOT be in AGC

mode. When adjusting the luminosity of an image, it is

recommended to alter exposure first and yield to gain

increases only when the exposure value has reached a

maximum limit.

Analog gain +bits (6 : 0) x 0.0625 for values16 *31

Analog gain +bits (6 : 0) ń2x 0.125 for values 32 *64

For values 16–31: each LSB increases analog gain

0.0625v/v. A value of 16 = 1X gain. Range: 1X to 1.9375X.

For values 32–64: each 2 LSB increases analog gain

0.125v/v (that is, double the gain increase for 2 LSB).

Range: 2X to 4X. Odd values do not result in gain increases;

the gain increases by 0.125 for values 32, 34, 36, and so on.

Digital gain is controlled by:

•R0x99–R0xA4 Tile Coordinates

•R0x80–R0x98 Tiled Digital Gain and Weight

In the MT9V022, the image may be divided into 25 tiles,

as shown in Figure 25, through the two−wire serial interface,

and apply digital gain individually to each tile.

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X0/5 X1/5 X2/5 X3/5 X4/5 X5/5

Y0/5

Y2/5

Y1/5

Y3/5

Y4/5

Y5/5

Figure 25. Tiled Sample

x0_y0 x1_y0 x4_y0

x0_y1 x1_y1 x4_y1

x0_y2 x1_y2 x4_y2

x0_y3 x1_y3 x4_y3

x0_y4 x1_y4 x4_y4

Registers 0x99–0x9E and 0x9F–0xA4 represent the

coordinates X0/5−X5/5 and Y0/5−Y5/5 in Figure 25,

respectively.

Digital gains of registers 0x80–0x98 apply to their

corresponding tiles. The MT9V022 supports a digital gain

of 0.25−3.75X.

The formula for digital gain setting is:

Digital Gain +Bits[3 : 0] 0.25 (eq. 8)

Black Level Calibration

Black level calibration is controlled by:

•R0x4C

•R0x42

•R0x46–R0x48

The MT9V022 has automatic black level calibration

on−chip, and if enabled, its result may be used in the offset

correction shown in Figure 26.

Figure 26. Black Level Calibration Flow Chart

Pixel Output

(reset minus signal)

Offset Correction

Voltage (R0x48 or

result of BLC)

Gain Selection

(R0x35 or

result of AGC)

ADC Data

(9:0)

10 (12) bit ADC

VREF

(R0x2C)

The automatic black level calibration measures the

average value of pixels from 2 dark rows (1 dark row if row

bin 4 is enabled) of the chip. (The pixels are averaged as if

they were light−sensitive and passed through the appropriate

gain.)

This row average is then digitally low−pass filtered over

many frames (R0x47, bits 7:5) to remove temporal noise and

random instabilities associated with this measurement.

Then, the new filtered average is compared to a minimum

acceptable level, low threshold, and a maximum acceptable

level, high threshold.

If the average is lower than the minimum acceptable level,

the offset correction voltage is increased by a programmable

offset LSB in R0x4C. (Default step size is 2 LSB Offset =

1 ADC LSB at analog gain = 1X.)

If it is above the maximum level, the offset correction

voltage is decreased by 2 LSB (default).

To avoid oscillation of the black level from below to

above, the region the thresholds should be programmed so

the difference is at least two times the offset DAC step size.

In normal operation, the black level calibration

value/offset correction value is calculated at the beginning

of each frame and can be read through the two−wire serial

interface from R0x48. This register is an 8−bit signed two’s

complement value.

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However, if R0x47, bit 0 is set to “1,” the calibration value

in R0x48 may be manually set to override the automatic

black level calculation result. This feature can be used in

conjunction with the “show dark rows” feature (R0x0D, bit

6) if using an external black level calibration circuit.

The offset correction voltage is generated according to the

following formulas:

Offset Correction Voltage +(8 *bit signed twoȀs complement calibration value, *127 to 127) 0.5mV (eq. 9)

ADC input voltage +(Pixel Output Voltage )Offset Correction Voltage) Analog Gain (eq. 10)

Row-wise Noise Correction

Row−wise noise correction is controlled by the following

registers:

•R0x70 Row Noise Control

•R0x72 Row Noise Constant

•R0x73 Dark Column Start

When the row−wise noise cancellation algorithm is

enabled, the average value of the dark columns read out is

used as a correction for the whole row. The row−wise

correction is in addition to the general black level correction

applied to the whole sensor frame and cannot be used to

replace the latter. The dark average is subtracted from each

pixel belonging to the same row, and then a positive constant

is added (R0x72, bits 7:0). This constant should be set to the

dark level targeted by the black level algorithm plus the

noise expected on the measurements of the averaged values

from dark columns; it is meant to prevent clipping from

negative noise fluctuations.

Pixel value +ADC value *dark column average )row noise constant (eq. 11)

On a per−row basis, the dark column average is calculated

from a programmable number of dark columns (pixels)

values (R0x70, bits 3:0). The default is 10 dark columns. Of

these, the maximum and minimum values are removed and

then the average is calculated. If R0x70, bits 3:0 are set to

“0” (2 pixels), it is essentially equivalent to disabling the

dark average calculation since the average is equal to “0”

after the maximum and minimum values are removed.

R0x73 is used to indicate the starting column address of

dark pixels which row−noise correction algorithm uses for

calculation. In the MT9V022, dark columns which may be

used are 759–776. R0x73 is used to select the starting

column for the calculation.

One additional note in setting the row−noise correction

777 t(R0x73, bits9 : 0) )number of dark pixels programmed in R0x70, bits 3 : 0 *1(eq. 12)

This is to ensure the column pointer does not go beyond

the limit the MT9V022 can support.

Automatic Gain Control and Automatic Exposure

Control

The integrated AEC/AGC unit is responsible for ensuring

that optimal auto settings of exposure and (analog) gain are

computed and updated every frame.

AEC and AGC can be individually enabled or disabled by

R0xAF. When AEC is disabled (R0xAF[0] = 0), the sensor

uses the manual exposure value in R0x0B. When AGC is

disabled (R0xAF[1] = 0), the sensor uses the manual gain

value in R0x35. See “MT9V022 AEC and AGC Functions,”

for further details.

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MAX. EXPOSURE

(R0xBD)

DESIRED BIN

(desired luminance)

(R0xA5)

MAX. GAIN

(R0x36)

EXP. LPF

(R0xA8)

EXP. SKIP

(R0xA6)

MANUAL EXP.

(R0x08)

AEC ENABLE

(R0Xaf[0])

To exposure

timing control

To analog

gain control

R0xBA

AEC

OUTPUT

R0xBB

AGC OUTPUT

MIN GAIN

MIN EXP

GAIN LPF

(R0xAB)

GAIN SKIP

(R0xA9)

MANUAL GAIN

(R0x35)

AGC ENABLE

(R0xAF[1])

CURRENT BIN

(current luminance

(R0xBC)

AEC

UNIT

HISTOGRAM

GENERATOR

UNIT

AGC

UNIT

Figure 27. Controllable and Observable AEC/AGC Registers

The exposure is measured in row−time by reading

R0xBB. The exposure range is 1 to 2047. The gain is

measured in gain−units by reading R0xBA. The gain range

is 16 to 63 (unity gain = 16 gain−units; multiply by 1/16 to

get the true gain).

When AEC is enabled (R0xAF[0] = 1), the maximum auto

exposure value is limited by R0xBD; minimum auto

exposure is fixed at 1 row.

When AGC is enabled (R0xAF[1] = 1), the maximum

auto gain value is limited by R0x36; minimum auto gain is

fixed to 16 gain−units.

The exposure control measures current scene luminosity

and desired output luminosity by accumulating a histogram

of pixel values while reading out a frame. The desired

exposure and gain are then calculated from this for

subsequent frame.

Pixel Clock Speed

The pixel clock speed is same as the master clock

(SYSCLK) at 26.66 MHz by default. However, when

column binning 2 or 4 (R0x0D, bit 2 or 3) is enabled, the

pixel clock speed is reduced by half and one−fourth of the

master clock speed respectively. See “Read More Options”

and “Column Binning” for additional information.

Hard Rest of Logic

The RC circuit for the MT9V022 uses a 10k∧ resistor and

a 0.1 mF capacitor. The rise time for the RC circuit is 1 ms

maximum.

Soft Rest of Logic

Soft reset of logic is controlled by:

•R0x0C Reset

Bit 0 is used to reset the digital logic of the sensor while

preserving the existing two−wire serial interface

configuration. Furthermore, by asserting the soft reset, the

sensor aborts the current frame it is processing and starts a

new frame. Bit 1 is a shadowed reset control register bit to

explicitly reset the automatic gain and exposure control

feature.

These two bits are self−resetting bits and also return to “0”

during two−wire serial interface reads.

STANDBY Control

The sensor goes into standby mode by setting STANDBY

to HIGH. Once the sensor detects that STANDBY is

asserted, it completes the current frame before disabling the

digital logic, internal clocks, and analog power enable

signal. To release the sensor out from the standby mode,

reset STANDBY back to LOW. The LVDS must be powered

to ensure that the device is in standby mode. See “Appendix

B − Power−On”.

“Reset and Standby Timing” for more information on

standby.

Monitor Mode Control

Monitor mode is controlled by:

•R0x0E Monitor Mode Enable

•R0xC0 Monitor Mode Image Capture Control

The sensor goes into monitor mode when R0x0E bit 0 is

set to HIGH. In this mode, the sensor first captures a

programmable number of frames (R0xC0), then goes into a

sleep period for five minutes. The cycle of sleeping for five

minutes and waking up to capture a number of frames

continues until R0x0E bit 0 is cleared to return to normal

operation.

In some applications when monitor mode is enabled, the

purpose of capturing frames is to calibrate the gain and

exposure of the scene using automatic gain and exposure

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control feature. This feature typically takes less than 10

frames to settle. In case a larger number of frames is needed,

the value of R0xC0 may be increased to capture more

frames.

During the sleep period, none of the analog circuitry and

a very small fraction of digital logic (including a

five−minute timer) is powered. The master clock

(SYSCLK) is therefore always required.

Read More Options

(Also see “Output Data Format” and “Output Data

Timing”.)

Column Flip

By setting bit 5 of R0x0D the readout order of the columns

is reversed, as shown in Figure 28.

Row Flip

By setting bit 4 of R0x0D the readout order of the rows is

reversed, as shown in Figure 29.

Figure 28. Readout of Six Pixels in Normal and Column Flip Output Mode

LINE_VALID

Normal readout

DOUT(9:0

)

Reverse readout

DOUT(9:0

)

P4,1

(9:0) P4,2

(9:0) P4,3

(9:0) P4,4

(9:0) P4,5

(9:0) P4,6

(9:0)

P4,n

(9:0) P4,n−1

(9:0) P4,n−2

(9:0) P4,n−3

(9:0)

P4,n−4

(9:0) P4,n−5

(9:0)

DOUT(9:0)

Figure 29. Readout of Six Rows in Normal and Row Flip Output Mode

LINE_VALID

Normal readout

DOUT(9:0

)

Reverse readout

DOUT(9:0

)

Row4

(9:0) Row5

(9:0) Row6

(9:0) Row7

(9:0) Row8

7(9:0) Row9

(9:0)

Row484

(9:0)

Row483

(9:0)

Row482

(9:0) Row481

(9:0)

Row480

7(9:0) Row479

(9:0)

DOUT(9:0)

Pixel Binning

In addition to windowing mode in which smaller

resolution (CIF, QCIF) is obtained by selecting small

window from the sensor array, the MT9V022 also provides

the ability to show the entire image captured by pixel array

with smaller resolution by pixel binning. Pixel binning is

based on combining signals from adjacent pixels by

averaging. There are two options: binning 2 and binning 4.

When binning 2 is on, 4 pixel signals from 2 adjacent rows

and columns are combined. In binning 4 mode, 16 pixels are

combined from 4 adjacent rows and columns. The image

mode may work in conjunction with image flip. The binning

operation increases SNR but decreases resolution.

Enabling row bin2 and row bin4 improves frame rate by

2x and 4x respectively. The feature of column binning does

not increase the frame rate in less resolution modes.

Row Binning

By setting bit 0 or 1 of R0x0D, only half or one−fourth of

the row set is read out, as shown in figure below. The number

of rows read out is half or one−fourth of what is set in R0x03.

Column Binning

In setting bit 2 or 3 of R0x0D, the pixel data rate is slowed

down by a factor of either two or four, respectively. This is

due to the overhead time in the digital pixel data processing

chain. As a result, the pixel clock speed is also reduced

accordingly.

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Row10

(9:0)

Row4

(9:0) Row5

(9:0) Row6

(9:0) Row7

(9:0) Row8

7(9:0) Row9

(9:0)

LINE_VALID

Normal readout

LINE_VALID

Row Bin 2 readout

LINE_VALID

Row Bin 4 readout

Row11

(9:0)

Row4

(9:0) Row6

(9:0) Row8

(9:0) Row10

(9:0)

Row4

(9:0) Row8

(9:0)

Figure 30. Readout of 8 Pixels in Normal and Row Bin Output Mode

DOUT(9:0)

Figure 31. Readout of 8 Pixels in Normal and Column Bin Output Mode

d1234

(9:0)

LINE_VALID

Normal readout

DOUT(9:0

)

PIXCLK

LINE_VALID

Column Bin 2 readout

DOUT(9:0

)

PIXCLK

LINE_VALID

Column Bin 4 readout

DOUT(9:0

)

PIXCLK

(9:0) D3

(9:0) D4

(9:0) D5

(9:0) D6

(9:0) D7

(9:0)

(9:0) D8

(9:0)

D12

(9:0) D34

(9:0) D56

(9:0) D78

(9:0)

d5678

(9:0)

DOUT(9:0)

Interlaced Readout

The MT9V022 has two interlaced readout options. By

setting R0x07[2:0] = 1, all the even−numbered rows are read

out first, followed by a number of programmable field

blanking (R0xBF, bits 7:0), and then the odd−numbered

rows and finally vertical blanking (minimum is 4 blanking

rows). By setting R0x07[2:0] = 2, only one field is read out;

consequently, the number of rows read out is half what is set

in R0x03. The row start address (R0x02) determines which

field gets read out; if the row start address is even, the even

field is read out; if row start address is odd, the odd field is

read out.

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VALID IMAGE − Even Field

00 00 00 ………… 00 00 00

P4,1 P4,2 P4,3…………P4,n−1 P4,n

P6,0 P6,1 P6,2…………P6,n−1 P6,n

00 00 00 …………………… 00 00 00

00 00 00 ………… 00 00 00

Pm−2,0 Pm−2,2………Pm−2,n−2 Pm−2,n

Pm,2 Pm,2…………Pm,n−1 Pm,n

VALID IMAGE − Odd Field

HORIZONTAL

BLANKING

FIELD BLANKING

VERTICAL BLANKING

P5,1 P5,2 P5,3…………P5,n−1 P5,n

P7,0 P7,1 P7,2…………P7,n−1 P7,n

Pm−3,1 Pm−3,2………Pm−3,n−1 Pm−3,n

Pm,1 Pm,1…………Pm,n−1 Pm,n

00 00 00 ……………………………… 00 00 00

Figure 32. Spatial Illustration of Interlaced Image Readout

When interlaced mode is enabled, the total number of

blanking rows are determined by both field blanking register

(R0xBF) and vertical blanking register (R0x06). The

followings are their equations.

Field Blanking +R0xBF, bits 7 : 0 (eq. 13)

Vertical Blanking +R0x06, bits 8 : 0 *R0xBF, bits 7 : 0 (eq. 14)

With

minimum vertical blanking requirement +4(eq. 15)

Similar to progressive scan, FRAME_VALID is logic

LOW during the valid image row only. Binning should not

be used in conjunction with interlaced mode.

LINE_VALID

By setting bit 2 and 3 of R0x74 the LINE_VALID signal

can get three different output formats. The formats for

reading out four rows and two vertical blanking rows are

shown in Figure 33. In the last format, the LINE_VALID

signal is the XOR between the continuous LINE_VALID

signal and the FRAME_VALID signal.

Default

FRAME_VALID

LINE_VALID

Continuously

FRAME_VALID

XOR

FRAME_VALID

LINE_VALID

Figure 33. Different LINE_VALID Formats

LVDS Serial (Stand−Alone/Stereo) Output

The LVDS interface allows for the streaming of sensor

data serially to a standard off−the− shelf deserializer up to

five meters away from the sensor. The pixels (and controls)

are packeted−12−bit packets for stand−alone mode and

18−bit packets for stereoscopy mode. All serial signalling

(CLK and data) is LVDS. The LVDS serial output could

either be data from a single sensor (stand−alone) or

stream−merged data from two sensors (self and its

stereoscopic slave pair). The appendices describe in detail

the topologies for both stand−alone and stereoscopic modes.

There are two standard deserializers that can be used. One

for a stand−alone sensor stream and the other from a

stereoscopic stream. The deserializer attached to a stand−

alone sensor is able to reproduce the standard parallel output

(8−bit pixel data, LINE_VALID, FRAME_VALID and

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PIXCLK). The deserializer attached to a stereoscopic sensor

is able to reproduce 8−bit pixel data from each sensor (with

embedded LINE_VALID and FRAME_VALID) and

pixel−clk. An additional (simple) piece of logic is required

to extract LINE_VALID and FRAME_VALID from the

8−bit pixel data. Irrespective of the mode

(stereoscopy/stand−alone), LINE_VALID and

FRAME_VALID are always embedded in the pixel data.

In stereoscopic mode, the two sensors run in lock−step,

implying all state machines are in the same state at any given

time. This is ensured by the sensor−pair getting their sys−

clks and sys−resets in the same instance. Configuration

writes through the two−wire serial interface are done in such

a way that both sensors can get their configuration updates

at once. The inter−sensor serial link is designed in such a

way that once the slave PLL locks and the data−dly,

shft−clk−dly and stream−latency−sel are configured, the

master sensor streams good stereo content irrespective of

any variation voltage and/or temperature as long as it is

within specification. The configuration values of data−dly,

shft−clk−dly and stream−latency−sel are either

predetermined from the board−layout or can be empirically

determined by reading back the stereo−error flag. This flag

gets asserted when the two sensor streams are not in sync

when merged. The combo_reg is used for out−of−sync

diagnosis.

Figure 34. Serial Output Format for 6x2 Frame

Internal

PIXCLK

Internal

Parallel

Data

Internal

Line_Valid

Internal

Frame_Valid

External

Serial

Data Out

NOTES: 1. External pixel values of 0, 1, 2, 3, are reserved (they only convey control information). Any

raw pixel of value 0, 1, 2 and 3 will be substituted with 4.

2.The external pixel sequence 1023, 0 1023 is a reserved sequence (conveys control

information). Any raw pixel sequence of 1023, 0, 1023 will be substituted with 1023, 4, 1023.

P42P41 P43 P44 P45 P46 P52 P53 P54 P56

P55

P51

1023 0 1023 1 P41 P42 P43 P44 P45 P46 2 1 P51 P52 P53 P54 P55 P56 3

LVDS Output Format

In stand−alone mode, the packet size is 12 bits (2 frame

bits and 10 payload bits); 10−bit pixels or 8−bit pixels can be

selected. In 8−bit pixel mode (R0xB6[0] = 0), the packet

consists of a start bit, 8−bit pixel data (with sync codes), the

line valid bit, the frame valid bit and the stop bit. For 10−bit

pixel mode (R0xB6[0] = 1), the packet consists of a start bit,

10−bit pixel data, and the stop bit.

Table 7. LVDS PACKET FORMAT IN STAND−ALONE MODE (Stereoscopy Mode Bit De−Asserted)

12 Bit Packet

Use_10−bit_pixels Bit De−Asserted

(8−Bit Mode)

Use_10−bit_pixels Bit Asserted

(10−Bit Mode)

Bit[0] 1’b1(Start bit) 1’b1(Start bit)

Bit[1] PixelData[2] PixelData[0]

Bit[2] PixelData[3] PixelData[1]

Bit[3] PixelData[4] PixelData[2]

Bit[4] PixelData[5] PixelData[3]

Bit[5] PixelData[6] PixelData[4]

Bit[6] PixelData[7] PixelData[5]

Bit[7] PixelData[8] PixelData[6]

Bit[8] PixelData[9] PixelData[7]

Bit[9] Line_Valid PixelData[8]

Bit[10] Frame_Valid PixelData[9]

Bit[11] 1’b0(Stop bit) 1’b0(Stop bit)

In stereoscopic mode (see Figure 47), the packet size is 18

bits (2 frame bits and 16 payload bits). The packet consists

of a start bit, the master pixel byte (with sync codes), the

slave byte (with sync codes), and the stop bit.)

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Table 8. LVDS PACKET FORMAT IN STEREOSCOPY MODE (Stereoscopy Mode Bit Asserted)

18−bit Packet Function

Bit[0] 1’b1 (Start bit)

Bit[1] Master Sensor Pixel Data [2]

Bit[2] Master Sensor Pixel Data [3]

Bit[3] Master Sensor Pixel Data [4]

Bit[4] Master Sensor Pixel Data [5]

Bit[5] Master Sensor Pixel Data [6]

Bit[6] Master Sensor Pixel Data [7]

Bit[7] Master Sensor Pixel Data [8]

Bit[8] Master Sensor Pixel Data [9]

Bit[9] Slave Sensor Pixel Data [2]

Bit[10] Slave Sensor Pixel Data [3]

Bit[11] Slave Sensor Pixel Data [4]

Bit[12] Slave Sensor Pixel Data [5]

Bit[13] Slave Sensor Pixel Data [6]

Bit[14] Slave Sensor Pixel Data [7]

Bit[15] Slave Sensor Pixel Data [8]

Bit[16] Slave Sensor Pixel Data [9]

Bit[17] 1’b0 (Stop bit)

Control signals LINE_VALID and FRAME_VALID can

be reconstructed from their respective preceding and

succeeding flags that are always embedded within the pixel

data in the form of reserved words.

Table 9. RESERVED WORDS IN THE PIXEL DATA STREAM

Pixel Data Reserved Word Flag

0Precedes frame valid assertion

1Precedes line valid assertion

2Succeeds line valid de−assertion

3Succeeds frame valid de−assertion

When LVDS mode is enabled along with column binning

(bin 2 or bin 4, R0x0D[3:2], the packet size remains the same

but the serial pixel data stream repeats itself depending on

whether 2X or 4X binning is set:

•For bin 2, LVDS outputs double the expected data

(pixel 0,0 is output twice in sequence, followed by pixel

0,1 twice, . . .).

•For bin 4, LVDS outputs 4 times the expected data

(pixel 0,0 is output 4 times in sequence followed by

pixel 0,1 times 4, . . .).

The receiving hardware will need to undersample the

output stream getting data either every 2 clocks (bin 2) or

every 4 (bin 4) clocks.

If the sensor provides a pixel whose value is 0,1, 2, or 3

(that is, the same as a reserved word) then the outgoing serial

pixel value is switched to 4.

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ELECTRICAL SPECIFICATIONS

Table 10. DC ELECTRICAL CHARACTERISTICS (VPWR = 3.3 V ± 0.3 V; TA = Ambient = 255°C)

Symbol Definition Condition Minimum

Typi

cal Maximum Unit

VIH Input high voltage VPWR − 0.5 – VPWR + 0.3 V

VIL Input low voltage –0.3 – 0.8 V

IIN Input leakage current No pull−up resistor; VIN = VPWR or

VGND

–15.0 – 15.0 μA

VOH Output high voltage IOH = –4.0mA VPWR −0.7 – – V

VOL Output low voltage IOL = 4.0mA – – 0.3 V

IOH Output high current VOH = VDD − 0.7 –9.0 – – mA

IOL Output low current VOL = 0.7 – – 9.0 mA

VAA Analog power supply Default settings 3.0 3.3 3.6 V

IPWRAAnalog supply current Default settings – 35.0 60.0 mA

VDD Digital power supply Default settings 3.0 3.3 3.6 V

IPWRDDigital supply current Default settings, CLOAD = 10pF – 35.0 60 mA

VAAPIX Pixel array power supply Default settings 3.0 3.3 3.6 V

IPIX Pixel supply current Default settings 0.5 1.4 3.0 mA

VLVDS LVDS power supply Default settings 3.0 3.3 3.6 V

ILVDS LVDS supply current Default settings 11.0 13.0 15.0 mA

IPWRA

Standby

Analog standby supply

current

STDBY = VDD 2 3 4 μA

IPWRD

Standby Clock Off Digital standby supply

current with clock off

STDBY = VDD, CLKIN = 0 MHz 1 2 4 μA

IPWRD

Standby Clock On Digital standby supply

current with clock on

STDBY= VDD, CLKIN = 27 MHz – 1.05 – mA

LVDS Driver DC Specifications

|VOD|Output differential voltage

RLOAD = 100

∧ ± 1%

250 – 400 mV

|DVOD|Change in VOD between

complementary output

states

– – 50 mV

VOS Output offset voltage 1.0 1.2 1.4 mV

DVOS Change in VOS between

complementary output

states

– – 35 mV

IOS Output current when

driver shorted to ground

±10 ±12 mA

IOZ Output current when

driver is tristate

±1±10 μA

LVDS Receiver DC Specifications

VIDTH+Input differential | VGPD| < 925mV –100 – 100 mV

Iin Input current – – ±20 μA

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Table 11. ABSOLUTE MAXIMUM RATINGS

Symbol Parameter Minimum Maximum Unit

VSUPPLY Power supply voltage (all supplies) –0.3 4.5 V

ISUPPLY Total power supply current – 200 mA

IGND Total ground current – 200 mA

VIN DC input voltage –0.3 VDD + 0.3 V

VOUT DC output voltage –0.3 VDD + 0.3 V

TSTG (Note 5) Storage temperature –40 +125 °C

Stresses exceeding those listed in the Maximum Ratings table may damage the device. If any of these limits are exceeded, device functionality

should not be assumed, damage may occur and reliability may be affected.

5. This is a stress rating only, and functional operation of the device at these or any other conditions above those indicated in the operational

sections of this specification is not implied.

Exposure to absolute maximum rating conditions for extended periods may affect reliability.

WARNING: Stresses greater than those listed may cause

permanent damage to the device.

Table 12. AC ELECTRICAL CHARACTERISTICS (VPWR = 3.3 V ± 0.3 V; TA = Ambient = 25°C; Output Load = 10 pF)

Definition Symbol Condition Min Typ Max Unit

SYSCLK Input clock frequency Note 6 13.0 26.6 27.0 MHz

Clock duty cycle 45.0 50.0 55.0 %

tRInput clock rise time 1 2 5 ns

tFInput clock fall time 1 2 5 ns

tPLHPSYSCLK to PIXCLK propa-

gation delay

CLOAD = 10pF 3 7 11 ns

tPD PIXCLK to valid DOUT(9:0)

propagation delay

CLOAD = 10pF –2 0 2 ns

tSD Data setup time 14 16 – ns

tHD Data hold time 14 16 – ns

tPFLR PIXCLK to LINE_VALID

propagation delay

CLOAD = 10pF –2 0 2 ns

tPFLF PIXCLK to FRAME_VALID

propagation delay

CLOAD = 10pF –2 0 2 ns

6. The frequency range specified applies only to the parallel output mode of operation.

Propagation Delays for PIXCLK and Data Out Signals

The pixel clock is inverted and delayed relative to the

master clock. The relative delay from the master clock

(SYSCLK) rising edge to both the pixel clock (PIXCLK)

falling edge and the data output transition is typically 7 ns.

Note that the falling edge of the pixel clock occurs at

approximately the same time as the data output transitions.

See Table 13 for data setup and hold times.

Propagation Delays for FRAME_VALID and

LINE_VALID Signals

The LINE_VALID and FRAME_VALID signals change

on the same rising master clock edge as the data output. The

LINE_VALID goes HIGH on the same rising master clock

edge as the output of the first valid pixel’s data and returns

LOW on the same master clock rising edge as the end of the

output of the last valid pixel’s data.

As shown in the “Output Data Timing”, FRAME_VALID

goes HIGH 143 pixel clocks before the first LINE_VALID

goes HIGH. Ut returns LOW23 pixel clocks after the last

LINE_VALID goes LOW.

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Figure 35. Propagation Delays for PIXCLK and Data Out Signals

DOUT(9:0)

tPLHP

SYSCLK

PIXCLK

tHDSD

tPDPD

DOUT(9:0)

PLHp

Figure 36. Propagation Delays for FRAME_VALID and LINE_VALID Signals

FRAME_VALID

LINE_VALID

FRAME_VALID

LINE_VALID

PIXCLK PIXCLK

tFLR FLF

Performance Specifications

Table 13 summarizes the specification for each

performance parameter.

Table 13. PERFORMANCE SPECIFICATIONS

Parameter Unit Minimum Typical Maximum Test Number

Sensitivity LSB 400 572 745 1

DSNU LSB N/A 2.3 7.0 2

PRNU % N/A 1.3 4.0 3

Dynamic Range dB 52.0 54.4 N/A 4

SNR dB 33.0 37.3 N/A 5

NOTES: All specifications address operation is at TA=25°C (±3°C) and supply voltage = 3.3 V. Image sensor was tested without a lens.

Multiple images were captured and analyzed.

Setup: VDD = VAA = VAAPIX = LVDSVDD = 3.3 V. Testing was done with default frame timing and default register settings, with

the exception of AEC/AGC, row noise correction, and auto black level, which were disabled.

Performance definitions are detailed in the following

sections.

Test 1: Sensitivity

A flat−field light source (90 lux, color temperature

4400K, broadband, w/ IR cut filter) is used as an

illumination source. Signals are measured in LSB on the

sensor output. A series of four frames are captured and

averaged to obtain a scalar sensitivity output code.

Test 2: Dark Signal Non−Uniformity (DSNU)

The image sensor is held in the dark. Analog gain is

changed to the maximum setting of 4X. Signals are

measured in LSB on the sensor output. A series of four

frames are captured and averaged (pixel−by−pixel) into one

average frame. DSNU is calculated as the standard deviation

of this average frame.

Test 3: Photo Response Non−Uniformity (PRNU)

A flat−field light source (90 lux, color temperature

4400K, broadband, with IR cut filter) is used as an

illumination source. Signals are measured in LSB on the

sensor output. Two series of four frames are captured and

averaged (pixel−by−pixel) into one average frame, one

series is captured under illuminated conditions, and one is

captured in the dark.

PRNU is expressed as a percentage relating the standard

deviation of the average frames difference (illuminated

frame - dark frame) to the average illumination level:

PRNU +100

Np@ȍNp

i+1ǒSillumination(i) *Sdark(i)Ǔ2

NpȍNp

i+1(Sillumination(i))

(eq. 16)

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Where Silumination(i) is the signal measured for the i−th

pixel from the average illuminated frame, Sdark(i) is the

signal measured for the i−th pixel from the average dark

frame, and Np is the total number of pixels contained in the

array.

Test 4: Dynamic Range

A temporal noise measurement is made with the image

sensor in the dark and analog gain changed to the maximum

setting of 4X. Signals are measured in LSB on the sensor

output. Two consecutive dark frames are captured.

Temporal noise is calculated as the average pixel value of the

difference frame:

si+ȍNpi+1(S1i *S2i)2

2@Np

Ǹ(eq. 17)

Where S1i is the signal measured for the i−th pixel from the

first frame, S2i is the signal measured for the i−th pixel from

the second frame, and Np is the total number of pixels

contained in the array.

The dynamic range is calculated according to the

following formula:

Dynamic Range +20 @logƪ4 1022

stƫ(eq. 18)

Where st is the temporal noise measured in the dark ar 4X

gain.

Test 5: Signal−to−Noise Ratio

A flat−field light source (90 lux, color temperature 4400

K, broadband, with IR cut filter) is used as an illumination

source. Signals are measured in LSB on the sensor output.

Two consecutive illuminated frames are captured. Temporal

noise is calculated as the average pixel value of the

difference frame (according to the formula shown in Test 4).

The signal−to−noise ratio is calculated as the ratio of the

average signal level to the temporal noise according to the

following formula:

si+ȍNpi+1(S1i *S2i)2

2@Np

Ǹ(eq. 19)

Where dt is the temporal noise measured from the

illuminated frames, S1i is the signal measured for the i−th

pixel from the first frame, and Np is the total number of

pixels contained in the array.

Two−Wire Serial Bus Timing

The two−wire serial bus operation requires certain

minimum master clock cycles between transitions. These

are specified in the following diagrams in master clock

cycles.

Figure 37. Serial Host Interface Start Condition Timing

SCLK

SDATA

Figure 38. Serial Host Interface Stop Condition Timing

NOTE: All timing are in units of master clock cycle.

SCLK

SDATA

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Figure 39. Serial Host Interface Data Timing for WRITE

SCLK

DATA

NOTE: SDATA is driven by an off-chip transmitter.

Figure 40. Serial Host Interface Data Timing for READ

SCLK

DATA

NOTE: SDATA is pulled LOW by the sensor, or allowed to be pulled HIGH by a pull-up resistor off-chip.

Figure 41. Acknowledge Signal Timing After an 8-Bit WRITE to the Sensor

SCLK

Sensor pulls down

DATA pin

SDATA

Figure 42. Acknowledge Signal Timing After an 8-Bit READ from the Sensor

SCLK

Sensor tri−states SDATA pin

(turns off pull down)

DATA

NOTE: After a READ, the master receiver must pull down SDATA to acknowledge receipt of data bits. When read sequence is

complete, the master must generate a “No Acknowledge” by leaving SDATA to float HIGH. On the following cycle,

a start or stop bit may be used.

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TEMPERATURE REFERENCE

The MT9V022 contains a temperature reference circuit

that can be used to measure relative temperatures. Contact

your ON Semiconductor field applications engineer (FAE)

for more information on using this circuit.

350 450 550 650 750 850 950 1050

Wavelength (nm)

Quantum Efficiency (%)

35 Blue

Red

Green (B)

Green (R)

Figure 43. Typical Quantum Efficiency − Color

350 450 550 650 750 850 950 1050

Wavelength (nm)

Quantum Efficiency (%)

Figure 44. Typical Quantum Efficiency − Monochrome

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APPENDIX A − SERIAL CONFIGURATIONS

With the LVDS serial video output, the deserializer can be

up to 8 meters from the sensor. The serial link can save on

the cabling cost of 14 wires (DOUT[9:0], LINE_VALID,

FRAME_VALID, PIXCLK, GND). Instead, just 3 wires (2

serial LVDS, one GND) are sufficient to carry the video

signal.

Configuration of Sensor for Stand − Alone Serial

Output with Internal PLL

In this configuration, the internal PLL generates the

shift−clk (x12). The LVDS pins SER_DATAOUT_P and

SER_DATAOUT_N must be connected to a deserializer

(clocked at approximately the same system clock

frequency).

Figure 45 shows how a standard off−the−shelf deserializer

(National Semiconductor DS92LV1212A) can be used to

retrieve the standard parallel video signals of DOUT(9:0),

LINE_VALID and FRAME_VALID.

Sensor

CLK 26.6 Mhz

Osc.

26.6 Mhz

Osc.

DS92LV1212A

LVDS

SER_DATAOUT

LVDS

SER_DATAIN

LVDS

BYPASS_CLKIN

LVDS

SHIFT_CLKOUT

8 meters (maximum)

LINE_VALID

FRAME_VALID

PIXEL

8−bit configuration shown

Figure 45. Stand−Alone Topology

Typical configuration of the sensor:

1. Power−up sensor.

2. Enable LVDS driver (set R0xB3[4]= 0).

3. De−assert LVDS power−down (set R0xB1[1] = 0.

4. Issue a soft reset (set R0x0C[0] = 1 followed by

R0x0C[0] = 0.

If necessary:

5. Force sync patterns for the deserializer to lock (set

R0xB5[0] = 1).

6. Stop applying sync patterns (set R0xB5[0] = 0).

Configuration of Sensor for Stereoscopic Serial

Output with Internal PPL

In this configuration the internal PLL generates the

shift−clk (x18) in phase with the system−clock. The LVDS

pins SER_DATAOUT_P and SER_DATAOUT_N must be

connected to a deserializer (clocked at approximately the

same system clock frequency).

Figure 46 shows how a standard off−the−shelf deserializer

can be used to retrieve back DOUT(9:2) for both the master

and slave sensors. Additional logic is required to extract out

LINE_VALID and FRAME_VALID embedded within the

pixel data stream.

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SENSOR SENSOR

26.6 MHz

Osc.

DS92LV16

LVDS

SER_DATAOUT

LVDS

SER_DATAIN

LVDS

BYPASS_CLKIN

LVDS

SHIFT_CLKOUT

5 meters (maximum)

PIXEL

FROM

MASTER

PIXEL

FROM

SLAVE

LV and FV are embedded in the data stream

Figure 46. Stereoscopic Topology

SLAVE

MASTER

LVDS

SER_DATAOUT

LVDS

SHIFT_CLKOUT

26.6 MHz

Osc.

LVDS

BYPASS_CLKIN

LVDS

SER_DATAIN

1. PLL in non−bypass mode

2. PLL in x 18 mode (stereoscopy)

Typical configuration of the master and slave sensors:

1. Power up the sensors.

2. Broadcast WRITE to de−assert LVDS

power−down (set R0xB1[1] = 0).

3. Individual WRITE to master sensor putting its

internal PLL into bypass mode (set R0xB1[0] = 1).

4. Broadcast WRITE to both sensors to set the

stereoscopy bit (set R0x07[5] = 1).

5. Make sure all resolution, vertical blanking,

horizontal blanking, window size, and AEC/AGC

configurations are done through broadcast WRITE

to maintain lockstep.

6. Broadcast WRITE to enable LVDS driver (set

R0xB3[4] = 0).

7. Broadcast WRITE to enable LVDS receiver (set

R0xB2[4] = 0).

8. Individual WRITE to master sensor, putting its

internal PLL into bypass mode (set R0xB1[0] = 1).

9. Individual WRITE to slave sensor, enabling its

internal PLL (set R0xB1[0] = 0).

10. Individual WRITE to slave sensor, setting it as a

stereo slave (set R0x07[6] = 1).

11. Individual WRITEs to master sensor to minimize

the inter−sensor skew (set R0xB2[2:0],

R0xB3[2:0], and R0xB4[1:0] appropriately). Use

R0xB7 and R0xB8 to get lockstep feedback from

stereo_error_flag.

12. Broadcast WRITE to issue a soft reset (set

R0x0C[0] = 1 followed by R0x0C[0] = 0).

NOTE: The stereo_error_flag is set if a mismatch has

occurred at a reserved byte (slave and master

sensor’s codes at this reserved byte must match).

If the flag is set, steps 11 and 12 are repeated

until the stereo_error_flag remains cleared.

Broadcast and Individual Writes for Stereoscopic

Topology

In stereoscopic mode, the two sensors are required to run

in lockstep. This implies that control logic in each sensor is

in exactly the same state as its pair on every clock. To ensure

this, all inputs that affect control logic must be identical and

arrive at the same time at each sensor.

These inputs include:

•system clock

•system reset

•two−wire serial interface clk − SCL

•two−wire serial interface data − SDA

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SLAVE

SENSOR

MASTER

SENSOR

CLK

HOST

26.6 MHz

Osc.

CLKS_CTRL_ADR[0] CLKS_CTRL_ADR[0]

SDASCL SDASCL

SCL

SDA

Host launches SCL and SDA on positive

edge of SYSCLK

All system clock lengths (L) must be equal.

SCL and SDA lengths to each sensor (from the host) must also be equal.

Figure 47. Two−Wire Serial Interface Configuration in Stereoscopic Mode

The setup in Figure 47 shows how the two sensors can

maintain lockstep when their configuration registers are

written through the two−wire serial interface. A WRITE to

configuration registers would either be broadcast

(simultaneous WRITES to both sensors) or individual

(WRITE to just one sensor at a time). READs from

configuration registers would be individual (READs from

just one sensor at a time).

One of the two serial interface slave address bits of the

sensor is hardwired. The other is controlled by the host. This

allows the host to perform either a broadcast or a one−to−one

access.

Broadcast WRITES are performed by setting the same

S_CTRL_ADR input bit for both slave and master sensor.

Individual WRITES are performed by setting opposite

S_CTRL_ADR input bit for both slave and master sensor.

Similarly, individual READs are performed by setting

opposite S_CTRL_ADR input bit for both slave and master

sensor.

MT9V022

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APPENDIX B − POWER−ON RESET AND STANDBY TIMING

Reset, Clocks, and Standby

There are no constraints concerning the order in which the

various power supplies are applied; however, the MT9V022

requires reset in order operate properly at power−up. Refer

to Figure 48 for the power−up, reset, and standby sequences.

Figure 48. Power−up, Reset, Clock and Standby Sequence

non−Low−Power Low−Power non−Low−Power

Power

down

Wake

up ActiveStandby

Pre−StandbyActive

Power

MIN 20 SYSCLK cycles

Note 3

RESET #

STANDBY

SYSCLK

MIN 10 SYSCLK cycles

Does not

respond to

serial

interface

when

STANDBY = 1

MIN 10 SYSCLK cycles

DOUT[9:0]

DATA OUTPUT

SCLK, SDATA

Two−Wire Serial I/F

Driven = 0

VDD, VDDLVDS

VAA, VAAPIX

1. All output signals are defined during initial power−up with RESET# held LOW without SYSCLK being active. To properly

reset the rest of the sensor, during initial power−up, assert RESET# (set to LOW state) for at least 750ns after all power

supplies have stabilized and SYSCLK is active (being clocked). Driving RESET# to LOW state does not put the part in

a low power state.

2. Before using two−wire serial interface,wait for 10 SYSCLK rising edges after RESET# is de−asserted.

3. Once the sensor detects that STANDBY has been asserted, it completes the current frame readout before entering

standby mode. The user must supply enough SYSCLKs to allow a complete frame readout. See Table 4, “Frame Time”,

for more information.

4. In standby, all video data and synchronization output signals are High−Z.

5. In standby, the two−wire serial interface is not active.

Standby Assertion Restrictions

STANDBY cannot be asserted at any time. If STANDBY

is asserted during a specific window within the vertical

blanking period, the MT9V022 may enter a permanent

standby state. This window (that is, dead zone) occurs prior

to the beginning of the new frame readout. The permanent

standby state is identified by the absence of the

FRAME_VALID signal on frame readouts. Issuing a

hardware reset (RESET# set to LOW state) will return the

image sensor to default startup conditions.

This dead zone can be avoided by:

1. Asserting STANDBY during the valid frame

readout time (FRAME_VALID is HIGH) and

maintaining STANDBY assertion for a minimum

of one frame period.

2. Asserting STANDBY at the end of valid frame

readout (falling edge of FRAME_VALID) and

maintaining STANDBY assertion for a minimum

of [5 + R0x06] row−times.

When STANDBY is asserted during the vertical blanking

period (FRAME_VALID is LOW), the STANDBY signal

must not change state between [Vertical Blanking Register

(R0x06) − 5] row−times and [Vertical Blanking Register

+ 5] row−times after the falling edge of FRAME_VALID.

MT9V022

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FRAME_VALID

Vertical Blanking Period

(R0x06) row−times

Dead Zone

10 row−times

5 row−times 5 row−times

Figure 49. STANDBY Restricted Location

MT9V022

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