LT3080-1 Parallelable 1.1A Adjustable Single Resistor Low Dropout Regulator Description Features n n n n n n n n n n n n n Internal Ballast Resistor Permits Direct Connection to Power Plane for Higher Current and Heat Spreading Output Current: 1.1A Single Resistor Programs Output Voltage 1% Initial Accuracy of SET Pin Current Output Adjustable to 0V Low Output Noise: 40VRMS (10Hz to 100kHz) Wide Input Voltage Range: 1.2V to 36V Low Dropout Voltage: 350mV <0.001%/ V Line Regulation Minimum Load Current: 0.5mA Stable with 2.2F Minimum Ceramic Output Capacitor Current Limit with Foldback and Overtemperature Protected Available in 8-Lead MSOP and 3mm x 3mm DFN n n n n The LT3080-1 is capable of supplying a wide output voltage range. A reference current through a single resistor programs the output voltage to any level between zero and 36V. The LT3080-1 is stable with 2.2F of ceramic capacitance on the output, not requiring additional ESR as is common with other regulators. Internal protection includes current limiting and thermal limiting. The LT3080-1 regulator is offered in the 8-lead MSOP (with an Exposed Pad for better thermal characteristics) and 3mm x 3mm DFN packages. Applications n The LT(R)3080-1 is a 1.1A low dropout linear regulator that incorporates an internal ballast resistor to allow direct paralleling of devices without the need for PC board trace resistors. The internal ballast resistor allows multiple devices to be paralleled directly on a surface mount board for higher output current and power dissipation while keeping board layout simple and easy. The device brings out the collector of the pass transistor to allow low dropout operation--down to 350mV--when used with multiple input supplies. High Current All Surface Mount Supply High Efficiency Linear Regulator Post Regulator for Switching Supplies Low Parts Count Variable Voltage Supply Low Output Voltage Power Supplies L, LT, LTC, LTM, Linear Technology and the Linear logo are registered trademarks and VLDO and ThinSOT are trademarks of Linear Technology Corporation. All other trademarks are the property of their respective owners. Typical Application Paralleling Regulators IN Offset Voltage Distribution LT3080-1 N = 13250 VCONTROL + - 25m OUT* 25m OUT* SET IN VIN 4.8V TO 28V LT3080-1 VCONTROL + - 1F SET VOUT 3.3V 2.2A 10F 165k 30801 TA01 -2 *OUTPUTS CAN BE DIRECTLY MOUNTED TO POWER PLANE 0 -1 1 VOS DISTRIBUTION (mV) 2 30801 TA01b 30801fb 1 LT3080-1 Absolute Maximum Ratings (Note 1) All Voltages Relative to VOUT VCONTROL Pin Voltage.....................................40V, -0.3V IN Pin Voltage.................................................40V, -0.3V SET Pin Current (Note 7)...................................... 10mA SET Pin Voltage (Relative to OUT)..........................0.3V Output Short-Circuit Duration........................... Indefinite Operating Junction Temperature Range (Notes 2, 10) E-, I-grades......................................... -40C to 125C Storage Temperature Range...................-65C to 150C Lead Temperature (Soldering, 10 sec) MS8E Package Only........................................... 300C Pin Configuration TOP VIEW OUT 1 OUT 2 OUT 3 9 OUT SET 4 8 IN 7 IN 6 NC 5 VCONTROL TOP VIEW OUT OUT OUT SET 1 2 3 4 9 OUT 8 7 6 5 IN IN NC VCONTROL MS8E PACKAGE 8-LEAD PLASTIC MSOP DD PACKAGE 8-LEAD (3mm x 3mm) PLASTIC DFN TJMAX = 125C, JA = 64C/W, JC = 3C/W EXPOSED PAD (PIN 9) IS OUT, MUST BE SOLDERED TO PCB TJMAX = 125C, JA = 60C/W, JC = 10C/W EXPOSED PAD (PIN 9) IS OUT, MUST BE SOLDERED TO PCB Order Information LEAD FREE FINISH TAPE AND REEL PART MARKING* PACKAGE DESCRIPTION TEMPERATURE RANGE LT3080EDD-1#PBF LT3080EDD-1#TRPBF LDPM 8-Lead (3mm x 3mm) Plastic DFN -40C to 125C LT3080IDD-1#PBF LT3080IDD-1#TRPBF LDPM 8-Lead (3mm x 3mm) Plastic DFN -40C to 125C LT3080EMS8E-1#PBF LT3080EMS8E-1#TRPBF LTDPN 8-Lead Plastic MSOP -40C to 125C LT3080IMS8E-1#PBF LT3080IMS8E-1#TRPBF LTDPN 8-Lead Plastic MSOP -40C to 125C LEAD BASED FINISH TAPE AND REEL PART MARKING* PACKAGE DESCRIPTION TEMPERATURE RANGE LT3080EDD-1 LT3080EDD-1#TR LDPM 8-Lead (3mm x 3mm) Plastic DFN -40C to 125C LT3080IDD-1 LT3080IDD-1#TR LDPM 8-Lead (3mm x 3mm) Plastic DFN -40C to 125C LT3080EMS8E-1 LT3080EMS8E-1#TR LTDPN 8-Lead Plastic MSOP -40C to 125C LT3080IMS8E-1 LT3080IMS8E-1#TR LTDPN 8-Lead Plastic MSOP -40C to 125C Consult LTC Marketing for parts specified with wider operating temperature ranges. *The temperature grade is identified by a label on the shipping container. For more information on lead free part marking, go to: http://www.linear.com/leadfree/ For more information on tape and reel specifications, go to: http://www.linear.com/tapeandreel/ 30801fb 2 LT3080-1 Electrical Characteristics The denotes the specifications which apply over the full operating temperature range, otherwise specifications are at TA = 25C. PARAMETER CONDITIONS MIN TYP MAX UNITS l 9.90 9.80 10 10 10.10 10.20 A A -2 -3.5 2 3.5 mV mV 34 48 nA mV mV Output Offset Voltage (VOUT - VSET) VOS VIN = 1V, VCONTROL = 2.0V, ILOAD = 1mA, TJ = 25C VIN 1V, VCONTROL 2.0V, 1mA ILOAD 1.1A (Note 9) VIN = 1V, VCONTROL = 2V, IOUT = 1mA Load Regulation ISET VOS VOS ILOAD = 1mA to 1.1A ILOAD = 1mA to 1.1A (Note 8) ILOAD = 1mA to 1.1A (Note 8) Line Regulation (Note 9) ISET VOS VIN = 1V to 22V, VCONTROL=1V to 22V, ILOAD=1mA VIN = 1V to 22V, VCONTROL=1V to 22V, ILOAD=1mA 0.1 0.003 0.5 nA/V mV/V Minimum Load Current (Notes 3, 9) VIN = VCONTROL = 10V VIN = VCONTROL = 22V l 300 500 1 A mA VCONTROL Dropout Voltage (Note 4) ILOAD = 100mA ILOAD = 1.1A l 1.2 1.35 1.6 V V VIN Dropout Voltage (Note 4) ILOAD = 100mA ILOAD = 1.1A l l 100 350 200 500 mV mV CONTROL Pin Current (Note 5) ILOAD = 100mA ILOAD = 1.1A l l 4 17 6 30 mA mA Current Limit (Note 9) VIN = 5V, VCONTROL = 5V, VSET = 0V, VOUT = -0.1V l Error Amplifier RMS Output Noise (Note 6) ILOAD = 1.1A, 10Hz f 100kHz, COUT = 10F, CSET = 0.1F SET Pin Current ISET -0.1 27.5 1.1 1.4 A 40 VRMS Reference Current RMS Output Noise (Note 6) 10Hz f 100kHz 1 nARMS Ripple Rejection f = 120Hz, VRIPPLE = 0.5VP-P, ILOAD = 0.2A, CSET = 0.1F, COUT = 2.2F f = 10kHz f = 1MHz 75 55 20 dB dB dB Thermal Regulation, ISET 10ms Pulse Note 1: Stresses beyond those listed under Absolute Maximum Ratings may cause permanent damage to the device. Exposure to any Absolute Maximum Rating condition for extended periods may affect device reliability and lifetime. Note 2: Unless otherwise specified, all voltages are with respect to VOUT. The LT3080-1 is tested and specified under pulse load conditions such that TJ TA. The LT3080E-1 is tested at TA = 25C. Performance of the LT3080E-1 over the full -40C and 125C operating temperature range is assured by design, characterization, and correlation with statistical process controls. The LT3080I-1 is guaranteed over the full -40C to 125C operating junction temperature range. Note 3: Minimum load current is equivalent to the quiescent current of the part. Since all quiescent and drive current is delivered to the output of the part, the minimum load current is the minimum current required to maintain regulation. Note 4: For the LT3080-1, dropout is caused by either minimum control voltage (VCONTROL) or minimum input voltage (VIN). Both parameters are specified with respect to the output voltage. The specifications represent the minimum input-to-output differential voltage required to maintain regulation. Note 5: The CONTROL pin current is the drive current required for the output transistor. This current will track output current with roughly a 1:60 ratio. The minimum value is equal to the quiescent current of the device. 0.003 %/W Note 6: Output noise is lowered by adding a small capacitor across the voltage setting resistor. Adding this capacitor bypasses the voltage setting resistor shot noise and reference current noise; output noise is then equal to error amplifier noise (see the Applications Information section). Note 7: SET pin is clamped to the output with diodes. These diodes only carry current under transient overloads. Note 8: Load regulation is Kelvin sensed at the package. Note 9: Current limit may decrease to zero at input-to-output differential voltages (VIN - VOUT) greater than 22V. Operation at voltages for both IN and VCONTROL is allowed up to a maximum of 36V as long as the difference between input and output voltage is below the specified differential (VIN - VOUT) voltage. Line and load regulation specifications are not applicable when the device is in current limit. Note 10: This IC includes over-temperature protection that is intended to protect the device during momentary overload conditions. Junction temperature will exceed the maximum operating junction temperature when over-temperature protection is active. Continuous operation above the specified maximum operating junction temperature may impair device reliability. 30801fb 3 LT3080-1 Typical Performance Characteristics Set Pin Current Offset Voltage (VOUT - VSET) Set Pin Current Distribution 10.20 2.0 N = 13792 10.10 1.0 OFFSET VOLTAGE (mV) 1.5 SET PIN CURRENT (A) 10.15 10.05 10.00 9.95 9.90 0.5 0 -0.5 -1.0 -1.5 9.85 9.80 -50 -25 0 9.80 25 50 75 100 125 150 TEMPERATURE (C) -2.0 -50 -25 10.00 10.20 9.90 10.10 SET PIN CURRENT DISTRIBUTION (A) Offset Voltage Distribution Offset Voltage 0 -5 0.50 OFFSET VOLTAGE (mV) OFFSET VOLTAGE (mV) 5 ILOAD = 1mA 0.75 0.25 0 -0.25 -0.50 -1.00 80 ILOAD = 1mA TO 1.1A VIN - VOUT = 2V 70 -10 60 -15 50 -20 -25 -30 40 CHANGE IN OFFSET VOLTAGE 30 20 (VOUT - VSET) -35 -40 -45 10 0 CHANGE IN REFERENCE CURRENT -50 -50 -25 0 -10 -20 25 50 75 100 125 150 TEMPERATURE (C) 30801 G07 0 6 12 24 30 18 INPUT-TO-OUTPUT VOLTAGE (V) 36* 0.4 0.8 0.6 LOAD CURRENT (A) 1.2 1.0 30801 G06 400 VIN, CONTROL - VOUT = 36V* 0.5 0.3 0.2 Dropout Voltage (Minimum IN Voltage) 0.7 0.4 0 30801 G05 0.8 0.6 TJ = 125C -30 Minimum Load Current MINIMUM LOAD CURRENT (mA) CHANGE IN OFFSET VOLTAGE WITH LOAD (mV) 0 CHANGE IN REFERENCE CURRENT WITH LOAD (nA) Load Regulation -20 -25 -40 *SEE NOTE 9 IN ELECTRICAL CHARACTERISTICS TABLE 30801 G04 TJ = 25C -15 -45 MINIMUM IN VOLTAGE (VIN - VOUT) (mV) 2 -10 -35 -0.75 0 -1 1 VOS DISTRIBUTION (mV) 25 50 75 100 125 150 TEMPERATURE (C) 30801 G03 Offset Voltage 1.00 N = 13250 -2 0 30801 G02 30801 G01 -5 IL = 1mA VIN, CONTROL - VOUT = 1.5V 0.2 0.1 0 -50 -25 0 25 50 75 100 125 150 TEMPERATURE (C) *SEE NOTE 9 IN ELECTRICAL CHARACTERISTICS TABLE 30801 G08 350 TJ = 125C 300 250 TJ = 25C 200 150 100 50 0 0 0.2 0.4 0.8 0.6 OUTPUT CURRENT (A) 1.0 1.2 30801 G09 30801fb 4 LT3080-1 ILOAD = 1.1A 300 250 ILOAD = 500mA 150 100 ILOAD = 100mA 50 0 -50 -25 0 25 50 75 100 125 150 TEMPERATURE (C) 1.4 1.2 TJ = 125C 1.0 TJ = 25C 0.8 0.6 0.4 0.2 0 0 0.2 0.4 0.8 0.6 OUTPUT CURRENT (A) Current Limit 1.4 1.2 1.2 1.0 0.8 0.6 1.0 0.6 0 25 50 75 100 125 150 TEMPERATURE (C) 100 50 OUTPUT VOLTAGE DEVIATION (mV) 75 0 -50 -100 1.2 0.6 0.3 0 5 10 15 20 25 30 35 40 45 50 TIME (s) 30801 G16 6 12 24 30 18 INPUT-TO-OUTPUT DIFFERENTIAL (V) 0.6 0.4 0.2 0 -50 -25 0 25 50 75 100 125 150 TEMPERATURE (C) 60 36* 20 0 COUT = 10F CERAMIC -20 0 VOUT = 1.5V ILOAD = 10mA COUT = 2.2F CERAMIC CSET = 0.1F CERAMIC -50 5 4 3 0 COUT = 2.2F CERAMIC 400 300 200 100 0 0 5 10 15 20 25 30 35 40 45 50 TIME (s) 30801 G15 Turn-On Response -25 2 VOUT = 1.5V CSET = 0.1F VIN = VCONTROL = 3V 40 30801 G14 25 6 IN/CONTROL VOLTAGE (V) VIN = VCONTROL = 3V VOUT = 1.5V COUT = 10F CERAMIC CSET = 0.1F ILOAD = 1mA 0.8 Line Transient Response Load Transient Response 50 0 *SEE NOTE 9 IN ELECTRICAL CHARACTERISTICS TABLE 150 0.9 1.0 -40 0.8 30801 G13 OUTPUT VOLTAGE DEVIATION (mV) TJ = 25C 0.2 VIN = 7V VOUT = 0V 0 1.2 Load Transient Response 0.4 0.4 0 -50 -25 ILOAD = 1.1A 1.4 30801 G12 LOAD CURRENT (mA) CURRENT LIMIT (A) CURRENT LIMIT (A) 1.4 0.2 1.6 Current Limit 1.6 1.6 LOAD CURRENT (A) 1.2 Dropout Voltage (Minimum VCONTROL Pin Voltage) 30801 G11 30801 G10 0 1.0 OUTPUT VOLTAGE DEVIATION (mV) 200 TJ = -50C 10 20 30 40 50 60 70 80 90 100 TIME (s) 30801 G17 INPUT VOLTAGE (V) 350 1.6 5 4 3 2 1 0 OUTPUT VOLTAGE (V) MINIMUM IN VOLTAGE (VIN - VOUT) (mV) 400 Dropout Voltage (Minimum VCONTROL Pin Voltage) MINIMUM CONTROL VOLTAGE (VCONTROL - VOUT) (V) Dropout Voltage (Minimum IN Voltage) MINIMUM CONTROL VOLTAGE (VCONTROL - VOUT) (V) Typical Performance Characteristics 2.0 COUT = 2.2F CERAMIC 1.5 1.0 RSET = 100k CSET = 0 RLOAD = 1 0.5 0 0 1 2 3 4 5 6 TIME (s) 7 8 9 10 30801 G18 30801fb 5 LT3080-1 Typical Performance Characteristics VCONTROL Pin Current 30 CONTROL PIN CURRENT (mA) CONTROL PIN CURRENT (mA) ILOAD = 1.1A DEVICE IN CURRENT LIMIT 15 10 5 0.8 VCONTROL - VOUT = 2V VIN - VOUT = 1V 25 20 TJ = -50C 15 TJ = 25C 10 TJ = 125C 5 30 12 18 24 6 INPUT-TO-OUTPUT DIFFERENTIAL (V) *SEE NOTE 9 IN ELECTRICAL CHARACTERISTICS TABLE 0 36* 0 RIPPLE REJECTION (dB) ILOAD = 100mA ILOAD = 1.1A 60 50 40 30 0 100 1k 10k FREQUENCY (Hz) 100k VIN = 10V 0.3 VIN = 5V 0.2 0 1.2 0 1k RTEST () Ripple Rejection - Dual Supply IN Pin 100 90 80 70 1M ILOAD = 1.1A ILOAD = 100mA 60 50 40 30 0 2k 30801 G21 80 10 COUT = 2.2F CERAMIC 10 0.4 90 20 20 10 1.0 100 RIPPLE = 50mVP-P 70 VIN = 20V 0.5 Ripple Rejection - Dual Supply VCONTROL Pin VIN = VCONTROL = VOUT (NOMINAL) + 2V 80 VOUT RTEST 30801 G20 RIPPLE REJECTION (dB) 90 0.4 0.6 0.8 LOAD CURRENT (A) 30801 G19 Ripple Rejection - Single Supply 100 0.2 RIPPLE REJECTION (dB) 0 VIN 0.6 0.1 ILOAD = 1mA 0 SET PIN = 0V 0.7 OUTPUT VOLTAGE (V) 25 20 Residual Output Voltage with Less Than Minimum Load VCONTROL Pin Current VIN = VOUT (NOMINAL) + 1V VCONTROL = VOUT (NOMINAL) +2V COUT = 2.2F CERAMIC RIPPLE = 50mVP-P 10 100 1k 10k FREQUENCY (Hz) 100k 1M 70 60 50 40 VIN = VOUT (NOMINAL) + 1V VCONTROL = VOUT (NOMINAL) +2V 30 RIPPLE = 50mVP-P 20 10 COUT = 2.2F CERAMIC ILOAD = 1.1A 0 10 100 1k 10k 100k FREQUENCY (Hz) 30801 G24 30801 G23 30801 G22 Ripple Rejection (120Hz) 1M Noise Spectral Density 80 10k 1k 1k 100 79 ERROR AMPLIFIER NOISE SPECTRAL DENSITY (nV/Hz) RIPPLE REJECTION (dB) 77 76 75 74 73 72 71 SINGLE SUPPLY OPERATION VIN = VOUT(NOMINAL) + 2V RIPPLE = 500mVP-P, f=120Hz ILOAD = 1.1A CSET = 0.1F, COUT = 2.2F 70 -50 -25 0 25 50 75 100 125 150 TEMPERATURE (C) 30801 G25 100 10 10 1.0 1 10 100 1k 10k FREQUENCY (Hz) REFERENCE CURRENT NOISE SPECTRAL DENSITY (pA/ Hz) 78 0.1 100k 30801 G26 30801fb 6 LT3080-1 Typical Performance Characteristics Error Amplifier Gain and Phase Output Voltage Noise 20 300 15 250 200 10 IL = 1.1A VOUT = 1V RSET = 100k CSET = O.1F COUT = 10F ILOAD = 1.1A TIME 1ms/DIV 30801 G27 GAIN (dB) 5 150 100 0 IL = 100mA -5 50 IL = 1.1A -10 -15 0 -50 IL = 100mA -20 -100 -150 -25 -30 10 PHASE (DEGREES) VOUT 100V/DIV 100 1k 10k FREQUENCY (Hz) 100k -200 1M 30801 G28 Pin Functions (DD/MS8E) VCONTROL (Pin 5/Pin 5): This pin is the supply pin for the control circuitry of the device. The current flow into this pin is about 1.7% of the output current. For the device to regulate, this voltage must be more than 1.2V to 1.35V greater than the output voltage (see Dropout specifications). IN (Pins 7, 8/Pins 7, 8): This is the collector to the power device of the LT3080-1. The output load current is supplied through this pin. For the device to regulate, the voltage at this pin must be more than 0.1V to 0.5V greater than the output voltage (see Dropout specifications). NC (Pin 6/Pin 6): No Connection. No Connect pins have no connection to internal circuitry and may be tied to VIN , VCONTROL, VOUT , GND, or floated. OUT (Pins 1-3/Pins 1-3): This is the power output of the device. There must be a minimum load current of 1mA or the output may not regulate. SET (Pin 4/Pin 4): This pin is the input to the error amplifier and the regulation set point for the device. A fixed current of 10A flows out of this pin through a single external resistor, which programs the output voltage of the device. Output voltage range is zero to the absolute maximum rated output voltage. Transient performance can be improved by adding a small capacitor from the SET pin to ground. Exposed Pad (Pin 9/Pin 9): OUT on MS8E and DFN packages. 30801fb 7 LT3080-1 Block Diagram IN VCONTROL 10A + - 25m 30801 BD SET OUT Applications Information The LT3080-1 regulator is easy to use and has all the protection features expected in high performance regulators. Included are short-circuit protection and safe operating area protection, as well as thermal shutdown. The LT3080-1 is especially well suited to applications needing multiple rails. The new architecture adjusts down to zero with a single resistor handling modern low voltage digital IC's as well as allowing easy parallel operation and thermal management without heat sinks. Adjusting to "zero" output allows shutting off the powered circuitry and when the input is pre-regulated--such as a 5V or 3.3V input supply--external resistors can help spread the heat. on the positive input. Older adjustable regulators, such as the LT1086 have a change in loop gain with output voltage as well as bandwidth changes when the adjustment pin is bypassed to ground. For the LT3080-1, the loop gain is unchanged by changing the output voltage or bypassing. Output regulation is not fixed at a percentage of the output voltage but is a fixed fraction of millivolts. Use of a true current source allows all the gain in the buffer amplifier to provide regulation and none of that gain is needed to amplify up the reference to a higher output voltage. A precision "0" TC 10A internal current source is connected to the non-inverting input of a power operational amplifier. The power operational amplifier provides a low impedance buffered output to the voltage on the noninverting input. A single resistor from the non-inverting input to ground sets the output voltage and if this resistor is set to zero, zero output results. As can be seen, any output voltage can be obtained from zero up to the maximum defined by the input power supply. The LT3080-1 also incorporates an internal ballast resistor to allow for direct paralleling of devices without the need for PC board trace resistors or sense resistors. This internal ballast resistor allows multiple devices to be paralleled directly on a surface mount board for higher output current and higher power dissipation while keeping board layout simple and easy. It is not difficult to add more regulators for higher output current; inputs of devices are all tied together, outputs of all devices are tied directly together, and SET pins of all devices are tied directly together. Because of the internal ballast resistor, devices automatically share the load and the power dissipation. What is not so obvious from this architecture are the benefits of using a true internal current source as the reference as opposed to a bootstrapped reference in older regulators. A true current source allows the regulator to have gain and frequency response independent of the impedance The LT3080-1 has the collector of the output transistor connected to a separate pin from the control input. Since the dropout on the collector (IN pin) is only 300mV, two supplies can be used to power the LT3080-1 to reduce dissipation: a higher voltage supply for the control circuitry 30801fb 8 LT3080-1 Applications Information probably be required. Surface coating may be necessary to provide a moisture barrier in high humidity environments. LT3080-1 IN VCONTROL + VIN + + - VCONTROL 25m OUT SET RSET VOUT COUT CSET 30801 F01 Figure 1. Basic Adjustable Regulator and a lower voltage supply for the collector. This increases efficiency and reduces dissipation. To further spread the heat, a resistor can be inserted in series with the collector to move some of the heat out of the IC and spread it on the PC board. The LT3080-1 can be operated in two modes. Three terminal mode has the control pin connected to the power input pin which gives a limitation of 1.35V dropout. Alternatively, the "control" pin can be tied to a higher voltage and the power IN pin to a lower voltage giving 300mV dropout on the IN pin and minimizing the power dissipation. This allows for a 1.1A supply regulating from 2.5VIN to 1.8VOUT or 1.8VIN to 1.2VOUT with low dissipation. Output Voltage The LT3080-1 generates a 10A reference current that flows out of the SET pin. Connecting a resistor from SET to ground generates a voltage that becomes the reference point for the error amplifier (see Figure 1). The reference voltage is a straight multiplication of the SET pin current and the value of the resistor. Any voltage can be generated and there is no minimum output voltage for the regulator. A minimum load current of 1mA is required to maintain regulation regardless of output voltage. For true zero voltage output operation, this 1mA load current must be returned to a negative supply voltage. With the low level current used to generate the reference voltage, leakage paths to or from the SET pin can create errors in the reference and output voltages. High quality insulation should be used (e.g., Teflon, Kel-F); cleaning of all insulating surfaces to remove fluxes and other residues will Board leakage can be minimized by encircling the SET pin and circuitry with a guard ring operated at a potential close to itself; the guard ring should be tied to the OUT pin. Guarding both sides of the circuit board is required. Bulk leakage reduction depends on the guard ring width. Ten nanoamperes of leakage into or out of the SET pin and associated circuitry creates a 0.1% error in the reference voltage. Leakages of this magnitude, coupled with other sources of leakage, can cause significant offset voltage and reference drift, especially over the possible operating temperature range. If guardring techniques are used, this bootstraps any stray capacitance at the SET pin. Since the SET pin is a high impedance node, unwanted signals may couple into the SET pin and cause erratic behavior. This will be most noticeable when operating with minimum output capacitors at full load current. The easiest way to remedy this is to bypass the SET pin with a small amount of capacitance from SET to ground, 10pF to 20pF is sufficient. Stability and Output Capacitance The LT3080-1 requires an output capacitor for stability. It is designed to be stable with most low ESR capacitors (typically ceramic, tantalum or low ESR electrolytic). A minimum output capacitor of 2.2F with an ESR of 0.5 or less is recommended to prevent oscillations. Larger values of output capacitance decrease peak deviations and provide improved transient response for larger load current changes. Bypass capacitors, used to decouple individual components powered by the LT3080-1, increase the effective output capacitor value. For improvement in transient performance, place a capacitor across the voltage setting resistor. Capacitors up to 1F can be used. This bypass capacitor reduces system noise as well, but start-up time is proportional to the time constant of the voltage setting resistor (RSET in Figure 1) and SET pin bypass capacitor. Extra consideration must be given to the use of ceramic capacitors. Ceramic capacitors are manufactured with a variety of dielectrics, each with different behavior across 30801fb 9 LT3080-1 Applications Information temperature and applied voltage. The most common dielectrics used are specified with EIA temperature characteristic codes of Z5U, Y5V, X5R and X7R. The Z5U and Y5V dielectrics are good for providing high capacitances in a small package, but they tend to have strong voltage and temperature coefficients as shown in Figures 2 and 3. When used with a 5V regulator, a 16V 10F Y5V capacitor can exhibit an effective value as low as 1F to 2F for the DC bias voltage applied and over the operating temperature range. The X5R and X7R dielectrics result in more stable characteristics and are more suitable for use as the output capacitor. The X7R type has better stability across temperature, while the X5R is less expensive and is available in higher values. Care still must be exercised when using X5R and X7R capacitors; the X5R and X7R codes only specify operating temperature range and maximum capacitance change over temperature. Capacitance change due to DC bias with X5R and X7R capacitors is better than Y5V and Z5U capacitors, but can still be significant enough 20 BOTH CAPACITORS ARE 16V, 1210 CASE SIZE, 10F CHANGE IN VALUE (%) 0 X5R -40 Y5V -80 -100 0 2 4 14 8 6 10 12 DC BIAS VOLTAGE (V) Voltage and temperature coefficients are not the only sources of problems. Some ceramic capacitors have a piezoelectric response. A piezoelectric device generates voltage across its terminals due to mechanical stress, similar to the way a piezoelectric microphone works. For a ceramic capacitor the stress can be induced by vibrations in the system or thermal transients. Paralleling Devices LT3080-1's may be directly paralleled to obtain higher output current. The SET pins are tied together and the IN pins are tied together. This is the same whether it's in three terminal mode or has separate input supplies. The outputs are connected in common; the internal ballast resistor equalizes the currents. The worst-case offset between the SET pin and the output of only 2 millivolts allows very small ballast resistors to be used. As shown in Figure 4, the two devices have internal ballast resistors, which at full output current gives better than 90 percent equalized sharing of the current. The internal resistance of 25 milliohms (per device) only adds about 25 millivolts of output regulation drop at an -20 -60 to drop capacitor values below appropriate levels. Capacitor DC bias characteristics tend to improve as component case size increases, but expected capacitance at operating voltage should be verified. VIN 16 LT3080-1 VCONTROL 30801 F02 + - Figure 2. Ceramic Capacitor DC Bias Characteristics 40 CHANGE IN VALUE (%) OUT 25m OUT SET 20 VIN 4.8V TO 28V X5R 0 VIN LT3080-1 VCONTROL -20 - 40 + - 1F Y5V - 60 - 80 SET BOTH CAPACITORS ARE 16V, 1210 CASE SIZE, 10F -100 -50 -25 50 25 75 0 TEMPERATURE (C) VOUT 3.3V 2.2A 10F 165k 100 125 30801 F04 3080 F03 Figure 3. Ceramic Capacitor Temperature Characteristics 10 25m Figure 4. Parallel Devices 30801fb LT3080-1 Applications Information output of 2A. At low output voltage, 1V, this adds 2.5% regulation. The output can be set 19mV high for lower absolute error 1.3%. Of course, more than two LT3080-1's can be paralleled for even higher output current. They are spread out on the PC board, spreading the heat. Input resistors can further spread the heat if the input-to-output difference is high. Thermal Performance In this example, two LT3080-1 3mm x 3mm DFN devices are mounted on a 1oz copper 4-layer PC board. They are placed approximately 1.5 inches apart and the board is mounted vertically for convection cooling. Two tests were set up to measure the cooling performance and current sharing of these devices. The power is then increased with 1.7V across each device. This gives 1.7 watts dissipation in each device and a device temperature of about 90C, about 65C above ambient as shown in Figure 6. Again, the temperature matching between the devices is within 2C, showing excellent tracking between the devices. The board temperature has reached approximately 40C within about 0.75 inches of each device. While 90C is an acceptable operating temperature for these devices, this is in 25C ambient. For higher ambients, the temperature must be controlled to prevent device temperature from exceeding 125C. A three meter per second airflow across the devices will decrease the device temperature about 20C providing a margin for higher operating ambient temperatures. The first test was done with approximately 0.7V inputto-output and 1A per device. This gave a 700 milliwatt dissipation in each device and a 2A output current. The temperature rise above ambient is approximately 28C and both devices were within plus or minus 1C. Both the thermal and electrical sharing of these devices is excellent. The thermograph in Figure 5 shows the temperature distribution between these devices and the PC board reaches ambient temperature within about a half an inch from the devices. Both at low power and relatively high power levels devices can be paralleled for higher output current. Current sharing and thermal sharing is excellent, showing that acceptable operation can be had while keeping the peak temperatures below excessive operating temperatures on a board. This technique allows higher operating current linear regulation to be used in systems where it could never be used before. Figure 5. Temperature Rise at 700mW Dissipation Figure 6. Temperature Rise at 1.7W Dissipation 30801fb 11 LT3080-1 Applications Information Quieting the Noise The LT3080-1 offers numerous advantages when it comes to dealing with noise. There are several sources of noise in a linear regulator. The most critical noise source for any LDO is the reference; from there, the noise contribution from the error amplifier must be considered, and the gain created by using a resistor divider cannot be forgotten. Traditional low noise regulators bring the voltage reference out to an external pin (usually through a large value resistor) to allow for bypassing and noise reduction of reference noise. The LT3080-1 does not use a traditional voltage reference like other linear regulators, but instead uses a reference current. That current operates with typical noise current levels of 3.2pA/Hz (1nARMS over the 10Hz to 100kHz bandwidth). The voltage noise of this is equal to the noise current multiplied by the resistor value. The resistor generates spot noise equal to 4kTR (k = Boltzmann's constant, 1.38 * 10-23 J/K, and T is absolute temperature) which is RMS summed with the reference current noise. To lower reference noise, the voltage setting resistor may be bypassed with a capacitor, though this causes start-up time to increase as a factor of the RC time constant. The LT3080-1 uses a unity-gain follower from the SET pin to drive the output, and there is no requirement to use a resistor to set the output voltage. Use a high accuracy voltage reference placed at the SET pin to remove the errors in output voltage due to reference current tolerance and resistor tolerance. Active driving of the SET pin is acceptable; the limitations are the creativity and ingenuity of the circuit designer. One problem that a normal linear regulator sees with reference voltage noise is that noise is gained up along with the output when using a resistor divider to operate at levels higher than the normal reference voltage. With the LT3080-1, the unity-gain follower presents no gain whatsoever from the SET pin to the output, so noise figures do not increase accordingly. Error amplifier noise is typically 125nV/Hz (40VRMS over the 10Hz to 100kHz bandwidth); this is another factor that is RMS summed in to give a final noise figure for the regulator. Curves in the Typical Performance Characteristics show noise spectral density and peak-to-peak noise characteristics for both the reference current and error amplifier over the 10Hz to 100kHz bandwidth. Overload Recovery Like many IC power regulators, the LT3080-1 has safe operating area (SOA) protection. The SOA protection decreases current limit as the input-to-output voltage increases and keeps the power dissipation at safe levels for all values of input-to-output voltage. The LT3080-1 provides some output current at all values of input-to-output voltage up to the device breakdown. See the Current Limit curve in the Typical Performance Characteristics section. When power is first turned on, the input voltage rises and the output follows the input, allowing the regulator to start into very heavy loads. During start-up, as the input voltage is rising, the input-to-output voltage differential is small, allowing the regulator to supply large output currents. With a high input voltage, a problem can occur wherein removal of an output short will not allow the output voltage to recover. Other regulators, such as the LT1085 and LT1764A, also exhibit this phenomenon so it is not unique to the LT3080-1. The problem occurs with a heavy output load when the input voltage is high and the output voltage is low. Common situations are immediately after the removal of a short circuit. The load line for such a load may intersect the output current curve at two points. If this happens, there are two stable operating points for the regulator. With this double intersection, the input power supply may need to be cycled down to zero and brought up again to make the output recover. 30801fb 12 LT3080-1 Applications Information Load Regulation Because the LT3080-1 is a floating device (there is no ground pin on the part, all quiescent and drive current is delivered to the load), it is not possible to provide true remote load sensing. Load regulation will be limited by the resistance of the connections between the regulator and the load. The data sheet specification for load regulation is Kelvin sensed at the pins of the package. Negative side sensing is a true Kelvin connection, with the bottom of the voltage setting resistor returned to the negative side of the load (see Figure 7). Connected as shown, system load regulation will be the sum of the LT3080-1 load regulation and the parasitic line resistance multiplied by the output current. It is important to keep the positive connection between the regulator and load as short as possible and use large wire or PC board traces. RSET = (VOUT + IMID * RBALLAST ) where ISET IMID = 1/2 (IOUT(MIN) + IOUT(MAX)) RBALLAST = 25m ISET = 10A LT3080-1 IN Thermal Considerations VCONTROL + - PARASITIC RESISTANCE 25m SET RSET OUT RP RP LOAD RP 30801 F07 Figure 7. Connections for Best Load Regulation The internal 25m ballast resistor is outside of the LT3080-1's feedback loop. Therefore, the voltage drop across the ballast resistor appears as additional DC load regulation. However, this additional load regulation can actually improve transient response performance by decreasing peak-to-peak output voltage deviation and even save on total output capacitance. This technique is called active voltage positioning and is especially useful for applications that must withstand large output load current transients. For more information, see Design Note 224, "Active Voltage Positioning Reduces Output Capacitors." The basic principle uses the fact that output voltage is a function of output load current. Output voltage is set based on the midpoint of the output load current range: ( As output current decreases below the midpoint, output voltage increases above the nominal set-point. Correspondingly, as output current increases above the midpoint, output voltage decreases below the nominal set-point. During a large output load transient, output voltage perturbation is contained within a window that is tighter than what would result if active voltage positioning is not employed. Choose the SET pin resistor value by using the formula below: 1 * I +I 2 OUT(MIN) OUT(MAX) The LT3080-1 has internal power and thermal limiting circuitry designed to protect it under overload conditions. For continuous normal load conditions, maximum junction temperature must not be exceeded. It is important to give consideration to all sources of thermal resistance from junction to ambient. This includes junction-to-case, case-to-heat sink interface, heat sink resistance or circuit board-to-ambient as the application dictates. Additional heat sources nearby must also be considered. For surface mount devices, heat sinking is accomplished by using the heat spreading capabilities of the PC board and its copper traces. Surface mount heat sinks and plated through-holes can also be used to spread the heat generated by power devices. Junction-to-case thermal resistance is specified from the IC junction to the bottom of the case directly below the die. This is the lowest resistance path for heat flow. Proper mounting is required to ensure the best possible thermal flow from this area of the package to the heat sinking material. Note that the Exposed Pad is electrically connected to the output. ) 30801fb 13 LT3080-1 Applications Information The following tables list thermal resistance for several different copper areas given a fixed board size. All measurements were taken in still air on two-sided 1/16" FR-4 board with one ounce copper. Table 1. MSE Package, 8-Lead MSOP COPPER AREA TOPSIDE* BACKSIDE BOARD AREA THERMAL RESISTANCE (JUNCTION-TO-AMBIENT) 2500mm2 2500mm2 2500mm2 55C/W 1000mm2 2500mm2 2500mm2 57C/W 225mm2 2500mm2 2500mm2 60C/W 100mm2 2500mm2 2500mm2 65C/W *Device is mounted on topside PDRIVE = (VCONTROL - VOUT)(ICONTROL) where ICONTROL is equal to IOUT /60. ICONTROL is a function of output current. A curve of ICONTROL vs IOUT can be found in the Typical Performance Characteristics curves. The power in the output transistor equals: POUTPUT = (VIN - VOUT)(IOUT) The total power equals: PTOTAL = PDRIVE + POUTPUT The current delivered to the SET pin is negligible and can be ignored. Table 2. DD Package, 8-Lead DFN COPPER AREA The power in the drive circuit equals: VCONTROL(MAX CONTINUOUS) = 3.630V (3.3V + 10%) TOPSIDE* BACKSIDE BOARD AREA THERMAL RESISTANCE (JUNCTION-TO-AMBIENT) 2500mm2 2500mm2 2500mm2 60C/W 1000mm2 2500mm2 2500mm2 62C/W VOUT = 0.9V, IOUT = 1A, TA = 50C 225mm2 2500mm2 2500mm2 65C/W 100mm2 2500mm2 2500mm2 68C/W Power dissipation under these conditions is equal to: *Device is mounted on topside PCB layers, copper weight, board layout and thermal vias affect the resultant thermal resistance. Although Tables 1 and 2 provide thermal resistance numbers for a 2-layer board with 1 ounce copper, modern multilayer PCBs provide better performance than found in these tables. For example, a 4-layer, 1 ounce copper PCB board with five thermal vias from the DFN or MSOP exposed backside pad to inner layers (connected to VOUT) achieves 40C/W thermal resistance. Demo circuit 995A's board layout achieves this 40C/W performance. This is approximately a 33% improvement over the numbers shown in Tables 1 and 2. Calculating Junction Temperature Example: Given an output voltage of 0.9V, a VCONTROL voltage of 3.3V 10%, an IN voltage of 1.5V 5%, output current range from 1mA to 1A and a maximum ambient temperature of 50C, what will the maximum junction temperature be for the DFN package on a 2500mm2 board with topside copper area of 500mm2? VIN(MAX CONTINUOUS) = 1.575V (1.5V + 5%) PDRIVE = (VCONTROL - VOUT)(ICONTROL) ICONTROL = IOUT 1A = = 17mA 60 60 PDRIVE = (3.630V - 0.9V)(17mA) = 46mW POUTPUT = (VIN - VOUT)(IOUT) POUTPUT = (1.575V - 0.9V)(1A) = 675mW Total Power Dissipation = 721mW Junction Temperature will be equal to: TJ = TA + PTOTAL * JA (approximated using tables) TJ = 50C + 721mW * 64C/W = 96C In this case, the junction temperature is below the maximum rating, ensuring reliable operation. 30801fb 14 LT3080-1 Applications Information C1 VIN VCONTROL LT3080-1 + - IN 25m SET RSET RS VIN OUT VOUT C2 The second technique for reducing power dissipation, shown in Figure 9, uses a resistor in parallel with the LT3080-1. This resistor provides a parallel path for current flow, reducing the current flowing through the LT3080-1. This technique works well if input voltage is reasonably constant and output load current changes are small. This technique also increases the maximum available output current at the expense of minimum load requirements. VIN 30801 F08 C1 VCONTROL LT3080-1 IN Figure 8. Reducing Power Dissipation Using a Series Resistor Reducing Power Dissipation In some applications it may be necessary to reduce the power dissipation in the LT3080-1 package without sacrificing output current capability. Two techniques are available. The first technique, illustrated in Figure 8, employs a resistor in series with the regulator's input. The voltage drop across RS decreases the LT3080-1's IN-toOUT differential voltage and correspondingly decreases the LT3080-1's power dissipation. As an example, assume: VIN = VCONTROL = 5V, VOUT = 3.3V and IOUT(MAX) = 1A. Use the formulas from the Calculating Junction Temperature section previously discussed. Without series resistor RS , power dissipation in the LT3080-1 equals: 1A PTOTAL = ( 5V - 3.3V ) * + ( 5V - 3.3V ) * 1A = 1.73W 60 If the voltage differential (VDIFF) across the NPN pass transistor is chosen as 0.5V, then RS equals: RS = 5V - 3.3V - 0.5V = 1.2 1A Power dissipation in the LT3080-1 now equals: PTOTAL 1A = ( 5V - 3.3V ) * + ( 0.5V ) * 1A = 0.53W 60 The LT3080-1's power dissipation is now only 30% compared to no series resistor. RS dissipates 1.2W of power. Choose appropriate wattage resistors to handle and dissipate the power properly. + - RP 25m OUT SET RSET VOUT C2 30801 F09 Figure 9. Reducing Power Dissipation Using a Parallel Resistor As an example, assume: VIN = VCONTROL = 5V, VIN(MAX) = 5.5V, VOUT = 3.3V, VOUT(MIN) = 3.2V, IOUT(MAX) = 1A and IOUT(MIN) = 0.7A. Also, assuming that RP carries no more than 90% of IOUT(MIN) = 630mA. Calculating RP yields: RP = 5.5V - 3.2V = 3.65 0.63A (5% Standard value = 3.6) The maximum total power dissipation is (5.5V - 3.2V) * 1A = 2.3W. However, the LT3080-1 supplies only: 1A - 5.5V - 3.2V = 0.36A 3.6 Therefore, the LT3080-1's power dissipation is only: PDIS = (5.5V - 3.2V) * 0.36A = 0.83W RP dissipates 1.47W of power. As with the first technique, choose appropriate wattage resistors to handle and dissipate the power properly. With this configuration, the LT3080-1 supplies only 0.36A. Therefore, load current can increase by 0.64A to 1.64A while keeping the LT3080-1 in its normal operating range. 30801fb 15 LT3080-1 Typical Applications Adding Shutdown LT3080-1 IN VCONTROL + - 25m OUT 25m OUT SET LT3080-1 IN VIN VCONTROL + - VOUT SET Q1 VN2222LL ON OFF Q2* VN2222LL R1 SHUTDOWN *Q2 INSURES ZERO OUTPUT IN THE ABSENCE OF ANY OUTPUT LOAD 30801 TA02 Current Source LT3080-1 IN VIN 10V VCONTROL + - 25m OUT 25m OUT SET LT3080-1 IN VCONTROL + - 2.2F SET 1 IOUT 0A TO 2A 100k 10F 30801 TA03 30801fb 16 LT3080-1 Typical Applications Using a Lower Value SET Resistor LT3080-1 IN VIN 10V VCONTROL + - 25m OUT 25m OUT SET LT3080-1 IN VCONTROL + - C1 2.2F VOUT = 0.5V + 2mA * RSET VOUT 0.5V TO 10V SET R1 24.9k 1% 2mA R2 249 1% COUT 10F RSET 4.99k 1% 30801 TA04 Adding Soft-Start VIN 4.8V TO 28V LT3080-1 IN VCONTROL + - D1 IN4148 25m OUT 25m OUT SET VOUT 3.3V 2.2A LT3080-1 IN VCONTROL + - C1 2.2F SET C2 0.01F R1 165k COUT 10F 30801 TA05 30801fb 17 LT3080-1 Typical Applications Lab Supply LT3080-1 IN VIN 13V TO 18V VCONTROL VCONTROL + - 25m + - OUT SET 25m OUT 25m OUT SET LT3080-1 IN LT3080-1 IN VCONTROL VCONTROL + - 25m OUT + - 0.5 50k 0A TO 2A SET + LT3080-1 IN CURRENT LIMIT 15F VOUT 0V TO 10V SET + R4 500k 15F 10F + 100F 3080 TA06 Boosting Fixed Output Regulators LT3080-1 + - 25m OUT SET LT1963-3.3 5V 10F 20m 42* 3.3VOUT 2.6A 47F 30801 TA07 33k *4mV DROP ENSURES LT3080-1 IS OFF WITH NO-LOAD MULTIPLE LT3080-1'S CAN BE USED IN PARALLEL 30801fb 18 LT3080-1 Typical Applications Low Voltage, High Current Adjustable High Efficiency Regulator* 0.47H 2.7V TO 5.5V 2x + 100F 2.2MEG 100k PVIN SW SVIN ITH LTC3414 10k + 12.1k 470pF RT 294k PGOOD 2x 100F 2N3906 LT3080-1 IN VCONTROL RUN/SS + - VFB 1000pF 78.7k PGND OUT 25m OUT 25m OUT 25m OUT SET SYNC/MODE SGND 25m 124k IN LT3080-1 VCONTROL + - * DIFFERENTIAL VOLTAGE ON LT3080-1 IS 0.6V SET BY THE VBE OF THE 2N3906 PNP MAXIMUM OUTPUT VOLTAGE IS 1.5V BELOW INPUT VOLTAGE SET 0V TO 4V 4A LT3080-1 IN VCONTROL + - SET IN LT3080-1 VCONTROL + - SET + 100k 100F 30801 TA08 30801fb 19 LT3080-1 Typical Applications Adjustable High Efficiency Regulator* CMDSH-4E 4.5V TO 25V VIN 10F 1F 100k BOOST LT3493 SHDN 0.1F 10H 0.1F LT3080-1 IN SW 68F MBRM140 VCONTROL TP0610L GND + - FB 10k 25m OUT SET 4.7F 0V TO 10V 1A 1MEG *DIFFERENTIAL VOLTAGE ON LT3080-1 1.4V SET BY THE TPO610L P-CHANNEL THRESHOLD. MAXIMUM OUTPUT VOLTAGE IS 2V BELOW INPUT VOLTAGE 10k 30801 TA09 2 Terminal Current Source CCOMP* IN LT3080-1 VCONTROL + - SET 25m OUT R1 100k 30801 TA10 *CCOMP R1 10 10F R1 10 2.2F CURRENT SET IOUT = 1V R1 30801fb 20 LT3080-1 Package Description Please refer to http://www.linear.com/designtools/packaging/ for the most recent package drawings. DD Package 8-Lead Plastic DFN (3mm x 3mm) (Reference LTC DWG # 05-08-1698 Rev C) 0.70 0.05 3.5 0.05 1.65 0.05 2.10 0.05 (2 SIDES) PACKAGE OUTLINE 0.25 0.05 0.50 BSC 2.38 0.05 RECOMMENDED SOLDER PAD PITCH AND DIMENSIONS APPLY SOLDER MASK TO AREAS THAT ARE NOT SOLDERED PIN 1 TOP MARK (NOTE 6) 0.200 REF 3.00 0.10 (4 SIDES) R = 0.125 TYP 5 0.40 0.10 8 1.65 0.10 (2 SIDES) 0.75 0.05 4 0.25 0.05 1 (DD8) DFN 0509 REV C 0.50 BSC 2.38 0.10 0.00 - 0.05 BOTTOM VIEW--EXPOSED PAD NOTE: 1. DRAWING TO BE MADE A JEDEC PACKAGE OUTLINE M0-229 VARIATION OF (WEED-1) 2. DRAWING NOT TO SCALE 3. ALL DIMENSIONS ARE IN MILLIMETERS 4. DIMENSIONS OF EXPOSED PAD ON BOTTOM OF PACKAGE DO NOT INCLUDE MOLD FLASH. MOLD FLASH, IF PRESENT, SHALL NOT EXCEED 0.15mm ON ANY SIDE 5. EXPOSED PAD SHALL BE SOLDER PLATED 6. SHADED AREA IS ONLY A REFERENCE FOR PIN 1 LOCATION ON TOP AND BOTTOM OF PACKAGE 30801fb 21 LT3080-1 Package Description Please refer to http://www.linear.com/designtools/packaging/ for the most recent package drawings. MS8E Package 8-Lead Plastic MSOP (Reference LTC DWG # 05-08-1662 Rev I) BOTTOM VIEW OF EXPOSED PAD OPTION 1.88 (.074) 1 1.88 0.102 (.074 .004) 0.29 REF 1.68 (.066) 0.889 0.127 (.035 .005) 0.05 REF 5.23 (.206) MIN DETAIL "B" CORNER TAIL IS PART OF DETAIL "B" THE LEADFRAME FEATURE. FOR REFERENCE ONLY NO MEASUREMENT PURPOSE 1.68 0.102 3.20 - 3.45 (.066 .004) (.126 - .136) 8 3.00 0.102 (.118 .004) (NOTE 3) 0.65 (.0256) BSC 0.42 0.038 (.0165 .0015) TYP 8 7 6 5 0.52 (.0205) REF RECOMMENDED SOLDER PAD LAYOUT 0.254 (.010) 3.00 0.102 (.118 .004) (NOTE 4) 4.90 0.152 (.193 .006) DETAIL "A" 0 - 6 TYP GAUGE PLANE 0.53 0.152 (.021 .006) DETAIL "A" 1 2 3 4 1.10 (.043) MAX 0.86 (.034) REF 0.18 (.007) SEATING PLANE 0.22 - 0.38 (.009 - .015) TYP 0.65 (.0256) BSC 0.1016 0.0508 (.004 .002) MSOP (MS8E) 0910 REV I NOTE: 1. DIMENSIONS IN MILLIMETER/(INCH) 2. DRAWING NOT TO SCALE 3. DIMENSION DOES NOT INCLUDE MOLD FLASH, PROTRUSIONS OR GATE BURRS. MOLD FLASH, PROTRUSIONS OR GATE BURRS SHALL NOT EXCEED 0.152mm (.006") PER SIDE 4. DIMENSION DOES NOT INCLUDE INTERLEAD FLASH OR PROTRUSIONS. INTERLEAD FLASH OR PROTRUSIONS SHALL NOT EXCEED 0.152mm (.006") PER SIDE 5. LEAD COPLANARITY (BOTTOM OF LEADS AFTER FORMING) SHALL BE 0.102mm (.004") MAX 6. EXPOSED PAD DIMENSION DOES NOT INCLUDE MOLD FLASH. MOLD FLASH ON E-PAD SHALL NOT EXCEED 0.254mm (.010") PER SIDE. 30801fb 22 LT3080-1 Revision History (Revision history begins at Rev B) REV DATE DESCRIPTION PAGE NUMBER B 9/11 Updated the Absolute Maximum Ratings, Order Information, and Note 2 in the Electrical Characteristics sections to include I-grade parts. 2, 3 30801fb Information furnished by Linear Technology Corporation is believed to be accurate and reliable. However, no responsibility is assumed for its use. Linear Technology Corporation makes no representation that the interconnection of its circuits as described herein will not infringe on existing patent rights. 23 LT3080-1 Typical Application Paralleling Regulators LT3080-1 IN VCONTROL + - 25m OUT 25m OUT SET LT3080-1 IN VIN 4.8V TO 28V VCONTROL + - 1F VOUT 3.3V 2.2A SET 165k 10F 30801 TA11 Related Parts PART NUMBER DESCRIPTION COMMENTS LT1086 1.5A Low Dropout Regulator Fixed 2.85V, 3.3V, 3.6V, 5V and 12V Output LT1117 800mA Low Dropout Regulator 1V Dropout, Adjustable or Fixed Output, DD-Pak, SOT-223 Packages LDOs LT1118 800mA Low Dropout Regulator Okay for Sinking and Sourcing, S0-8 and SOT-223 Packages LT1963A 1.5A Low Noise, Fast Transient Response LDO 340mV Dropout Voltage, Low Noise = 40VRMS , VIN : 2.5V to 20V, TO-220, DD, SOT-223 and SO-8 Packages LT1965 1.1A Low Noise LDO 290mV Dropout Voltage, Low Noise 40VRMS , VIN : 1.8V to 20V, VOUT : 1.2V to 19.5V, Stable with Ceramic Caps, TO-220, DDPak, MSOP and 3mm x 3mm DFN Packages LTC(R)3026 1.5A Low Input Voltage VLDOTM Regulator VIN : 1.14V to 3.5V (Boost Enabled), 1.14V to 5.5V (with External 5V), VDO = 0.1V, IQ = 950A, Stable with 10F Ceramic Capacitors, 10-Lead MSOP and DFN Packages LT3080 1.1A, Parallelable, Low Noise, Low Dropout Linear Regulator 300mV Dropout Voltage (2-Supply Operation), Low Noise: 40VRMS , VIN : 1.2V to 36V, VOUT : 0V to 35.7V, Current-Based Reference with 1-Resistor VOUT Set, Directly Parallelable (No Op Amp Required), Stable with Ceramic Capacitors, TO-220, SOT-223, MSOP and 3mm x 3mm DFN Packages. LTC3414 4A (IOUT), 4MHz Synchronous Step-Down DC/DC Converter 95% Efficiency, VIN: 2.25V to 5.5V, VOUT(MIN) = 0.8V, TSSOP Package LTC3406/LTC3406B 600mA (IOUT), 1.5MHz Synchronous Step-Down DC/DC Converter 95% Efficiency, VIN: 2.5V to 5.5V, VOUT(MIN) = 0.6V, IQ = 20A, ISD < 1A, ThinSOTTM Package LTC3411 1.25A (IOUT), 4MHz Synchronous Step-Down DC/DC Converter 95% Efficiency, VIN: 2.5V to 5.5V, VOUT(MIN) = 0.8V, IQ = 60A, ISD < 1A, 10-Lead MS or DFN Packages Switching Regulators 30801fb 24 Linear Technology Corporation LT 0911 REV B * PRINTED IN USA 1630 McCarthy Blvd., Milpitas, CA 95035-7417 (408) 432-1900 FAX: (408) 434-0507 www.linear.com LINEAR TECHNOLOGY CORPORATION 2008