CAUTION: These devices are sensitive to electrostatic discharge. Users should follow proper I.C. Handling Procedures.
Copyright © Harris Corporation 1993 2-33
SEMICONDUCTOR
Pinouts
ICL7106, ICL7107
(PDIP)
TOP VIEW
ICL7106, ICL7107
(MQFP)
TOP VIEW
13
1
2
3
4
5
6
7
8
9
10
11
12
14
15
16
17
18
19
20
V+
D1
C1
B1
A1
F1
G1
E1
D2
C2
B2
A2
F2
E2
D3
B3
F3
E3
(1000) AB4
POL
28
40
39
38
37
36
35
34
33
32
31
30
29
27
26
25
24
23
22
21
OSC 1
OSC 2
OSC 3
TEST
REF HI
REF LO
CREF+
CREF-
COMMON
IN HI
IN LO
A-Z
BUFF
INT
V-
G2 (10’s)
C3
A3
G3
BP/GND
(1’s)
(10’s)
(100’s)
(MINUS)
(100’s)
OSC 2
NC
OSC 3
TEST
NC
NC 1
2
3
4
5
6
7
8
9
10
11
12 13 14 15 16 17
OSC 1
V+
D1
C1
B1
A1 F1 G1 E1 D2 C2
28
27
26
25
24
23
2221201918
B2 A2 F2 E2 D3
B3
F3
E3
AB4
POL
BP/GND
39 38 37 36 35 34
33
32
31
30
29
44 43 42 41 40
IN HI
IN LO
A-Z
BUFF
INT
V-
NC
G2
C3
A3
G3
REF HI
REF LO
CREF+
CREF-
COMMON
ICL7106, ICL7107
31/2 Digit LCD/LED
Display A/D Converter
Features
• Guaranteed Zero Reading for 0V Input on All Scales
• True Polarity at Zero for Precise Null Detection
• 1pA Typical Input Current
• True Differential Input and Reference, Direct Display Drive
- LCD ICL7106
- LED lCL7l07
• Low Noise - Less Than 15µVp-p
• On Chip Clock and Reference
• Low Power Dissipation - Typically Less Than 10mW
• No Additional Active Circuits Required
• New Small Outline Surface Mount Package Available
Ordering Information
PART
NUMBER TEMPERATURE
RANGE PACKAGE
ICL7106CPL 0oC to +70oC 40 Lead Plastic DIP
ICL7106RCPL 0oC to +70oC 40 Lead Plastic DIP (Note 1)
ICL7106CM44 0oC to +70oC 44Lead Metric Plastic Quad Flatpack
ICL7107CPL 0oC to +70oC 40 Lead Plastic DIP
ICL7107RCPL 0oC to +70oC 40 Lead Plastic DIP (Note 1)
ICL7107CM44 0oC to +70oC 44Lead Metric Plastic Quad Flatpack
NOTE: 1. “R” indicates device with reversed leads.
File Number 3082
January 1994
Description
The Harris ICL7106 and ICL7107 are high
performance, low power 31/2 digit A/D converters.
Included are seven segment decoders, display drivers,
a reference, and a clock. The ICL7106 is designed to
interface with a liquid crystal display (LCD) and
includes a multiplexed backplane drive; the ICL7107
will directly drive an instrument size light emitting
diode (LED) display.
The ICL7106 and ICL7107 bring together a
combination of high accuracy, versatility, and true
economy. It features auto-zero to less than 10µV, zero
drift of less than 1µV/οC, input bias current of 10pA
max., and rollover error of less than one count. True
differential inputs and reference are useful in all sys-
tems, but give the designer an uncommon advantage
when measuring load cells, strain gauges and other
bridge type transducers. Finally, the true economy of
single power supply operation (ICL7106), enables a
high performance panel meter to be built with the
addition of only 10 passive components and a display.
2-34
Specifications ICL7106, ICL7107
Absolute Maximum Ratings Thermal Information
Supply Voltage
ICL7106, V+ to V- . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 15V
ICL7107, V+ to GND. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 6V
ICL7107, V- to GND . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .-9V
Analog Input Voltage (Either Input) (Note 1). . . . . . . . . . . . . V+ to V-
Reference Input Voltage (Either Input). . . . . . . . . . . . . . . . . V+ to V-
Clock Input
ICL7106 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . TEST to V+
ICL7107 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .GND to V+
Thermal Resistance (MAX, See Note 1) θJA
40 Pin Plastic Package . . . . . . . . . . . . . . . . . . . . . . . . 50oC/W
44 Pin MQFP Package . . . . . . . . . . . . . . . . . . . . . . . . 80oC/W
Maximum Power Dissipation
ICL7106. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .1.0W
ICL7107. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .1.2W
Operating Temperature Range . . . . . . . . . . . . . . . . . . 0oC to +70oC
Storage Temperature Range. . . . . . . . . . . . . . . . . .-65oC to +150oC
Lead Temperature (Soldering 10s Max) . . . . . . . . . . . . . . . . +265oC
Junction Temperature . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . +150oC
CAUTION: Stresses above those listed in “Absolute Maximum Ratings” may cause permanent damage to the device. This is a stress only rating and operation
of the device at these or any other conditions above those indicated in the operational sections of this specification is not implied.
Electrical Specifications (Note 3)
PARAMETERS TEST CONDITIONS MIN TYP MAX UNIT
SYSTEM PERFORMANCE
Zero Input Reading VIN = 0.0V, Full-Scale = 200mV -000.0 ±000.0 +000.0 Digital
Reading
Ratiometric Reading VlN = VREF, VREF = 100mV 999 999/
1000 1000 Digital
Reading
Rollover Error -VIN = +VlN ≅ 200mV
Difference in Reading for Equal Positive and Nega-
tive Inputs Near Full-Scale
-±0.2 ±1 Counts
Linearity Full-Scale = 200mV or Full-Scale = 2V Maximum
Deviation from Best Straight Line Fit (Note 5) -±0.2 ±1 Counts
Common Mode Rejection Ratio VCM = 1V, VIN = 0V, Full-Scale = 200mV(Note 5) - 50 - µV/V
Noise VIN = 0V, Full-Scale = 200mV
(Pk-Pk Value Not Exceeded 95% of T ime) -15- µV
Leakage Current Input VlN = 0 (Note 5) - 1 10 pA
Zero Reading Drift VlN = 0, 0o< TA < +70oC (Note 5) - 0.2 1 µV/oC
Scale Factor Temperature Coefficient VIN = 199mV, 0o< TA < +70oC,
(Ext. Ref. 0ppm/oC) (Note 5) - 1 5 ppm/oC
End Power Supply Character V+ Supply Cur-
rent VIN = 0 (Does Not Include LED Current for ICL7107) - 0.8 1.8 mA
End Power Supply Character V - Supply Current ICL7107 Only - 0.6 1.8 mA
COMMON Pin Analog Common Voltage 25kΩ Between Common and
Positive Supply (With Respect to + Supply) 2.4 2.8 3.2 V
Temperature Coefficient of Analog Common 25kΩ Between Common and
Positive Supply (With Respect to + Supply) - 80 - ppm/oC
DISPLAY DRIVER ICL7106 ONLY
Pk-Pk Segment Drive Voltage
Pk-Pk Backplane Drive Voltage V+= to V- = 9V, (Note 4) 4 5 6 V
2-35
ICL7106, ICL7107
Typical Applications and Test Circuits
ICL7107 ONLY
Segment Sinking Current V+ = 5V, Segment Voltage = 3V
(Except Pin 19 and 20) 58- mA
Pin 19 Only 10 16 - mA
Pin 20 Only 47- mA
NOTES:
1. Input voltages may exceed the supply voltages provided the input current is limited to ±100µA.
2. Dissipation rating assumes device is mounted with all leads soldered to printed circuit board.
3. Unless otherwise noted, specifications apply to both the ICL7106 and ICL7107 at TA = +25 oC, fCLOCK = 48kHz. ICL7106 is tested in the
circuit of Figure 1. ICL7107 is tested in the circuit of Figure 2.
4. Back plane drive is in phase with segment drive for ‘off’ segment, 180 o out of phase for ‘on’ segment. Frequency is 20 times conversion
rate. Average DC component is less than 50mV.
5. Not tested, guaranteed by design.
FIGURE 1. ICL7106 TEST CIRCUIT AND TYPICAL APPLICATION WITH LCD DISPLAY COMPONENTS SELECTED FOR 200mV FULL-
SCALE
FIGURE 2. ICL7107 TEST CIRCUIT AND TYPICAL APPLICATION WITH LED DISPLAY COMPONENTS SELECTED FOR 200mV FULL-
SCALE
Electrical Specifications (Note 3) (Continued)
PARAMETERS TEST CONDITIONS MIN TYP MAX UNIT
13
1
2
3
4
5
6
7
8
9
10
11
12
14
15
16
17
18
19
20
28
40
39
38
37
36
35
34
33
32
31
30
29
27
26
25
24
23
22
21
V+
D1
C1
B1
A1
F1
G1
E1
D2
C2
B2
A2
F2
E2
D3
B3
F3
E3
AB4
POL
OSC 1
OSC 2
OSC 3
TEST
REF HI
REF LO
CREF+
CREF-
COM
IN HI
IN LO
A-Z
BUFF
INT
V-
G2
C3
A3
G3
BP
DISPLAY
DISPLAY
C1C2C3
C4
R3
R1
R4C5
+-
IN
R5
R2
9V
ICL7106
C1 = 0.1µF
C2 = 0.47µF
C3 = 0.22µF
C4 = 100pF
C5 = 0.02µF
R1 = 24kΩ
R2 = 47kΩ
R3 = 100kΩ
R4 = 1kΩ
R5 = 1MΩ
13
1
2
3
4
5
6
7
8
9
10
11
12
14
15
16
17
18
19
20
28
40
39
38
37
36
35
34
33
32
31
30
29
27
26
25
24
23
22
21
V+
D1
C1
B1
A1
F1
G1
E1
D2
C2
B2
A2
F2
E2
D3
B3
F3
E3
AB4
POL
OSC 1
OSC 2
OSC 3
TEST
REF HI
REF LO
CREF+
CREF-
COM
IN HI
IN LO
A-Z
BUFF
INT
V-
G2
C3
A3
G3
GND
DISPLAY
DISPLAY
C1C2C3
C4
R3
R1
R4C5
+-
IN
R5
R2
ICL7107
+5V -5V
C1 = 0.1µF
C2 = 0.47µF
C3 = 0.22µF
C4 = 100pF
C5 = 0.02µF
R1 = 24kΩ
R2 = 47kΩ
R3 = 100kΩ
R4 = 1kΩ
R5 = 1MΩ
2-36
ICL7106, ICL7107
Typical Integrator Amplifier Output Waveform (INT Pin)
Design Information Summary Sheet
• OSCILLATOR FREQUENCY
fOSC = 0.45/RC
COSC > 50pF; ROSC > 50KΩ
fOSC Typ. = 48KHz
• OSCILLATOR PERIOD
tOSC = RC/0.45
• INTEGRATION CLOCK FREQUENCY
fCLOCK = fOSC/4
• INTEGRATION PERIOD
tINT = 1000 x (4/fOSC)
• 60/50Hz REJECTION CRITERION
tINT/t60Hz or tlNT/t60Hz = Integer
• OPTIMUM INTEGRATION CURRENT
IINT = 4.0µA
• FULL-SCALE ANALOG INPUT VOLTAGE
VlNFS Typically = 200mV or 2.0V
• INTEGRATE RESISTOR
• INTEGRATE CAPACITOR
• INTEGRATOR OUTPUT VOLTAGE SWING
•V
INT MAXIMUM SWING:
(V- + 0.5V) < VINT < (V+ - 0.5V), VINT typically = 2.0V
• DISPLAY COUNT
• CONVERSION CYCLE
tCYC = tCL0CK x 4000
tCYC = tOSC x 16,000
when fOSC = 48KHz; tCYC = 333ms
• COMMON MODE INPUT VOLTAGE
(V- + 1.0V) < VlN < (V+ - 0.5V)
• AUTO-ZERO CAPACITOR
0.01µF < CAZ < 1.0µF
• REFERENCE CAPACITOR
0.1µF < CREF < 1.0µF
•V
COM
Biased between Vi and V-.
•V
COM ≅ V+ - 2.8V
Regulation lost when V+ to V- < ≅6.8V.
If VCOM is externally pulled down to (V + to V -)/2,
the VCOM circuit will turn off.
• ICL7106 POWER SUPPLY: SINGLE 9V
V+ - V- = 9V
Digital supply is generated internally
VGND ≅ V+ - 4.5V
• ICL7106 DISPLAY: LCD
Type: Direct drive with digital logic supply amplitude.
• ICL7107 POWER SUPPLY: DUAL ±5.0V
V+ = +5.0V to GND
V- = -5.0V to GND
Digital Logic and LED driver supply V+ to GND
• ICL7107 DISPLAY: LED
Type: Non-Multiplexed Common Anode
RINT
VINFS
IINT
=
CINT
tINT
()I
INT
()
V
INT
=
VINT
tINT
()I
INT
()
C
INT
=
COUNT 1000 VIN
VREF
×=
AUTO ZERO PHASE
(COUNTS)
2999 - 1000
SIGNAL INTEGRATE
PHASE FIXED
1000 COUNTS
DE-INTEGRATE PHASE
0 - 1999 COUNTS
TOTAL CONVERSION TIME = 4000 x tCLOCK = 16,000 x tOSC
2-37
ICL7106, ICL7107
Detailed Description
Analog Section
Figure 3 shows the Analog Section for the ICL7106 and
ICL7107. Each measurement cycle is divided into three
phases. They are (1) auto-zero (A-Z), (2) signal integrate
(INT) and (3) de-integrate (DE).
Auto-Zero Phase
During auto-zero three things happen. First, input high and
low are disconnected from the pins and internally shorted to
analog COMMON. Second, the reference capacitor is
charged to the reference voltage. Third, a feedback loop is
closed around the system to charge the auto-zero capacitor
CAZ to compensate for offset voltages in the buffer amplifier,
integrator, and comparator. Since the comparator is included
in the loop, the A-Z accuracy is limited only by the noise of
the system. In any case, the offset referred to the input is
less than 10µV.
Signal Integrate Phase
During signal integrate, the auto-zero loop is opened, the
internal short is removed, and the internal input high and low
are connected to the external pins. The converter then
integrates the differential voltage between IN HI and IN LO
for a fixed time. This differential voltage can be within a wide
common mode range: up to 1V from either supply. If, on the
other hand, the input signal has no return with respect to the
converter power supply, IN LO can be tied to analog
COMMON to establish the correct common mode voltage. At
the end of this phase, the polarity of the integrated signal is
determined.
De-Integrate Phase
The final phase is de-integrate, or reference integrate. Input
low is internally connected to analog COMMON and input
high is connected across the previously charged reference
capacitor. Circuitry within the chip ensures that the capacitor
will be connected with the correct polarity to cause the
integrator output to return to zero. The time required for the
output to return to zero is proportional to the input signal.
Specifically the digital reading displayed is:
.
Differential Input
The input can accept differential voltages anywhere within
the common mode range of the input amplifier, or specifically
from 0.5V below the positive supply to 1.0V above the
negative supply. In this range, the system has a CMRR of
86dB typical. However, care must be exercised to assure the
integrator output does not saturate. A worst case condition
would be a large positive common mode voltage with a near
full-scale negative differential input voltage. The negative
input signal drives the integrator positive when most of its
swing has been used up by the positive common mode
voltage. For these critical applications the integrator output
swing can be reduced to less than the recommended 2V full-
scale swing with little loss of accuracy. The integrator output
can swing to within 0.3V of either supply without loss of
linearity.
DISPLAYCOUNT=1000 VIN
VREF


FIGURE 3. ANALOG SECTION OF ICL7106 AND ICL7107
DE-DE+
CINT
CAZ
RINT
BUFFER A-Z INT
-
+
A-Z
COMPARATOR
IN HI
COMMON
IN LO
31
32
30
DE- DE+
INT
A-Z
34
CREF+
36
REF HI
CREF
REF LO
35
A-Z A-Z
33
CREF-
28 29 27
TO
DIGITAL
SECTION
A-Z AND DE(±)
INTEGRATOR
INT
STRAY STRAY
V+
10µA
V-
N
INPUT
HIGH
2.8V
6.2V
V+
1
INPUT
LOW
-
+
-
+
-
+
2-38
ICL7106, ICL7107
Differential Reference
The reference voltage can be generated anywhere within the
power supply voltage of the converter. The main source of
common mode error is a roll-over voltage caused by the
reference capacitor losing or gaining charge to stray capacity
on its nodes. If there is a large common mode voltage, the
reference capacitor can gain charge (increase voltage) when
called up to de-integrate a positive signal but lose charge
(decrease voltage) when called up to de-integrate a negative
input signal. This difference in reference for positive or
negative input voltage will give a roll-over error. However, by
selecting the reference capacitor such that it is large enough
in comparison to the stray capacitance, this error can be
held to less than 0.5 count worst case. (See Component
Value Selection.)
Analog COMMON
This pin is included primarily to set the common mode
voltage for battery operation (ICL7106) or for any system
where the input signals are floating with respect to the power
supply. The COMMON pin sets a voltage that is approxi-
mately 2.8V more negative than the positive supply. This is
selected to give a minimum end-of-life battery voltage of
about 6V. However, analog COMMON has some of the
attributes of a reference voltage. When the total supply
voltage is large enough to cause the zener to regulate (>7V),
the COMMON voltage will have a low voltage coefficient
(0.001%/V), low output impedance (≅15Ω), and a
temperature coefficient typically less than 80ppm/oC.
The limitations of the on chip reference should also be
recognized, however. With the ICL7107, the internal heating
which results from the LED drivers can cause some
degradation in performance. Due to their higher thermal
resistance, plastic parts are poorer in this respect than
ceramic. The combination of reference Temperature
Coefficient (TC), internal chip dissipation, and package ther-
mal resistance can increase noise near full-scale from 25µV
to 80µVp-p. Also the linearity in going from a high dissipation
count such as 1000 (20 segments on) to a low dissipation
count such as 1111(8 segments on) can suffer by a count or
more. Devices with a positive TC reference may require
several counts to pull out of an over-range condition. This is
because over-range is a low dissipation mode, with the three
least significant digits blanked. Similarly, units with a
negative TC may cycle between over-range and a non-over-
range count as the die alternately heats and cools. All these
problems are of course eliminated if an external reference is
used.
The ICL7106, with its negligible dissipation, suffers from
none of these problems. In either case, an external
reference can easily be added, as shown in Figure 4.
Analog COMMON is also used as the input low return during
auto-zero and de-integrate. If IN LO is different from analog
COMMON, a common mode voltage exists in the system
and is taken care of by the excellent CMRR of the converter.
However, in some applications IN LO will be set at a fixed
known voltage (power supply common for instance). In this
application, analog COMMON should be tied to the same
point, thus removing the common mode voltage from the
converter. The same holds true for the reference voltage. If
reference can be conveniently tied to analog COMMON, it
should be since this removes the common mode voltage
from the reference system.
Within the lC, analog COMMON is tied to an N channel FET
that can sink approximately 30mA of current to hold the
voltage 2.8V below the positive supply (when a load is trying
to pull the common line positive). However, there is only
10µA of source current, so COMMON may easily be tied to a
more negative voltage thus overriding the internal reference.
FIGURE 4. USING AN EXTERNAL REFERENCE
TEST
The TEST pin serves two functions. On the ICL7106 it is
coupled to the internally generated digital supply through a
500Ω resistor. Thus it can be used as the negative supply for
externally generated segment drivers such as decimal points
or any other presentation the user may want to include on
the LCD display. Figures 5 and 6 show such an application.
No more than a 1mA load should be applied.
FIGURE 5. SIMPLE INVERTER FOR FIXED DECIMAL POINT
ICL7106
V
REF LO
ICL7107
REF HI
V+
V-
6.8V
ZENER
IZ
ICL7106
V
REF HI
REF LO
COMMON
V+
ICL8069
1.2V
REFERENCE
6.8kΩ
20kΩ
ICL7107
FIGURE 4A.
FIGURE 4B.
ICL7106
V+
BP
TEST
21
37 TO LCD
BACKPLANE
TO LCD
DECIMAL
POINT
1MΩ
2-39
ICL7106, ICL7107
The second function is a “lamp test”. When TEST is pulled
high (to V+) all segments will be turned on and the display
should read “1888”. The TEST pin will sink about 15mA
under these conditions.
CAUTION: In the lamp test mode, the segments have a constant DC
voltage (no square-wave). This may burn the LCD display if main-
tained for extended periods.
FIGURE 6. EXCLUSIVE ‘OR’ GATE FOR DECIMAL POINT DRIVE
ICL7106
V+ BP
TEST
DECIMAL
POINT
SELECT
CD4030
GND
V+
TO LCD
DECIMAL
POINTS
Digital Section
Figures 7 and 8 show the digital section for the ICL7106 and
ICL7107, respectively. In the ICL7106, an internal digital
ground is generated from a 6V Zener diode and a large P-
channel source follower. This supply is made stiff to absorb
the relative large capacitive currents when the back plane
(BP) voltage is switched. The BP frequency is the clock fre-
quency divided by 800. For three readings/second this is a
60Hz square wave with a nominal amplitude of 5V. The seg-
ments are driven at the same frequency and amplitude and
are in phase with BP when OFF, but out of phase when ON.
In all cases negligible DC voltage exists across the seg-
ments.
Figure 8 is the Digital Section of the ICL7107. It is identical
to the ICL7106 except that the regulated supply and back
plane drive have been eliminated and the segment drive has
been increased from 2mA to 8mA, typical for instrument size
common anode LED displays. Since the 1000 output (pin 19)
must sink current from two LED segments, it has twice the
drive capability or 16mA.
In both devices, the polarity indication is “on” for negative
analog inputs. If IN LO and IN HI are reversed, this indication
can be reversed also, if desired.
FIGURE 7. ICL7106 DIGITAL SECTION
7
SEGMENT
DECODE
SEGMENT
OUTPUT
0.5mA
2.0mA
INTERNAL DIGITAL GROUND
TYPICAL SEGMENT OUTPUT
V+
LCD PHASE DRIVER
LATCH
7
SEGMENT
DECODE ÷200
LOGIC CONTROL
INTERNAL VTH = 1V
7
SEGMENT
DECODE
1000’s 100’s 10’s 1’s
TO SWITCH DRIVERS
FROM COMPARATOR OUTPUT
DIGITAL
GROUND
÷4
CLOCK
40 39 38
OSC 1 OSC 2 OSC 3
BACKPLANE
21
V+
TEST
V-
500Ω
37
26
6.2V
COUNTER COUNTER COUNTER COUNTER
1
c
ab
c
d
fg
e
a
b
ab
c
d
fg
e
ab
c
d
fg
e
†
† THREE INVERTERS
ONE INVERTER SHOWN FOR CLARITY
2-40
ICL7106, ICL7107
System Timing
Figure 9 shows the clocking arrangement used in the
ICL7106 and ICL7107. Two basic clocking arrangements
can be used:
1. An external oscillator connected to pin 40.
2. An R-C oscillator using all three pins.
The oscillator frequency is divided by four before it clocks the
decade counters. It is then further divided to form the three
convert-cycle phases. These are signal integrate (1000
counts), reference de-integrate (0 to 2000 counts) and auto-
zero (1000 to 3000 counts). For signals less than full-scale,
auto-zero gets the unused portion of reference de-integrate.
This makes a complete measure cycle of 4,000 counts
(16,000 clock pulses) independent of input voltage. For three
readings/second, an oscillator frequency of 48kHz would be
used.
To achieve maximum rejection of 60Hz pickup, the signal
integrate cycle should be a multiple of 60Hz. Oscillator
frequencies of 240kHz, 120kHz, 80kHz, 60kHz, 48kHz,
40kHz, 331/3kHz, etc. should be selected. For 50Hz rejec-
tion, Oscillator frequencies of 200kHz, 100kHz, 662/3kHz,
50kHz, 40kHz, etc. would be suitable. Note that 40kHz (2.5
readings/second) will reject both 50Hz and 60Hz (also
400Hz and 440Hz). FIGURE 9. CLOCK CIRCUITS
CLOCK
INTERNAL TO PART
40 39 38
GND ICL7107
÷4
CLOCK
INTERNAL TO PART
40 39 38
÷4
RC OSCILLATOR
RC
TEST ICL7106
FIGURE 8. ICL7107 DIGITAL SECTION
7
SEGMENT
DECODE
TO
SEGMENT
0.5mA
8.0mA
DIGITAL GROUND
TYPICAL SEGMENT OUTPUT
V+ LATCH
7
SEGMENT
DECODE
LOGIC CONTROL
7
SEGMENT
DECODE
1000’s 100’s 10’s 1’s
TO SWITCH DRIVERS
FROM COMPARATOR OUTPUT
DIGITAL
GROUND
÷4
CLOCK
40 39 38
OSC 1 OSC 2 OSC 3
V+
TEST
500Ω
COUNTER COUNTER COUNTER COUNTER
1
V+
37
27
c
ab
c
d
fg
e
a
b
ab
c
d
fg
e
ab
c
d
fg
e
†
† THREE INVERTERS
ONE INVERTER SHOWN FOR CLARITY
2-41
ICL7106, ICL7107
Component Value Selection
Integrating Resistor
Both the buffer amplifier and the integrator have a class A
output stage with 100µA of quiescent current. They can
supply 4µA of drive current with negligible nonlinearity. The
integrating resistor should be large enough to remain in this
very linear region over the input voltage range, but small
enough that undue leakage requirements are not placed on
the PC board. For 2V full-scale, 470kΩ is near optimum and
similarly a 47kΩ for a 200mV scale.
Integrating Capacitor
The integrating capacitor should be selected to give the
maximum voltage swing that ensures tolerance buildup will
not saturate the integrator swing (approximately. 0.3V from
either supply). In the ICL7106 or the ICL7107, when the
analog COMMON is used as a reference, a nominal +2V full-
scale integrator swing is fine. For the ICL7107 with +5V
supplies and analog COMMON tied to supply ground, a
±3.5V to +4V swing is nominal. For three readings/second
(48kHz clock) nominal values for ClNT are 0.22µF and
0.10µF, respectively. Of course, if different oscillator frequen-
cies are used, these values should be changed in inverse
proportion to maintain the same output swing.
An additional requirement of the integrating capacitor is that
it must have a low dielectric absorption to prevent roll-over
errors. While other types of capacitors are adequate for this
application, polypropylene capacitors give undetectable
errors at reasonable cost.
Auto-Zero Capacitor
The size of the auto-zero capacitor has some influence on
the noise of the system. For 200mV full-scale where noise is
very important, a 0.47µF capacitor is recommended. On the
2V scale, a 0.047µF capacitor increases the speed of recov-
ery from overload and is adequate for noise on this scale.
Reference Capacitor
A 0.1µF capacitor gives good results in most applications.
However, where a large common mode voltage exists (i.e.
the REF LO pin is not at analog COMMON) and a 200mV
scale is used, a larger value is required to prevent roll-over
error. Generally 1.0µF will hold the roll-over error to 0.5
count in this instance.
Oscillator Components
For all ranges of frequency a 100kΩ resistor is recom-
mended and the capacitor is selected from the equation
f0.45
RC For48kHzClock(3Readings/second),=
C 100pF=
Reference Voltage
The analog input required to generate full-scale output (2000
counts) is: VlN = 2VREF. Thus, for the 200mV and 2V scale,
VREF should equal 100mV and 1V, respectively. However, in
many applications where the A/D is connected to a
transducer, there will exist a scale factor other than unity
between the input voltage and the digital reading. For
instance, in a weighing system, the designer might like to
have a full-scale reading when the voltage from the
transducer is 0.662V. Instead of dividing the input down to
200mV, the designer should use the input voltage directly
and select VREF = 0.341V. Suitable values for integrating
resistor and capacitor would be 1 20kΩ and 0.22µF. This
makes the system slightly quieter and also avoids a divider
network on the input. The ICL7107 with ±5V supplies can
accept input signals up to ±4V. Another advantage of this
system occurs when a digital reading of zero is desired for
VIN ≠ 0. Temperature and weighing systems with a variable
fare are examples. This offset reading can be conveniently
generated by connecting the voltage transducer between IN
HI and COMMON and the variable (or fixed) offset voltage
between COMMON and IN LO.
ICL7107 Power Supplies
The ICL7107 is designed to work from ±5V supplies.
However, if a negative supply is not available, it can be
generated from the clock output with 2 diodes, 2 capacitors,
and an inexpensive l.C. Figure 10 shows this application.
See ICL7660 data sheet for an alternative.
In fact, in selected applications no negative supply is
required. The conditions to use a single +5V supply are:
1. The input signal can be referenced to the center of the
common mode range of the converter.
2. The signal is less than ±1.5V.
3. An external reference is used.
FIGURE 10. GENERATING NEGATIVE SUPPLY FROM +5V
ICL7107
V+
OSC 1
V-
OSC 2
OSC 3
GND
V+
V- = 3.3V
0.047
µF
10
µF
+
-
IN914
IN914
CD4009
2-42
ICL7106, ICL7107
Typical Applications
FIGURE 11. ICL7106 USING THE INTERNAL REFERENCE FIGURE 12. ICL7107 USING THE INTERNAL REFERENCE
28
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27
26
25
24
23
22
21
OSC 1
OSC 2
OSC 3
TEST
REF HI
REF LO
CREF
CREF
COMMON
IN HI
IN LO
A-Z
BUFF
INT
V -
G2
C3
A3
G3
BP
100pF
TO PIN 1
SET VREF
= 100mV
0.1µF
0.01µF
1MΩ
100KΩ
1KΩ22KΩ
IN
+
-
9V
47KΩ
0.22µF
0.47µF
TO BACKPLANE
TO DISPLAY
Values shown are for 200mV full-scale, 3 readings/sec., floating
supply voltage (9V battery). Values shown are for 200mV full-scale, 3 readings/sec. IN LO may
be tied to either COMMON for inputs floating with respect to
supplies, or GND for single ended inputs. (See discussion under
Analog COMMON.)
28
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37
36
35
34
33
32
31
30
29
27
26
25
24
23
22
21
OSC 1
OSC 2
OSC 3
TEST
REF HI
REF LO
CREF
CREF
COMMON
IN HI
IN LO
A-Z
BUFF
INT
V -
G2
C3
A3
G3
GND
100pF
TO PIN 1
SET VREF
= 100mV
0.1µF
0.01µF
1MΩ
100KΩ
1KΩ22KΩ
IN
+
-
47KΩ
0.22µF
0.47µF
TO DISPLAY
+5V
-5V
Typical Applications
The ICL7106 and ICL7107 may be used in a wide variety of
configurations. The circuits which follow show some of the
possibilities, and serve to illustrate the exceptional versatility
of these A/D converters.
The following application notes contain very useful
information on understanding and applying this part and are
available from Harris semiconductor.
Application Notes
A016 “Selecting A/D Converters”
A017 “The Integrating A/D Converter”
A018 “Do’s and Don’ts of Applying A/D Converters”
A023 “Low Cost Digital Panel Meter Designs”
A032 “Understanding the Auto-Zero and Common Mode
Performance of the ICL7106/7/9 Family”
A046 “Building a Battery-Operated Auto Ranging DVM with
the ICL7106”
A052 “T ips for Using Single Chip 31/2 Digit A/D Converters”
2-43
ICL7106, ICL7107
FIGURE 13. ICL7107 WITH AN EXTERNAL BAND-GAP
REFERENCE (1.2V TYPE) FIGURE 14. ICL7107 WITH ZENER DIODE REFERENCE
FIGURE 15. ICL7106 AND ICL7107: RECOMMENDED COMPO-
NENT VALUES FOR 2.0V FULL-SCALE FIGURE 16. ICL7107 OPERATED FROM SINGLE +5V
Typical Applications
(Continued)
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31
30
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26
25
24
23
22
21
OSC 1
OSC 2
OSC 3
TEST
REF HI
REF LO
CREF
CREF
COMMON
IN HI
IN LO
A-Z
BUFF
INT
V-
G2
C3
A3
G3
GND
100pF
TO PIN 1
SET VREF
= 100mV
0.1µF
0.01µF
1MΩ
100KΩ
1KΩ10KΩ
IN
+
47KΩ
0.47µF
TO DISPLAY
IN LO is tied to supply COMMON establishing the correct common
mode voltage. If COMMON is not shorted to GND, the input voltage
may float with respect to the power supply and COMMON acts as a
pre-regulator for the reference. If COMMON is shorted to GND, the
input is single ended (referred to supply GND) and the pre-regulator
is overridden.
10KΩ
1.2V (ICL8069)
V -
V+
-
0.22µF
Since low TC zeners have breakdown voltages ~ 6.8V, diode must
be plasced across the total supply (10V). As in the case of Figure
14, IN LO may be tied to either COMMON or GND
28
40
39
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34
33
32
31
30
29
27
26
25
24
23
22
21
OSC 1
OSC 2
OSC 3
TEST
REF HI
REF LO
CREF
CREF
COMMON
IN HI
IN LO
A-Z
BUFF
INT
V -
G2
C3
A3
G3
GND
100pF
TO PIN 1
SET VREF
= 100mV
0.1µF
0.01µF
1MΩ
100KΩ
1KΩ100KΩ
IN
+
-
47KΩ
0.22µF
0.47µF
TO DISPLAY
+5V
-5V
6.8V
28
40
39
38
37
36
35
34
33
32
31
30
29
27
26
25
24
23
22
21
OSC 1
OSC 2
OSC 3
TEST
REF HI
REF LO
CREF
CREF
COMMON
IN HI
IN LO
A-Z
BUFF
INT
V -
G2
C3
A3
G3
BP/GND
100pF
TO PIN 1
SET VREF
= 100mV
0.1µF
0.01µF
1MΩ
100KΩ
25KΩ24KΩ
IN
+
-
470KΩ
0.22µF
0.047µF
TO DISPLAY
V+
V-
28
40
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37
36
35
34
33
32
31
30
29
27
26
25
24
23
22
21
OSC 1
OSC 2
OSC 3
TEST
REF HI
REF LO
CREF
CREF
COMMON
IN HI
IN LO
A-Z
BUFF
INT
V -
G2
C3
A3
G3
GND
100pF
TO PIN 1
SET VREF
= 100mV
0.1µF
0.01µF
1MΩ
100kΩ
1KΩ10KΩ
IN
+
-
47KΩ
0.22µF
0.47µF
TO DISPLAY
An external reference must be used in this application, since the
voltage between V+ and V- is insufficient for correct operation of the
internal reference.
15KΩ
1.2V (ICL8069)
+5V
2-44
ICL7106, ICL7107
FIGURE 17. ICL7107 MEASUREING RATIOMETRIC VALUES OF
QUAD LOAD CELL FIGURE 18. ICL7106 USED AS A DIGITAL CENTIGRADE
THERMOMETER
FIGURE 19. CIRCUIT FOR DEVELOPING UNDERRANGE AND
OVERRANGE SIGNAL FROM ICL7106 OUTPUTS FIGURE 20. CIRCUIT FOR DEVELOPING UNDERRANGE AND
OVERRANGE SIGNALS FROM ICL7107 OUTPUT
Typical Applications
(Continued)
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31
30
29
27
26
25
24
23
22
21
OSC 1
OSC 2
OSC 3
TEST
REF HI
REF LO
CREF
CREF
COMMON
IN HI
IN LO
A-Z
BUFF
INT
V -
G2
C3
A3
G3
GND
100pF
TO PIN 1
0.1µF
100KΩ
0.47µF
TO DISPLAY
The resistor values within the bridge are determined by the desired
sensitivity.
V+
0.22µF
47KΩ28
40
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38
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36
35
34
33
32
31
30
29
27
26
25
24
23
22
21
OSC 1
OSC 2
OSC 3
TEST
REF HI
REF LO
CREF
CREF
COMMON
IN HI
IN LO
A-Z
BUFF
INT
V -
G2
C3
A3
G3
BP
100pF
TO PIN 1
0.1µF
0.01µF
100KΩ
100kΩ1MΩ
9V
47KΩ
0.22µF
0.47µF
TO BACKPLANE
TO DISPLAY
A silicon diode-connected transistor has a temperature coefficient of
about -2mV/oC. Calibration is achieved by placing the sensing
transistor in ice water and adjusting the zeroing potentiometer for a
000.0 reading. The sensor should then be placed in boiling water
and the scale-factor potentiometer adjusted for a 100.0 reading.
SCALE
FACTOR
ADJUST
100kΩ220kΩ
22KΩ
SILICON NPN
MPS 3704 OR
SIMILAR
ZERO
ADJUST
13
1
2
3
4
5
6
7
8
9
10
11
12
14
15
16
17
18
19
20
V+
D1
C1
B1
A1
F1
G1
E1
D2
C2
B2
A2
F2
E2
D3
B3
F3
E3
AB4
POL
28
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39
38
37
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33
32
31
30
29
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26
25
24
23
22
21
OSC 1
OSC 2
OSC 3
TEST
REF HI
REF LO
CREF
CREF
COMMON
IN HI
IN LO
A-Z
BUFF
INT
V-
G2
C3
A3
G3
BP
O /RANGE
U /RANGE
CD4023 OR
74C10 CD4077
TO LOGIC
VCC
V+
TO
LOGIC
V-
GND
O /RANGE
U /RANGE
CD4023 OR
74C10
TO LOGIC
VCC
+5V
V-
33KΩ
The LM339 is required to
ensure logic compatibility
with heavy display loading. 13
1
2
3
4
5
6
7
8
9
10
11
12
14
15
16
17
18
19
20
V+
D1
C1
B1
A1
F1
G1
E1
D2
C2
B2
A2
F2
E2
D3
B3
F3
E3
AB4
POL
28
40
39
38
37
36
35
34
33
32
31
30
29
27
26
25
24
23
22
21
OSC 1
OSC 2
OSC 3
TEST
REF HI
REF LO
CREF
CREF
COMMON
IN HI
IN LO
A-Z
BUFF
INT
V-
G2
C3
A3
G3
BP
12KΩ
+
-
+
-
+
-
+
-
2-45
ICL7106, ICL7107
FIGURE 21. AC TO DC CONVERTER WITH ICL7106
FIGURE 22. DISPLAY BUFFERING FOR INCREASED DRIVE CURRENT
Typical Applications
(Continued)
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23
22
21
OSC 1
OSC 2
OSC 3
TEST
REF HI
REF LO
CREF
CREF
COMMON
IN HI
IN LO
A-Z
BUFF
INT
V-
G2
C3
A3
G3
BP
100pF
TO PIN 1
0.1µF
100kΩ
1KΩ22KΩ
47KΩ
0.22µF
0.47µF
TO BACKPLANE
TO DISPLAY
Test is used as a common-mode reference level to ensure compatibility with most op amps.
10µF
9V
10µF
470KΩ
1µF
4.3KΩ
100pF
(FOR OPTIMUM BANDWIDTH)
1µF
10KΩ10KΩ
1N914
1µF
0.22µF
5µFCA3140
2.2MΩ
+
-
100kΩ
AC IN
SCALE FACTOR ADJUST
(VREF = 100mV FOR AC TO RMS)
ICL7107 130Ω
130Ω
130Ω
LED
SEGMENTS
+5V
DM7407