TPA0211 2-W MONO AUDIO POWER AMPLIFIER SLOS275D - JANUARY 2000 - REVISED NOVEMBER 2002 D Ideal for Wireless Communicators, D D D D D D D D DGN PACKAGE (TOP VIEW) Notebook PCs, PDAs, and Other Small Portable Audio Devices 2 W Into 4 From 5-V Supply 0.6 W Into 4 From 3-V Supply Wide Power Supply Compatibility 3 V to 5 V Low Supply Current - 4 mA Typical at 5 V - 4 mA Typical at 3 V Shutdown Control . . . 1 A Typical Shutdown Pin Is TTL Compatible -40C to 85C Operating Temperature Range Space-Saving, Thermally-Enhanced MSOP Packaging IN SHUTDOWN VDD BYPASS 1 8 2 7 3 6 4 5 VO- GND SE/BTL VO+ description The TPA0211 is a 2-W mono bridge-tied-load (BTL) amplifier designed to drive speakers with as low as 4- impedance. The device is ideal for small wireless communicators, notebook PCs, PDAs, anyplace a mono speaker and stereo headphones are required. From a 5-V supply, the TPA0211 can deliver 2 W of power into a 4- speaker. The gain of the input stage is set by the user-selected input resistor and a 50-k internal feedback resistor (AV = - RF/RI). The power stage is internally configured with a gain of -1.25 V/V in SE mode, and -2.5 V/V in BTL mode. Thus, the overall gain of the amplifier is -62.5 k/ RI in SE mode and -125 k/RI in BTL mode. The input terminals are high-impedance CMOS inputs, and can be used as summing nodes. The TPA0211 is available in the 8-pin thermally-enhanced MSOP package (DGN) and operates over an ambient temperature range of -40C to 85C. AVAILABLE OPTIONS TA PACKAGED DEVICES MSOP (DGN) MSOP SYMBOLIZATION - 40C to 85C TPA0211DGN AEG The DGN package are available taped and reeled. To order a taped and reeled part, add the suffix R to the part number (e.g., TPA0211DGNR). Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of Texas Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet. Copyright 2002, Texas Instruments Incorporated PRODUCTION DATA information is current as of publication date. Products conform to specifications per the terms of Texas Instruments standard warranty. Production processing does not necessarily include testing of all parameters. POST OFFICE BOX 655303 * DALLAS, TEXAS 75265 1 TPA0211 2-W MONO AUDIO POWER AMPLIFIER SLOS275D - JANUARY 2000 - REVISED NOVEMBER 2002 functional block diagram CB 4 BYPASS VDD 3 VDD GND 7 BYPASS VDD 50 k 1.25*R Audio Input Ci RI 1 IN 100 k R - CC - VO+ + 5 + BYPASS 100 k BYPASS 1 k 50 k SE/BTL Control SE/BTL 6 VO- 8 50 k 1.25*R - R - + + BYPASS BYPASS From System Control 2 SHUTDOWN Shutdown and Depop Circuitry Terminal Functions TERMINAL NAME NO. I/O DESCRIPTION I BYPASS is the tap to the voltage divider for internal mid-supply bias. This terminal should be connected to a 0.1-F to 1-F capacitor. BYPASS 4 GND 7 IN 1 I IN is the audio input terminal. SE/BTL 6 I When SE/BTL is held low, the TPA0211 is in BTL mode. When SE/BTL is held high, the TPA0211 is in SE mode. SHUTDOWN 2 I SHUTDOWN places the entire device in shutdown mode when held low. TTL compatible input. VDD VO+ 3 5 O VDD is the supply voltage terminal. VO+ is the positive output for BTL and SE modes. VO- 8 O VO- is the negative output in BTL mode and a high-impedance output in SE mode. 2 GND is the ground connection. POST OFFICE BOX 655303 * DALLAS, TEXAS 75265 TPA0211 2-W MONO AUDIO POWER AMPLIFIER SLOS275D - JANUARY 2000 - REVISED NOVEMBER 2002 absolute maximum ratings over operating free-air temperature range (unless otherwise noted) Supply voltage, VDD . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 6 V Input voltage range, VI . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . -0.3 V to VDD +0.3 V Continuous total power dissipation . . . . . . . . . . . . . . . . . . . . . internally limited (see Dissipation Rating Table) Operating free-air temperature range, TA . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . - 40C to 85C Operating junction temperature range, TJ . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . - 40C to 150C Storage temperature range, Tstg . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . -65C to 150C Lead temperature 1,6 mm (1/16 inch) from case for 10 seconds . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 260C Stresses beyond those listed under "absolute maximum ratings" may cause permanent damage to the device. These are stress ratings only, and functional operation of the device at these or any other conditions beyond those indicated under "recommended operating conditions" is not implied. Exposure to absolute-maximum-rated conditions for extended periods may affect device reliability. DISSIPATION RATING TABLE PACKAGE DGN TA 25C 2.14 W DERATING FACTOR 17.1 mW/C TA = 70C 1.37 W TA = 85C 1.11 W See the Texas Instruments document, PowerPAD Thermally Enhanced Package Application Report (SLMA002), for more information on the PowerPAD package. The thermal data was measured on a PCB layout based on the information in the section entitled Texas Instruments Recommended Board for PowerPAD on page 33 of that document. recommended operating conditions AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA Supply voltage, VDD High-level High level in input ut voltage, VIH VDD = 3 V VDD = 5 V SE/BTL MAX 2.5 5.5 4.5 V V 2 VDD = 3 V VDD = 5 V SE/BTL UNIT 2.7 SHUTDOWN Low-level input Low level in ut voltage, VIL MIN 1.65 2.75 V AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA SHUTDOWN 0.8 Operating free-air temperature, TA - 40 85 C electrical characteristics at specified free-air temperature, VDD = 3 V, TA = 25C (unless otherwise noted) AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAA AAAAAAAAA AAAAAAAAAAAAAA AAA AAA AAA AAA AAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAA AAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAA AAAA AAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAA AAAAAA AAAAAA AAAAAA AAA AAAA AAAAAAAAA PARAMETER TEST CONDITIONS Output offset voltage (measured differentially) SE/BTL = 0 V, SHUTDOWN = 2 V, RL = 8 , Inputs floating IDD(BTL) IDD(SE) Supply current, BTL mode SE/BTL = 1.375 V, SHUTDOWN = 2 V, VDD = 2.5 V Supply current, SE mode SE/BTL = 2.25 V, SHUTDOWN = 2 V, VDD = 2.5 V IDD(SD) Supply current, shutdown mode SHUTDOWN = 0 V, SE/BTL = 3 V |IIH| High level input current High-level |IIL| Low level input current Low-level RF Feedback resistor |VOO| SHUTDOWN SE/BTL SHUTDOWN SE/BTL MIN TYP MAX 30 mV 4 6 mA 2 4 mA 1 10 A VDD = 3.3 V, VI = VDD VDD = 3.3 V, VI = VDD 1 VDD = 3.3 V, VI = 0 V VDD = 3.3 V, VI = 0 V 1 VDD = 2.5 V, SHUTDOWN = 2 V, SE/BTL = 0 V, RL = 4 1 1 45 UNIT 50 60 A A A A k PowerPAD is a trademark of Texas Instruments. POST OFFICE BOX 655303 * DALLAS, TEXAS 75265 3 TPA0211 2-W MONO AUDIO POWER AMPLIFIER SLOS275D - JANUARY 2000 - REVISED NOVEMBER 2002 operating characteristics, VDD = 3 V, TA = 25C, RL = 4 AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA PARAMETER PO Output power THD + N Total harmonic distortion plus noise BOM Maximum output power bandwidth SNR Signal-to-noise ratio Vn Output noise voltage TEST CONDITIONS MIN TYP THD = 1%, BTL mode, f = 1 kHz 660 THD = 0.1%, SE mode, f = 1 kHz, RL = 32 33 PO = 500 mW, Gain = 2, f = 20 Hz to 20 kHz CB = 0.47 F, f = 20 Hz to 20 kHz MAX UNIT mW 0.3% THD = 2% 20 kHz 88 dB BTL mode, RL = 8 , AV= 8 dB 65 SE mode, RL = 32 , AV= 2 dB 25 VRMS electrical characteristics at specified free-air temperature, VDD = 5 V, TA = 25C (unless otherwise noted) AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA AAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAAA PARAMETER TEST CONDITIONS MIN TYP Output offset voltage (measured differentially) SE/BTL = 0 V, SHUTDOWN = 2 V, RL = 8 , Inputs floating IDD(BTL) IDD(SE) Supply current, BTL mode SE/BTL = 2.75 V, SHUTDOWN = VDD 4 Supply current, SE mode SE/BTL = 4.5 V, SHUTDOWN = VDD IDD(SD) Supply current, shutdown mode SE/BTL = 5 V, SHUTDOWN = 0 V |IIH| High level input current High-level |IIL| Low-level input current |VOO| MAX UNIT 30 mV 6 mA 2 4 mA 1 10 A SHUTDOWN VDD = 5.5 V, VI = VDD 1 SE/BTL VDD = 5.5 V, VI = VDD 1 SHUTDOWN VDD = 5.5 V, VI = 0 V 1 SE/BTL VDD = 5.5 V, VI = 0 V 1 A A operating characteristics, VDD = 5 V, TA = 25C, RL = 4 PARAMETER TEST CONDITIONS MAX UNIT f = 1 kHz 2 W THD = 0.1%, SE mode, f = 1 kHz, RL = 32 92 mW Output power THD + N BOM Total harmonic distortion plus noise PO = 1.5 W, Maximum output power bandwidth Gain = 2.5, SNR Signal-to-noise ratio Output noise voltage TYP BTL mode, PO Vn MIN THD = 1%, CB = 0.47 F, f = 20 Hz to 20 kHz f = 20 Hz to 20 kHz 0.2% THD = 2% 20 kHz 93 dB BTL mode, RL = 8 , AV= 8 dB 65 SE mode, RL = 32 , AV= 2 dB 25 VRMS TYPICAL CHARACTERISTICS Table of Graphs FIGURE IDD PO Supply ripple rejection ratio vs Frequency Supply current vs Supply voltage 3 vs Supply voltage 4, 5 Output power vs Load resistance THD+N Total harmonic distortion plus noise Vn Output noise voltage vs Frequency vs Output power vs Frequency Closed loop gain and phase 4 1, 2 6, 7 8, 9, 10, 11 12, 13, 14, 15, 16, 17 18, 19 20, 21 POST OFFICE BOX 655303 * DALLAS, TEXAS 75265 TPA0211 2-W MONO AUDIO POWER AMPLIFIER SLOS275D - JANUARY 2000 - REVISED NOVEMBER 2002 TYPICAL CHARACTERISTICS SUPPLY RIPPLE REJECTION RATIO vs FREQUENCY SUPPLY RIPPLE REJECTION RATIO vs FREQUENCY 0 0 RL = 8 , CB = 1 ,F Mode = BTL -20 RL = 32 , CB = 1 F, Mode = SE -10 Supply Ripple Rejection Ratio - dB Supply Ripple Rejection Ratio - dB -10 -30 -40 -50 -60 -70 -80 -90 -20 -30 -40 -50 -60 -70 -80 -90 -100 20 50 100 200 500 1 k 2 k -100 5 k 10 k 20 k 20 50 f - Frequency - Hz 100 200 Figure 1 OUTPUT POWER vs SUPPLY VOLTAGE 4 3 THD+N = 1%, f = 1 kHz, Mode = BTL, AV = 8 dB 3.5 2.5 TA = 125 C 3 PO - Output Power - W I DD - Supply Current - mA 5 k 10 k 20 k Figure 2 SUPPLY CURRENT vs SUPPLY VOLTAGE TA = 25 C 2.5 2 TA = -40 C 1.5 SHUTDOWN = VDD, VDD From Low to High, Mode = SE, RL = Open, Temperature From Hot to Cold 1 0.5 0 2.5 500 1 k 2 k f - Frequency - Hz 3 3.5 4 4.5 VDD - Supply Voltage - V 5 RL = 4 2 RL = 8 1.5 1 0.5 5.5 0 3 3.5 Figure 3 4 4.5 5 VDD - Supply Voltage - V 5.5 Figure 4 POST OFFICE BOX 655303 * DALLAS, TEXAS 75265 5 TPA0211 2-W MONO AUDIO POWER AMPLIFIER SLOS275D - JANUARY 2000 - REVISED NOVEMBER 2002 TYPICAL CHARACTERISTICS OUTPUT POWER vs LOAD RESISTANCE OUTPUT POWER vs SUPPLY VOLTAGE 2.5 500 THD+N = 1%, f = 1 kHz, Mode = SE, AV = 2 dB 2 PO - Output Power - W PO - Output Power - mW 400 THD+N = 1%, f = 1 kHz, Mode = BTL, AV = 8 dB RL = 8 300 200 1.5 VDD = 5 V 1 RL = 32 100 0.5 0 0 VDD = 3 V 3 3.5 4 4.5 5 VDD - Supply Voltage - V 5.5 0 10 Figure 6 OUTPUT POWER vs LOAD RESISTANCE 700 THD+N = 1%, f = 1 kHz, Mode = SE, AV = 2 dB 600 PO - Output Power - mW 30 500 400 300 VDD = 5 V 200 100 VDD = 3 V 0 0 10 20 30 40 50 RL - Load Resistance - Figure 7 POST OFFICE BOX 655303 40 50 RL - Load Resistance - Figure 5 6 20 * DALLAS, TEXAS 75265 60 60 TPA0211 2-W MONO AUDIO POWER AMPLIFIER SLOS275D - JANUARY 2000 - REVISED NOVEMBER 2002 TYPICAL CHARACTERISTICS 10 VDD = 3 V, PO = 250 mW, RL = 8 , Mode = BTL 5 2 1 0.5 0.2 0.1 AV = 20 dB 0.05 0.02 AV = 8 dB 0.01 0.005 0.002 0.001 20 50 100 200 500 1 k 2 k TOTAL HARMONIC DISTORTION PLUS NOISE vs FREQUENCY THD+N - Total Harmonic Distortion Plus Noise - % THD+N - Total Harmonic Distortion Plus Noise - % TOTAL HARMONIC DISTORTION PLUS NOISE vs FREQUENCY 5 k 10 k 20 k 10 VDD = 5 V, PO = 1 W, RL = 8 , Mode = BTL 5 2 1 0.5 0.2 0.1 AV = 20 dB 0.05 0.02 0.01 AV = 8 dB 0.005 0.002 0.001 20 50 100 200 f - Frequency - Hz Figure 8 VDD = 3 V, PO = 25 mW, RL = 32 , Mode = SE 1 0.5 0.2 0.1 AV = 14 dB 0.05 0.02 0.01 AV = 2 dB 0.005 0.002 0.001 20 50 TOTAL HARMONIC DISTORTION PLUS NOISE vs FREQUENCY THD+N - Total Harmonic Distortion Plus Noise - % THD+N - Total Harmonic Distortion Plus Noise - % 10 2 100 200 500 1 k 2 k 5 k 10 k 20 k Figure 9 TOTAL HARMONIC DISTORTION PLUS NOISE vs FREQUENCY 5 500 1 k 2 k f - Frequency - Hz 5 k 10 k 20 k 10 VDD = 5 V, PO = 75 mW, RL = 32 , Mode = SE 5 2 1 0.5 0.2 0.1 AV = 14 dB 0.05 0.02 0.01 AV = 2 dB 0.005 0.002 0.001 20 50 f - Frequency - Hz 100 200 500 1 k 2 k 5 k 10 k 20 k f - Frequency - Hz Figure 10 Figure 11 POST OFFICE BOX 655303 * DALLAS, TEXAS 75265 7 TPA0211 2-W MONO AUDIO POWER AMPLIFIER SLOS275D - JANUARY 2000 - REVISED NOVEMBER 2002 TYPICAL CHARACTERISTICS 10 VDD = 3 V, RL = 4 , Mode = BTL, AV = 8 dB 5 20 kHz 2 1 15 kHz 0.5 1 kHz 0.2 0.1 20 Hz 0.05 0.02 0.01 0.005 0.002 0.001 0.01 0.02 0.05 0.5 1 2 0.1 0.2 PO - Output Power - W 5 TOTAL HARMONIC DISTORTION PLUS NOISE vs OUTPUT POWER THD+N - Total Harmonic Distortion Plus Noise - % THD+N - Total Harmonic Distortion Plus Noise - % TOTAL HARMONIC DISTORTION PLUS NOISE vs OUTPUT POWER 10 10 20 kHz 2 1 0.5 15 kHz 0.2 1 kHz 0.1 0.05 20 Hz 0.02 0.01 0.005 0.002 0.001 0.01 0.02 0.05 Figure 12 VDD = 3 V, RL = 32 , Mode = SE, AV = 2 dB 1 0.5 20 kHz 0.2 0.1 0.05 15 kHz 0.02 20 Hz 0.01 1 kHz 0.005 0.002 0.001 10 10 20 40 PO - Output Power - mW 70 100 10 5 2 1 15 kHz 0.5 0.2 0.1 1 kHz 20 Hz 0.02 0.01 VDD = 5 V, RL = 4 , Mode = BTL, AV = 8 dB 0.005 0.002 0.001 0.01 0.02 0.05 0.5 1 2 0.1 0.2 PO - Output Power - W Figure 15 POST OFFICE BOX 655303 20 kHz 0.05 Figure 14 8 5 TOTAL HARMONIC DISTORTION PLUS NOISE vs OUTPUT POWER THD+N - Total Harmonic Distortion Plus Noise - % THD+N - Total Harmonic Distortion Plus Noise - % 10 2 0.5 1 2 0.1 0.2 PO - Output Power - W Figure 13 TOTAL HARMONIC DISTORTION PLUS NOISE vs OUTPUT POWER 5 VDD = 3 V, RL = 8 , Mode = BTL, AV = 8 dB 5 * DALLAS, TEXAS 75265 5 10 TPA0211 2-W MONO AUDIO POWER AMPLIFIER SLOS275D - JANUARY 2000 - REVISED NOVEMBER 2002 TYPICAL CHARACTERISTICS TOTAL HARMONIC DISTORTION PLUS NOISE vs OUTPUT POWER 10 THD+N - Total Harmonic Distortion Plus Noise - % THD+N - Total Harmonic Distortion Plus Noise - % TOTAL HARMONIC DISTORTION PLUS NOISE vs OUTPUT POWER VDD = 5 V, RL = 8 , Mode = BTL, AV = 8 dB 5 2 1 20 kHz 0.5 0.2 15 kHz 1 kHz 0.1 0.05 20 Hz 0.02 0.01 0.005 0.002 0.001 0.01 0.02 0.05 0.5 1 2 0.1 0.2 PO - Output Power - W 5 10 10 VDD = 5 V, RL = 32 , Mode = SE, AV = 2 dB 5 2 1 0.5 0.2 20 kHz 0.1 0.05 15 kHz 0.02 20 Hz 0.01 1 kHz 0.005 0.002 0.001 0.01 0.02 0.2 0.05 0.1 PO - Output Power - W Figure 16 1 Figure 17 OUTPUT NOISE VOLTAGE vs FREQUENCY OUTPUT NOISE VOLTAGE vs FREQUENCY 1M 1M VDD = 5 V, RL = 8 , Mode = BTL, AV = 8 dB 500 200 Vn - Output Noise Voltage - V RMS Vn - Output Noise Voltage - V RMS 0.5 100 50 20 10 5 2 VDD = 5 V, RL = 32 , Mode = SE, AV = 2 dB 500 200 100 50 20 10 5 2 1 20 50 100 200 500 1 k 2 k f - Frequency - Hz 5 k 10 k 20 k 1 20 50 Figure 18 100 200 500 1 k 2 k f - Frequency - Hz 5 k 10 k 20 k Figure 19 POST OFFICE BOX 655303 * DALLAS, TEXAS 75265 9 TPA0211 2-W MONO AUDIO POWER AMPLIFIER SLOS275D - JANUARY 2000 - REVISED NOVEMBER 2002 TYPICAL CHARACTERISTICS CLOSED LOOP RESPONSE 180 30 Gain - dB 10 135 Gain 90 0 45 Phase -10 0 -20 -45 -30 -90 -40 -135 -50 10 Phase 20 VDD = 5 V, RL = 4 , Mode = BTL, AV = 8 dB -180 100 1k 10k 100k 1M f - Frequency - Hz Figure 20 CLOSED LOOP RESPONSE 30 Gain - dB 10 135 Gain 90 0 45 Phase -10 0 -20 -45 -30 -90 -40 -135 -50 10 100 1k 10k 100k f - Frequency - Hz Figure 21 10 POST OFFICE BOX 655303 * DALLAS, TEXAS 75265 -180 1M Phase 20 180 VDD = 5 V, RL = 32 , Mode = SE, AV = 2 dB TPA0211 2-W MONO AUDIO POWER AMPLIFIER SLOS275D - JANUARY 2000 - REVISED NOVEMBER 2002 APPLICATION INFORMATION gain setting via input resistance The gain of the input stage is set by the user-selected input resistor and a 50-k internal feedback resistor. However, the power stage is internally configured with a gain of -1.25 V/V in SE mode, and -2.5 V/V in BTL mode. Thus, the feedback resistor (RF) is effectively 62.5 k in SE mode and 125 k in BTL mode. Therefore, the overall gain can be calculated using equations (1) and (2). A + -125 kW V R I (BTL) A + -62.5 kW V R I (SE) (1) (2) The -3 dB frequency can be calculated using equation 3: -3 dB + 1 2p R C I i (3) If the filter must be more accurate, the value of the capacitor should be increased while the value of the resistor to ground should be decreased. In addition, the order of the filter could be increased. input capacitor, Ci In the typical application an input capacitor, Ci, is required to allow the amplifier to bias the input signal to the proper dc level for optimum operation. In this case, Ci and the input resistance of the amplifier, RI, form a high-pass filter with the corner frequency determined in equation 4. -3 dB f c(highpass) + (4) 1 2 p RI Ci fc The value of Ci is important to consider as it directly affects the bass (low frequency) performance of the circuit. Consider the example where RI is 10 k and the specification calls for a flat bass response down to 40 Hz. Equation 2 is reconfigured as equation 5. 1 C + i 2p R f c I (5) In this example, CI is 0.4 F so one would likely choose a value in the range of 0.47 F to 1 F. A further consideration for this capacitor is the leakage path from the input source through the input network (Ci) and the feedback network to the load. This leakage current creates a dc offset voltage at the input to the amplifier that reduces useful headroom, especially in high gain applications. For this reason a low-leakage tantalum or ceramic capacitor is the best choice. When polarized capacitors are used, the positive side of the capacitor should face the amplifier input in most applications as the dc level there is held at VDD/2, which is likely higher than the source dc level. Note that it is important to confirm the capacitor polarity in the application. POST OFFICE BOX 655303 * DALLAS, TEXAS 75265 11 TPA0211 2-W MONO AUDIO POWER AMPLIFIER SLOS275D - JANUARY 2000 - REVISED NOVEMBER 2002 APPLICATION INFORMATION power supply decoupling, C(S) The TPA0211 is a high-performance CMOS audio amplifier that requires adequate power supply decoupling to ensure the output total harmonic distortion (THD) is as low as possible. Power supply decoupling also prevents oscillations for long lead lengths between the amplifier and the speaker. The optimum decoupling is achieved by using two capacitors of different types that target different types of noise on the power supply leads. For higher frequency transients, spikes, or digital hash on the line, a good low equivalent-series-resistance (ESR) ceramic capacitor, typically 0.1 F placed as close as possible to the device VDD lead, works best. For filtering lower-frequency noise signals, a larger aluminum electrolytic capacitor of 10 F or greater placed near the audio power amplifier is recommended. midrail bypass capacitor, C(BYP) The midrail bypass capacitor, C(BYP), is the most critical capacitor and serves several important functions. During start-up or recovery from shutdown mode, C(BYP) determines the rate at which the amplifier starts up. The second function is to reduce noise produced by the power supply caused by coupling into the output drive signal. This noise is from the midrail generation circuit internal to the amplifier, which appears as degraded PSRR and THD+N. Bypass capacitor, C(BYP), values of 0.47 F to 1 F ceramic or tantalum low-ESR capacitors are recommended for the best THD and noise performance. output coupling capacitor, C(C) In the typical single-supply SE configuration, an output coupling capacitor (C(C)) is required to block the dc bias at the output of the amplifier thus preventing dc currents in the load. As with the input coupling capacitor, the output coupling capacitor and impedance of the load form a high-pass filter governed by equation 6. -3 dB f c(high) + 1 2 p R L C (C) (6) fc The main disadvantage, from a performance standpoint, is that the load impedances are typically small, which drives the low-frequency corner higher, degrading the bass response. Large values of C(C) are required to pass low frequencies into the load. Consider the example where a C(C) of 330 F is chosen and loads vary from 3 , 4 , 8 , 32 , 10 k, to 47 k. Table 1 summarizes the frequency response characteristics of each configuration. 12 POST OFFICE BOX 655303 * DALLAS, TEXAS 75265 TPA0211 2-W MONO AUDIO POWER AMPLIFIER SLOS275D - JANUARY 2000 - REVISED NOVEMBER 2002 APPLICATION INFORMATION Table 1. Common Load Impedances vs Low Frequency Output Characteristics in SE Mode RL C(C) 330 F Lowest Frequency 3 4 330 F 120 Hz 161 Hz 8 330 F 60 Hz 32 330 F 15 Hz 10,000 330 F 0.05 Hz 47,000 330 F 0.01 Hz As Table 1 indicates, most of the bass response is attenuated into a 4- load, an 8- load is adequate, headphone response is good, and drive into line level inputs (a home stereo for example) is exceptional. Furthermore, the total amount of ripple current that must flow through the capacitor must be considered when choosing the component. As shown in the application circuit, one coupling capacitor must be in series with the mono loudspeaker for proper operation of the stereo-mono switching circuit. For a 4- load, this capacitor must be able to handle about 700 mA of ripple current for a continuous output power of 2 W. using low-ESR capacitors Low-ESR capacitors are recommended throughout this applications section. A real (as opposed to ideal) capacitor can be modeled simply as a resistor in series with an ideal capacitor. The voltage drop across this resistor minimizes the beneficial effects of the capacitor in the circuit. The lower the equivalent value of this resistance the more the real capacitor behaves like an ideal capacitor. bridged-tied load versus single-ended mode Figure 22 shows a Class-AB audio power amplifier (APA) in a BTL configuration. The TPA0211 BTL amplifier consists of two Class-AB amplifiers driving both ends of the load. There are several potential benefits to this differential drive configuration, but initially consider power to the load. The differential drive to the speaker means that as one side is slewing up, the other side is slewing down, and vice versa. This, in effect, doubles the voltage swing on the load as compared to a ground referenced load. Plugging 2 x VO(PP) into the power equation, where voltage is squared, yields 4x the output power from the same supply rail and load impedance. (See equation 7.) V V (RMS) + V Power + O(PP) 2 2 (7) 2 (RMS) R L POST OFFICE BOX 655303 * DALLAS, TEXAS 75265 13 TPA0211 2-W MONO AUDIO POWER AMPLIFIER SLOS275D - JANUARY 2000 - REVISED NOVEMBER 2002 APPLICATION INFORMATION VDD VO(PP) RL 2x VO(PP) VDD -VO(PP) Figure 22. Bridge-Tied Load Configuration In a typical computer sound channel operating at 5 V, bridging raises the power into an 8- speaker from a singled-ended (SE, ground reference) limit of 250 mW to 1 W. In sound power, that is a 6-dB improvement-- which is loudness that can be heard. In addition to increased power, there are frequency response concerns. Consider the single-supply SE configuration shown in Figure 23. A coupling capacitor is required to block the dc offset voltage from reaching the load. These capacitors can be quite large (approximately 33 F to 1000 F) so they tend to be expensive, heavy, occupy valuable PCB area, and have the additional drawback of limiting low-frequency performance of the system. This frequency limiting effect is due to the high pass filter network created with the speaker impedance and the coupling capacitance and is calculated with equation 8. fc + 14 1 2p R C L (C) (8) POST OFFICE BOX 655303 * DALLAS, TEXAS 75265 TPA0211 2-W MONO AUDIO POWER AMPLIFIER SLOS275D - JANUARY 2000 - REVISED NOVEMBER 2002 APPLICATION INFORMATION bridged-tied load versus single-ended mode (continued) For example, a 68-F capacitor with an 8- speaker would attenuate low frequencies below 293 Hz. The BTL configuration cancels the dc offsets, which eliminates the need for the blocking capacitors. Low-frequency performance is then limited only by the input network and speaker response. Cost and PCB space are also minimized by eliminating the bulky coupling capacitor. VDD -3 dB VO(PP) C(C) RL VO(PP) fc Figure 23. Single-Ended Configuration and Frequency Response Increasing power to the load does carry a penalty of increased internal power dissipation. The increased dissipation is understandable considering that the BTL configuration produces 4x the output power of the SE configuration. Internal dissipation versus output power is discussed further in the crest factor and thermal considerations section. single-ended operation In SE mode (see Figure 22 and Figure 23), the load is driven from one amplifier output (VO+, terminal 5). The amplifier switches to single-ended operation when the SE/BTL terminal is held high. BTL amplifier efficiency Class-AB amplifiers are inefficient. The primary cause of inefficiencies is the voltage drop across the output stage transistors. There are two components of the internal voltage drop. One is the headroom or dc voltage drop that varies inversely to output power. The second component is due to the sinewave nature of the output. The total voltage drop can be calculated by subtracting the RMS value of the output voltage from VDD. The internal voltage drop multiplied by the RMS value of the supply current, IDDrms, determines the internal power dissipation of the amplifier. An easy-to-use equation to calculate efficiency starts out as being equal to the ratio of power from the power supply to the power delivered to the load. To accurately calculate the RMS and average values of power in the load and in the amplifier, the current and voltage waveform shapes must first be understood. See Figure 24. IDD VO IDD(avg) V(LRMS) Figure 24. Voltage and Current Waveforms for BTL Amplifiers POST OFFICE BOX 655303 * DALLAS, TEXAS 75265 15 TPA0211 2-W MONO AUDIO POWER AMPLIFIER SLOS275D - JANUARY 2000 - REVISED NOVEMBER 2002 APPLICATION INFORMATION BTL amplifier efficiency (continued) Although the voltages and currents for SE and BTL are sinusoidal in the load, currents from the supply are very different between SE and BTL configurations. In an SE application the current waveform is a half-wave rectified shape, whereas in BTL it is a full-wave rectified waveform. This means RMS conversion factors are different. Keep in mind that for most of the waveform both the push and pull transistors are not on at the same time, which supports the fact that each amplifier in the BTL device only draws current from the supply for half the waveform. The following equations are the basis for calculating amplifier efficiency. Efficiency of a BTL amplifier + where PL + V LRMS RL 2 PL (9) P SUP 2 V V , and V LRMS + P , therefore, P L + P 2 2 RL and P SUP + V DD I DDavg 1 I DDavg + p and p 0 VP 1 sin(t) dt + p RL VP RL [cos(t)] p 2V P + 0 p RL therefore, P SUP + 2 V DD V P p RL substituting PL and PSUP into equation 9, 2 Efficiency of a BTL amplifier + where VP + VP 2 RL 2 V DD V P p RL + p VP 4 V DD 2 P L RL therefore, h BTL + p 2 PL R L (10) 4 V DD PL = Power devilered to load PSUP = Power drawn from power supply VLRMS = RMS voltage on BTL load RL = Load resistance 16 VP = Peak voltage on BTL load IDDavg = Average current drawn from the power supply VDD = Power supply voltage BTL = Efficiency of a BTL amplifier POST OFFICE BOX 655303 * DALLAS, TEXAS 75265 TPA0211 2-W MONO AUDIO POWER AMPLIFIER SLOS275D - JANUARY 2000 - REVISED NOVEMBER 2002 APPLICATION INFORMATION BTL amplifier efficiency (continued) Table 2 employs equation 10 to calculate efficiencies for four different output power levels. Note that the efficiency of the amplifier is quite low for lower power levels and rises sharply as power to the load is increased resulting in a nearly flat internal power dissipation over the normal operating range. Note that the internal dissipation at full output power is less than in the half power range. Calculating the efficiency for a specific system is the key to proper power supply design. Table 2. Efficiency Vs Output Power in 5-V 8- BTL Systems Output Power (W) Efficiency (%) Peak Voltage (V) Internal Dissipation (W) 0.25 31.4 2.00 0.55 0.50 44.4 2.83 0.62 1.00 62.8 0.59 1.25 70.2 4.00 4.47 0.53 High peak voltages cause the THD to increase. A final point to remember about Class-AB amplifiers (either SE or BTL) is how to manipulate the terms in the efficiency equation to utmost advantage when possible. Note that in equation 10, VDD is in the denominator. This indicates that as VDD goes down, efficiency goes up. crest factor and thermal considerations Class-AB power amplifiers dissipate a significant amount of heat in the package under normal operating conditions. A typical music CD requires 12 dB to 15 dB of dynamic range, or headroom above the average power output, to pass the loudest portions of the signal without distortion. In other words, music typically has a crest factor between 12 dB and 15 dB. When determining the optimal ambient operating temperature, the internal dissipated power at the average output power level must be used.The TPA0211 data sheet shows that when the TPA0211 is operating from a 5-V supply into a 4- speaker 4-W peaks are available. Converting watts to dB: P dB + 10Log PW P ref + 10 Log 4 W + 6 dB 1W (11) Subtracting the headroom restriction to obtain the average listening level without distortion yields: 6 dB - 15 dB = -9 dB (15-dB crest factor) 6 dB - 12 dB = -6 dB (12-dB crest factor) 6 dB - 9 dB = -3 dB (9-dB crest factor) 6 dB - 6 dB = 0 dB (6-dB crest factor) 6 dB - 3 dB = 3 dB (3-dB crest factor) POST OFFICE BOX 655303 * DALLAS, TEXAS 75265 17 TPA0211 2-W MONO AUDIO POWER AMPLIFIER SLOS275D - JANUARY 2000 - REVISED NOVEMBER 2002 APPLICATION INFORMATION crest factor and thermal considerations (continued) Converting dB back into watts: P W + 10 PdB10 + + + + + + P ref (12) 63 mW (18-dB crest factor) 125 mW (15-dB crest factor) 250 mW (9-dB crest factor) 500 mW (6-dB crest factor) 1000 mW (3-dB crest factor) 2000 mW (15-dB crest factor) This is valuable information to consider when attempting to estimate the heat dissipation requirements for the amplifier system. Comparing the absolute worst case, which is 2 W of continuous power output with a 3 dB crest factor, against 12 dB and 15 dB applications drastically affects maximum ambient temperature ratings for the system. Table 3 shows maximum ambient temperatures and TPA0211 internal power dissipation for various output-power levels. Table 3. TPA0211 Power Rating, 5-V, 4-, Mono PEAK OUTPUT POWER (W) AVERAGE OUTPUT POWER POWER DISSIPATION (W) MAXIMUM AMBIENT TEMPERATURE 4 2 W (3-dB crest factor) 1.7 4 1000 mW (6-dB crest factor) 1.6 6C 4 500 mW (9-dB crest factor) 1.4 24C 4 250 mW (12-dB crest factor) 1.1 51C 4 125 mW (15-dB crest factor) 0.8 78C 4 63 mW (18-dB crest factor) 0.6 96C - 3C As a result, this simple formula for calculating PDmax may be used for an 4- application: P Dmax + 2V 2 DD (13) p 2R L However, in the case of a 4- load, the PDmax occurs at a point well above the normal operating power level. The amplifier may therefore be operated at a higher ambient temperature than required by the PDmax formula for a 4- load. The maximum ambient temperature depends on the heat sinking ability of the PCB system. The derating factor for the DGN package is shown in the dissipation rating table. Converting this to JA: JA + 18 1 1 + + 58.48CW 0.0171 Derating Factor POST OFFICE BOX 655303 * DALLAS, TEXAS 75265 (14) TPA0211 2-W MONO AUDIO POWER AMPLIFIER SLOS275D - JANUARY 2000 - REVISED NOVEMBER 2002 APPLICATION INFORMATION crest factor and thermal considerations (continued) To calculate maximum ambient temperatures, first consider that the numbers from the dissipation graphs are per channel so the dissipated power needs to be doubled for two channel operation. Given JA, the maximum allowable junction temperature, and the total internal dissipation, the maximum ambient temperature can be calculated with the following equation. The maximum recommended junction temperature for the TPA0211 is 150C. The internal dissipation figures are taken from the Power Dissipation vs Output Power graphs. T A Max + T J Max * JA P D + 150 * 58.48 (0.8 2) + 56C (15-dB crest factor) (15) NOTE: Internal dissipation of 0.8 W is estimated for a 2-W system with 15-dB crest factor per channel. Table 3 shows that for some applications no airflow is required to keep junction temperatures in the specified range. The TPA0211 is designed with thermal protection that turns the device off when the junction temperature surpasses 150C to prevent damage to the IC. Table 3 was calculated for maximum listening volume without distortion. When the output level is reduced the numbers in the table change significantly. Also, using 8- speakers dramatically increases the thermal performance by increasing amplifier efficiency. SE/BTL (stereo/mono) operation The ability of the TPA0211 to easily switch between mono BTL and stereo SE modes is one of its most important cost saving features. This feature eliminates the requirement for an additional headphone amplifier in applications where an internal speaker is driven in BTL mode but an external headphone must be accommodated. When SE/BTL is held high for SE mode, the VO- output goes into a high impedance state while the VO+ output operates normally. When SE/BTL is held low, the VO- output operates normally, placing the amplifier in BTL mode. POST OFFICE BOX 655303 * DALLAS, TEXAS 75265 19 TPA0211 2-W MONO AUDIO POWER AMPLIFIER SLOS275D - JANUARY 2000 - REVISED NOVEMBER 2002 APPLICATION INFORMATION ST/BTL operation (continued) CB 4 BYPASS VDD 3 VDD GND 7 BYPASS VDD 50 k 1.25*R Audio Input Ci RI 1 IN 100 k R - CC - VO+ + 5 + BYPASS 100 k BYPASS 1 k 50 k SE/BTL Control SE/BTL 6 VO- 8 50 k 1.25*R - R - + + BYPASS BYPASS From System Control 2 SHUTDOWN Shutdown and Depop Circuitry Figure 25. TPA0211 Resistor Divider Network Circuit Using a readily available 1/8-in. (3,5 mm) mono headphone jack, the control switch is closed when no plug is inserted. When closed, the 100-k/1-k divider pulls the SE/BTL input low. When a plug is inserted, the 1-k resistor is disconnected and the SE/BTL input is pulled high. 20 POST OFFICE BOX 655303 * DALLAS, TEXAS 75265 PACKAGE OPTION ADDENDUM www.ti.com 18-Apr-2006 PACKAGING INFORMATION Orderable Device Status (1) Package Type Package Drawing Pins Package Eco Plan (2) Qty TPA0211DGN ACTIVE MSOPPower PAD DGN 8 80 Green (RoHS & no Sb/Br) CU NIPDAU Level-1-260C-UNLIM TPA0211DGNG4 ACTIVE MSOPPower PAD DGN 8 80 Green (RoHS & no Sb/Br) CU NIPDAU Level-1-260C-UNLIM TPA0211DGNR ACTIVE MSOPPower PAD DGN 8 2500 Green (RoHS & no Sb/Br) CU NIPDAU Level-1-260C-UNLIM Lead/Ball Finish MSL Peak Temp (3) (1) The marketing status values are defined as follows: ACTIVE: Product device recommended for new designs. LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect. NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design. PREVIEW: Device has been announced but is not in production. Samples may or may not be available. OBSOLETE: TI has discontinued the production of the device. (2) Eco Plan - The planned eco-friendly classification: Pb-Free (RoHS), Pb-Free (RoHS Exempt), or Green (RoHS & no Sb/Br) - please check http://www.ti.com/productcontent for the latest availability information and additional product content details. TBD: The Pb-Free/Green conversion plan has not been defined. Pb-Free (RoHS): TI's terms "Lead-Free" or "Pb-Free" mean semiconductor products that are compatible with the current RoHS requirements for all 6 substances, including the requirement that lead not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, TI Pb-Free products are suitable for use in specified lead-free processes. Pb-Free (RoHS Exempt): This component has a RoHS exemption for either 1) lead-based flip-chip solder bumps used between the die and package, or 2) lead-based die adhesive used between the die and leadframe. The component is otherwise considered Pb-Free (RoHS compatible) as defined above. Green (RoHS & no Sb/Br): TI defines "Green" to mean Pb-Free (RoHS compatible), and free of Bromine (Br) and Antimony (Sb) based flame retardants (Br or Sb do not exceed 0.1% by weight in homogeneous material) (3) MSL, Peak Temp. -- The Moisture Sensitivity Level rating according to the JEDEC industry standard classifications, and peak solder temperature. Important Information and Disclaimer:The information provided on this page represents TI's knowledge and belief as of the date that it is provided. TI bases its knowledge and belief on information provided by third parties, and makes no representation or warranty as to the accuracy of such information. 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Addendum-Page 1 PACKAGE MATERIALS INFORMATION www.ti.com 1-Mar-2012 TAPE AND REEL INFORMATION *All dimensions are nominal Device Package Package Pins Type Drawing SPQ Reel Reel A0 Diameter Width (mm) (mm) W1 (mm) B0 (mm) K0 (mm) P1 (mm) W Pin1 (mm) Quadrant TPA0211DGNR MSOPPower PAD DGN 8 2500 330.0 12.4 5.3 3.4 1.4 8.0 12.0 Q1 TPA0211DGNR MSOPPower PAD DGN 8 2500 330.0 12.4 5.3 3.4 1.4 8.0 12.0 Q1 Pack Materials-Page 1 PACKAGE MATERIALS INFORMATION www.ti.com 1-Mar-2012 *All dimensions are nominal Device Package Type Package Drawing Pins SPQ Length (mm) Width (mm) Height (mm) TPA0211DGNR MSOP-PowerPAD DGN 8 2500 364.0 364.0 27.0 TPA0211DGNR MSOP-PowerPAD DGN 8 2500 358.0 335.0 35.0 Pack Materials-Page 2 IMPORTANT NOTICE Texas Instruments Incorporated and its subsidiaries (TI) reserve the right to make corrections, modifications, enhancements, improvements, and other changes to its products and services at any time and to discontinue any product or service without notice. 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