FSDM0565R
11
Functional Description
1.
1. 1.
1. Startup : In previous generations of Fairchild Power
Switches (FPS
TM
) the Vcc pin had an external start-up
resistor to the DC input voltage line. In this generation the
startup resistor is replaced by an internal high voltage current
source. At startup, an internal high voltage current source
supplies the internal bias and charges the external capacitor
(C
vcc
) that is connected to the Vcc pin as illustrated in figure
4. When Vcc reaches 12V, the FPS
TM
begins switching and
the internal high voltage current source is disabled. Then, the
FPS
TM
continues its normal switching operation and the
power is supplied from the auxiliary transformer winding
unless Vcc goes below the stop voltage of 8V.
Figure 4. Internal startup circuit
2. Feedback Control : FS DM0565R employ s curre nt mode
control, as shown in figure 5. An opto-coupler (such as the
H11A817A) and shunt regulator (such as the KA431) are
typically used to implement the feedback network.
Comparing the feedback volta ge with the voltage across the
Rsense resistor plus an offset voltage makes it possible to
control the switching duty cycle. When the reference pin
voltage of the KA431 exceeds the internal r eference voltage
of 2.5V, the H11A817A LED current increases, thus pulling
down the feedback voltage and reducing the duty cycle. This
event typically happens when the input voltage is increased
or the output load is decreased.
2.1 Pulse-by-pulse current limit: Because current mode
control is employed, the peak cur ren t thr ough the Sense FET
is limited by the inv erting input of PWM c omparato r (Vfb *)
as shown in figure 5. Assuming that the 0.9mA current
sourc e flows only thro ugh t he inte rnal r esistor (2.5R +R= 2.8
kΩ), the cathode voltage of diode D2 is about 2.5V. Since D1
is blocked when the feedback voltage (Vfb) exceeds 2.5V,
the max i mu m vo l ta ge of th e cat ho de of D2 i s cla m pe d at thi s
voltage, thus clamping Vfb*. Therefore, the peak value of
the current through the Sense FET is limited.
2.2 Leading edge blanking (LEB) : At the instant the
internal Sense FET is turned on, there usually exists a high
curr ent spike thro ugh the Se nse FET, caused by pri ma r y- side
capacitance and secondary-side rectifier reverse recovery.
Excessive voltage across the Rsense resistor would lead to
incorrect feedback operation in the current mode PWM
control. To counter th is effect, the FPS
TM
employs a leading
edge blanking (LEB) circuit. This circuit inhibits the PWM
comparator for a short time (T
LEB
) after the Sense FET is
turned on.
Figure 5. Pulse width modul ation (PWM) circuit
3. Protection Circuit : The FSDM0565R has several self
protective functions such as over load protection (OLP),
abnormal over current protection (AOCP), over voltage
protection (OVP) and thermal shutdown (TSD). Because
these protection circuits are fully integrated into the IC
without external components, the reliability can be improved
without increasing cost. Once the fault condition occurs,
switching is terminated an d the Sense FET rem ains off. This
causes Vcc to fall. When Vcc reaches the UVLO stop
voltage, 8V, the protection is reset and the internal high
voltage current source charges the Vcc capacitor via th e Vstr
pin. When Vcc reaches the UVLO start voltage,12V, the
FPS
TM
resumes its normal operation. In this manner, the
auto-restart can alternately enable and disable the switching
of the power Sense FET until the fault condition is
eliminated (see figure 6).
8V/12V
3
Vref
Internal
Bias
Vcc 6Vstr
I
start
Vcc good
V
DC
C
Vcc
4
OSC
Vcc Vref
I
delay
I
FB
VSD
R
2.5R
Gate
driver
OLP
D1 D2
+
V
fb
*
-
Vfb
KA431
C
B
Vo
H11A817A
Rsense
SenseFET