ML4831CP - Micro Linear - Datasheet.Directory

GENERAL DESCRIPTION

The ML4831 is a complete solution for a dimmable, high

power factor, high efficiency electronic ballast. Contained

in the ML4831 are controllers for “boost” type power

factor correction as well as for a dimming ballast.

The Power factor circuit uses the average current sensing

method with a gain modulator and over-voltage

protection. This system produces power factors of better

than 0.99 with low input current THD at > 95%

efficiency. Special care has been taken in the design of the

ML4831 to increase system noise immunity by using a

high amplitude oscillator, and a current fed multiplier. An

over-voltage protection comparator inhibits the PFC

section in the event of a lamp out or lamp failure

condition.

The ballast section provides for programmable starting

scenarios with programmable preheat and lamp out-of-

socket interrupt times. The IC controls lamp output

through either frequency modulation using lamp current

feedback.

The ML4831 is designed using Micro Linear‘s Semi-

Standard tile array technology. Customized versions of this

IC, optimized to specific ballast architectures can be made

available. Contact Micro Linear or an authorized

representative for more information. * This product is End Of Life as of July 1, 2000

FEATURES

■Complete Power Factor Correction and Dimming

Ballast Control on one IC

■Low Distortion, High Efficiency Continuous Boost,

Average Current sensing PFC section

■Programmable Start Scenario for Rapid or Instant Start

Lamps

■Lamp Current feedback for Dimming Control

■Variable Frequency dimming and starting

■Programmable Restart for lamp out condition to

reduce ballast heating

■Over-Temperature Shutdown replaces external heat

sensor for safety

■PFC Over-Voltage comparator eliminates output

“runaway” due to load removal

■Large oscillator amplitude and gain modulator

improves noise immunity

BLOCK DIAGRAM

JULY 2000

ML4831*

Electronic Ballast Controller

7R(SET)

OSCILLATOR

8R(T)/C(T)

10 R(X)/C(X) PRE-HEAT

AND INTERRUPT

TIMERS

CONTROL

GATING LOGIC

2IA OUT

4IA+

POWER

FACTOR

CONTROLLER

UNDER-VOLTAGE

AND THERMAL

SHUTDOWN

OUTPUT

DRIVERS

3I(SINE)

1EA OUT

18 EA–/OVP VREF 17

PFC OUT 15

GND 11

VCC 16

PGND 12

OUT B 13

OUT A 14

LFB OUT 6

LAMP F.B. 5

INTERRUPT 9

ML4831

PIN CONFIGURATION

PIN# NAME FUNCTION PIN# NAME FUNCTION

1 EA OUT PFC Error Amplifier output and

compensation node

2 IA OUT Output and compensation node of the

PFC average current transconductance

amplifier.

3 I(SINE) PFC gain modulator input.

4 IA+ Non-inverting input of the PFC

average current transconductance

amplifier and peak current sense point

of the PFC cycle by cycle current limit

comparator.

5 LAMP F.B. Inverting input of an Error Amplifier

used to sense (and regulate) lamp arc

current. Also the input node for

dimming control.

6 LFB OUT Output from the Lamp Current Error

Transconductance Amplifier used for

lamp current loop compensation

7 R(SET) External resistor which sets oscillator

FMAX, and R(X)/C(X) charging current

PIN DESCRIPTION

8 R(T)C(T) Oscillator timing components

9 INTERRUPT Input used for lamp-out detection and

restart. A voltage greater than 7.5 volts

resets the chip and causes a restart

after a programmable interval.

10 R(X)/C(X) Sets the timing for the preheat,

dimming lockout, and interrupt

11 GND Ground

12 P GND Power ground for the IC

13 OUT B Ballast MOSFET drive output

14 OUT A Ballast MOSFET drive output

15 PFC OUT Power Factor MOSFET drive output

16 VCC Positive Supply for the IC

17 VREF Buffered output for the 7.5V voltage

reference

18 EA–/OVP Inverting input to PFC error amplifier

and OVP comparator input

ML4831

18-Pin DIP (P18)

EA OUT

IA OUT

I(SINE)

IA+

LAMP F.B.

LFB OUT

R(SET)

R(T)/C(T)

INTERRUPT

EA–/OVP

REF

VCC

PFC OUT

OUT A

OUT B

P GND

GND

R(X)/C(X)

TOP VIEW

ML4831

ELECTRICAL CHARACTERISTICS

Unless otherwise specified, R(SET) = 31.6kΩ, R(T) = 16.2kΩ, C(T) = 1.5nF, TJ = Junction Operating Temperature Range,

ICC = 25mA

PARAMETER CONDITIONS MIN TYP MAX UNITS

PFC Current Sense Amplifier (Pins 2, 4)

Small Signal Transconductance 130 200 270 µmhos

Input Voltage Range –0.3 3.5 V

Output Low ISINE = 0mA, VPIN1 = 0V,

VPIN4 = –0.3V, RL = ∞0.2 0.4 V

Output High ISINE = 1.5mA, VPIN18/4 = 0V, RL = ∞5.2 5.6 6 V

Source Current ISINE = 1.5mA, VPIN18/4 = 0V, VPIN2 = 5V –0.3 mA

Sink Current ISINE = 0mA, VPIN2 = 0.3V,

VPIN4 = –0.3V, VPIN1 = 0V 0.3 mA

PFC Voltage Feedback Amplifier (Pins 1, 18)/Lamp Current Amplifier (Pins 5, 6)

Input Offset Voltage ±3.0 ±10.0 mV

Input Bias Current –0.3 –1.0 µA

Small Signal Transconductance 50 80 110 µmhos

Input Voltage Range –0.3 3.5 V

Output Low VPIN5/18 = 3V, RL = ∞0.2 0.4 V

Output High VPIN5/18 = 2V, RL = ∞7.2 7.5 V

Source Current VPIN5/18 = 0V, VPIN1/6 = 7V –0.2 mA

Sink Current VPIN5/18 = 5V, VPIN1/6 = 0.3V 0.2 mA

Gain Modulator

Output Voltage ISINE = 100µA, VPIN1 = 3V 40 mV

ISINE = 300µA, VPIN1 = 3V 130 mV

ISINE =100µA, VPIN1 = 6V 112 mV

ISINE = 300µA, VPIN1 = 6V 350 mV

Output Voltage Limit ISINE = 1.5mA, VPIN18 = 0V 865 mV

Offset Voltage ISINE = 0, VPIN18 = 0V 15 mV

ISINE = 150µA, VPIN18 = 3V 15 mV

I(SINE) Input Voltage ISINE = 200µA 0.8 1.4 1.8 V

ABSOLUTE MAXIMUM RATINGS

Absolute maximum ratings are those values beyond which

the device could be permanently damaged. Absolute

maximum ratings are stress ratings only and functional

device operation is not implied.

Supply Current (ICC) ............................................... 75mA

Output Current, Source or Sink (Pins 13, 14, 15)

DC ................................................................... 250mA

Output Energy (capacitive load per cycle) .............. 1.5 mJ

Gain Modulator I(SINE) Input (Pin 3) ..................... 10 mA

Analog Inputs (Pins 5, 9, 18) ............... –0.3V to VCC –2V

Pin 4 input voltage ........................................... –3V to 2V

Maximum Forced Voltage (Pins 1, 6) .......... –0.3V to 7.7V

Maximum Forced Current (Pins 1, 2, 6) ................ ±20mA

Maximum Forced Voltage (Pin 2) .................. –0.3V to 6V

Junction Temperature ............................................. 150°C

Storage Temperature Range ..................... –65°C to 150°C

Lead Temperature (Soldering 10 Sec.)..................... 260°C

Thermal Resistance (θJA)

Plastic DIP–P ................................................... 70°C/W

OPERATING CONDITIONS

Temperature Range

ML4831C .................................................. 0°C to 85°C

ML4831

ELECTRICAL CHARACTERISTICS (Continued)

PARAMETER CONDITIONS MIN TYP MAX UNITS

Oscillator

Initial accuracy TA = 25°C 727680kHz

Voltage stability VCCZ – 3V < VCC <VCCZ – 0.5V 1 %

Temperature stability 2%

Total Variation Line, temperature 69 83 kHz

Ramp Valley to Peak 2.5 V

C(T) Charging Current (FM Modes) VPIN5 = 3V, VPIN8 = 2.5V,

VPIN10 = 0.9V (Preheat) –78 µA

VPIN5 = 3V, VPIN8 = 2.5V,

VPIN10 = Open –156 µA

C(T) Discharge Current VPIN8 = 2.5V 5 mA

Output Drive Deadtime 0.75 µs

Reference Section

Output Voltage TA = 25°C, IO = 1mA 7.4 7.5 7.6 V

Line regulation VCCZ – 3V < VCC < VCCZ – 0.5V 2 10 mV

Load regulation 1mA < IO < 20mA 2 15 mV

Temperature stability 0.4 %

Total Variation Line, load, temp 7.35 7.65 V

Output Noise Voltage 10Hz to 10KHz 50 µV

Long Term Stability TJ = 125°C, 1000 hrs 5 mV

Short Circuit Current VCC < VCCZ – 0.5V, VREF = 0V –40 mA

Preheat and Interrupt Timer (Pin 10) (R(X) = 590KΩ, C(X) = 5.6µF)

Initial Preheat Period 0.8 s

Subsequent Preheat Period 0.7 s

Start Period 2.1 s

Interrupt Period 6.3 s

Pin 10 Charging Current –19 µA

Pin 10 Open Circuit Voltage VCC = 12.3V in UVLO 0.4 0.9 1.1 V

Pin 10 Maximum Voltage 7.0 7.3 7.7 V

Input Bias Current VPIN10 = 1.2V –0.2 µA

Preheat Lower Threshold 1.18 V

Preheat Upper Threshold 3.36 V

Interrupt Recovery Threshold 1.18 V

Start Period End Threshold 6.7 V

Interrupt Input (Pin 9)

Interrupt Threshold 7.35 7.5 7.65 V

Input Bias Current –0.3 –1 µA

ML4831

ELECTRICAL CHARACTERISTICS (Continued)

PARAMETER CONDITIONS MIN TYP MAX UNITS

OVP Comparator (Pin 18)

OVP Threshold 2.6 2.7 2.8 V

Hysteresis 0.25 V

Propagation Delay 500 ns

Outputs

Output Voltage Low IOUT = 20mA 0.4 0.8 V

IOUT = 200mA 2.1 3.0 V

Output Voltage High IOUT = –20mA VCC – 2.5 VCC – 1.9 V

IOUT = –200mA VCC – 3.0 VCC – 2.2 V

Output Voltage Low in UVLO IOUT = 10mA, VCC = 8V 0.8 1.5 V

Output Rise/Fall Time CL = 1000pF 50 ns

Under-Voltage Lockout and Bias Circuits

IC Shunt Voltage (VCCZ)I

CC = 25mA 12.8 13.5 14.2 V

VCCZ Load Regulation 25mA < ICC < 68mA 150 300 mV

VCCZ Total Variation Load, Temp 12.4 14.6 V

Start-up Current VCC ≤ 12.3V 1.3 1.7 mA

Operating Current VCC = VCCZ – 0.5V 15 19 mA

Start-up Threshold VCCZ – 0.5 V

Shutdown Threshold VCCZ – 3.5 V

Shutdown Temperature (TJ) 120 °C

Hysteresis (TJ)30 °C

FUNCTIONAL DESCRIPTION

OVERVIEW

The ML4831 consists of an Average Current controlled

continuous boost Power Factor front end section with a

flexible ballast control section. Start-up and lamp-out retry

timing are controlled by the selection of external timing

components, allowing for control of a wide variety of

different lamp types. The ballast section controls the lamp

power using frequency modulation (FM) with additional

programmability provided to adjust the VCO frequency

range. This allows for the IC to be used with a variety of

different output networks.

POWER FACTOR SECTION

The ML4831 Power Factor section is an average current

sensing boost mode PFC control circuit which is

architecturally similar to that found in the ML4821. For

detailed information on this control architecture, please

refer to Application Note 16 and the ML4821 data sheet.

GAIN MODULATOR

The ML4831 gain modulator provides high immunity to

the disturbances caused by high power switching. The

rectified line input sine wave is converted to a current via

a dropping resistor. In this way, small amounts of ground

noise produce an insignificant effect on the reference to

the PWM comparator.

The output of the gain modulator appears on the positive

terminal of the IA amplifier to form the reference for the

current error amplifier. Please refer to Figure 1.

VISINE VEA V

MUL

≈×−

[]

()( .)

417

(1)

where: I(SINE) is the current in the dropping resistor,

V(EA) is the output of the error amplifier (Pin 1).

The output of the gain modulator is limited to 1.0V.

ML4831

AVERAGE CURRENT AND OUTPUT VOLTAGE

REGULATION

The PWM regulator in the PFC Control section will act to

offset the positive voltage caused by the multiplier output

by producing an offsetting negative voltage on the current

sense resistor at Pin 4. A cycle-by-cycle current limit is

included to protect the MOSFET from high speed current

transients. When the voltage at Pin 4 goes negative by

more than 1V, the PWM cycle is terminated.

For more information on compensating the average

current and boost voltage error amplifier loops, see

ML4821 data sheet.

OVERVOLTAGE PROTECTION AND INHIBIT

The OVP pin serves to protect the power circuit from

being subjected to excessive voltages if the load should

change suddenly (lamp removal). A divider from the high

voltage DC bus sets the OVP trip level. When the voltage

on Pin 18 exceeds 2.75V, the PFC transistors are inhibited.

The ballast section will continue to operate. The OVP

threshold should be set to a level where the power

components are safe to operate, but not so low

as to interfere with the boost voltage regulation loop.

Figure 1. ML4831 Block Diagram

TRANSCONDUCTANCE AMPLIFIERS

The PFC voltage feedback, PFC current sense, and the

loop current amplifiers are all implemented as operational

transconductance amplifiers. They are designed to have

low small signal forward transconductance such that a

large value of load resistor (R1) and a low value ceramic

capacitor (<1µF) can be used for AC coupling (C1) in the

frequency compensation network. The compensation

network shown in Figure 2 will introduce a zero and a

pole at:

fRC fRC

11 12

ππ

(2)

–

2.5V

Figure 2. Compensation Network

7R(SET)

R(X)/C(X)

VCC

REF

GND

IA OUT

IA + –V

MUL

OUT B 13

–

2.5V

REF

–1V

PREHEAT

TIMER

OSC

UNDER-VOLTAGE

AND THERMAL

SHUTDOWN

–

P GND 12

OUT A 14

PFC OUT 15

R(T)/C(T) 8

INTERRUPT 9

LFB OUT 6

LAMP F.B. 5

PWM (PFC)

I(SINE)

EA OUT

EA –/OVP

18 –

2.5V

–

2.75V

OVP

GAIN

MODULATORS

ML4831

Figure 3 shows the output configuration for the

operational transconductance amplifiers.

CURRENT

MIRROR

IN OUT

CURRENT

MIRROR

IN OUT

gmV

io = gmV

IQ + 2

gmV

IQ – 2

Figure 3. Output Configuration

A DC path to ground or VCC at the output of the

transconductance amplifiers will introduce an offset error.

The magnitude of the offset voltage that will appear at the

input is given by VOS = io/gm. For a io of 1uA and a gm

of 0.08 µmhos the input referred offset will be 12.5mV.

Capacitor C1 as shown in Figure 2 is used to block the

DC current to minimize the adverse effect of offsets.

Slew rate enhancement is incorporated into all of the

operational transconductance amplifiers in the ML4831.

This improves the recovery of the circuit in response to

power up and transient conditions. The response to large

signals will be somewhat non-linear as the

transconductance amplifiers change from their low to high

transconductance mode. This is illustrated in Figure 4.

Differential

Linear Slope Region

Figure 4. Transconductance Amplifier Characteristics

BALLAST OUTPUT SECTION

The IC controls output power to the lamps via frequency

modulation with non-overlapping conduction. This means

that both ballast output drivers will be low during the

discharging time tDIS of the oscillator capacitor CT.

OSCILLATOR

The VCO frequency ranges are controlled by the output of

the LFB amplifier (Pin 6). As lamp current decreases, Pin 6

rises in voltage, causing the C(T) charging current to

decrease, thereby causing the oscillator frequency to

decrease. Since the ballast output network attenuates high

frequencies, the power to the lamp will be increased.

–

1.25/3.75

C(T)

REF

CHG

REF

CONTROL

R(T)/C(T)

R(T)

5 mA

CLOCK

C(T)

= 3.75V

= 1.25V

DIS

CHG

Figure 5. Oscillator Block Diagram and Timing

The oscillator frequency is determined by the following

equations:

Ftt

OSC CHG DIS

(3)

and

tRCIn

VIRV

CHG T T REF CH T TL

REF CH T TH

=+−

+−











(4)

ML4831

The oscillator’s minimum frequency is set when ICH = 0

where:

FRC

OSC TT

≅×

051.

(5)

This assumes that tCHG >> tDIS.

When LFB OUT is high, ICH = 0 and the minimum

frequency occurs. The charging current varies according

to two control inputs to the oscillator:

1. The output of the preheat timer

2. The voltage at Pin 6 (lamp feedback amplifier

output)

In preheat condition, charging current is fixed at

IR SET

CHG PREHEAT()

()

25 (6)

In running mode, charging current decreases as the VPIN6

rises from 0V to VOH of the LAMP FB amplifier. The

highest frequency will be attained when ICHG is highest,

which is attained when VPIN6 is at 0V:

IR SET

CHG( )

()

(7)

Highest lamp power, and lowest output frequency are

attained when VPIN6 is at its maximum output voltage

(VOH).

In this condition, the minimum operating frequency of the

ballast is set per (5) above.

For the IC to be used effectively in dimming ballasts with

higher Q output networks a larger CT value and lower RT

value can be used, to yield a smaller frequency excursion

over the control range (VPIN6). The discharge current is set

to 5mA. Assuming that IDIS >> IRT:

DIS VCO T()

≅×490

(8)

IC BIAS, UNDER-VOLTAGE LOCKOUT AND THERMAL

SHUTDOWN

The IC includes a shunt regulator which will limit the

voltage at VCC to 13.5 (VCCZ). The IC should be fed with

a current limited source, typically derived from the ballast

transformer auxiliary winding. When VCC is below

VCCZ – 0.7V, the IC draws less than 1.7mA of quiescent

current and the outputs are off. This allows the IC to start

using a “bleed resistor” from the rectified AC line.

To help reduce ballast cost, the ML4831 includes a

temperature sensor which will inhibit ballast operation if

the IC’s junction temperature exceeds 120°C. In order to

use this sensor in lieu of an external sensor, care should be

taken when placing the IC to ensure that it is sensing

temperature at the physically appropriate point in the

ballast. The ML4831’s die temperature can be estimated

with the following equation:

TT P CW

JAD

≅××°65 /

(9)

VCCZ

V(ON)

V(OFF)

15mA

1.3mA

Figure 6. Typical VCC and ICC Waveforms when

the ML4831 is Started with a Bleed Resistor from

the Rectified AC Line and Bootstrapped from an

Auxiliary Winding.

STARTING, RE-START, PREHEAT AND INTERRUPT

The lamp starting scenario implemented in the ML4831

is designed to maximize lamp life and minimize ballast

heating during lamp out conditions.

The circuit in Figure 7 controls the lamp starting scenarios:

Filament preheat and Lamp Out interrupt. C(X) is charged

with a current of IR(SET)/4 and discharged through R(X).

The voltage at C(X) is initialized to 0.7V (VBE) at power

up. The time for C(X) to rise to 3.4V is the filament preheat

time. During that time, the oscillator charging current

(ICHG) is 2.5/R(SET). This will produce a high frequency

for filament preheat, but will not produce sufficient

voltage to ignite the lamp.

After cathode heating, the inverter frequency drops to FMIN

causing a high voltage to appear to ignite the lamp. If the

voltage does not drop when the lamp is supposed to have

ignited, the lamp voltage feedback coming into Pin 9 rises

to above VREF, the C(X) charging current is shut off and the

inverter is inhibited until C(X) is discharged by R(X) to the

1.2V threshold. Shutting off the inverter in this manner

prevents the inverter from generating excessive heat when

the lamp fails to strike or is out of socket. Typically this

time is set to be fairly long by choosing a large value of R(X).

ML4831

R(X)

C(X)

6.8

–

1.2/3.4

HEAT

INHIBIT

0.625

R(SET)

–

1.2/6.8

–

REF

DIMMING

LOCKOUT

R(X)/C(X)

INT Q

Figure 7. Lamp Preheat and Interrupt Timers

LFB OUT is ignored by the oscillator until C(X) reaches

6.8V threshold. The lamps are therefore driven to full

power and then dimmed. The C(X) pin is clamped to

about 7.5V.

A summary of the operating frequencies in the various

operating modes is shown below.

Operating Mode Operating Frequency

[F(MAX) to F(MIN)]

Preheat 2

Dimming

Lock-out F(MIN)

Dimming

Control F(MIN) to F(MAX)

6.8

3.4

1.2

.65

7.5

R(X)/C(X)

HEAT

DIMMING

LOCKOUT

INT

INHIBIT

Figure 8. Lamp Starting and Restart Timing

ML4831

APPLICATIONS POWER FACTOR CORRECTED FLUORESCENT DIMMING LAMP BALLAST

ML4831

D1 D3

D2 D4

120V

L2 C2

C1 C3

R14

C12 C5 D5

R1 R4 R2 R3 R5 R24

C25 C26 C4 C6 C7

R16

R10

R17

C10

R11

C11

R12

R13

R9 R8

C13 C14 C24 C15 C16

R15

D11 D12

C22

C17

R21 R22

10 9

C20

C19

C23

D13

C21

R23

Figure 9. Typical Application: 2-Lamp Isolated Dimming Ballast with Active Power Factor Correction for 120VAC Input

ML4831

TABLE 1: PARTS LIST FOR THE ML4831EVAL EVALUATION KIT

CAPACITORS

QTY. REF. DESCRIPTION MFR. PART NUMBER

2 C1, 2 3.3nF, 125VAC, 10%, ceramic, “Y” capacitor Panasonic ECK-DNS332ME

1 C3 0.33µF, 250VAC, “X”, capacitor Panasonic ECQ-U2A334MV

4 C4, 8, 9, 22 0.1µF, 50V, 10%, ceramic capacitor AVX SR215C104KAA

2 C5, 21 0.01µF, 50V, 10%, ceramic capacitor AVX SR211C103KAA

1 C6 1.5µF, 50V, 2.5%, NPO ceramic capacitor AVX RPE121COG152

2 C7, 12 1µF, 50V, 20%, ceramic capacitor AVX SR305E105MAA

1 C10 100µF, 25V, 20%, electrolytic capacitor Panasonic ECE-A1EFS101

1 C11 100µF, 250V, 20%, electrolytic capacitor Panasonic ECE-S2EG101E

1 C13 4.7µF, 50V, 20%, electrolytic capacitor Panasonic ECE-A50Z4R7

3 C14, 15, 17 0.22µF, 50V, 10%, ceramic capacitor AVX SR305C224KAA

1 C16 1.5µF, 50V, 10%, ceramic capacitor AVX SR151V152KAA

1 C19 22nF, 630V, 5%, polypropylene capacitor WIMA MKP10, 22nF, 630V, 5%

1 C20 0.1µF, 250V, 5%, polypropylene capacitor WIMA MKP10, 0.1µF, 250V, 5%

1 C23 0.068µF, 160V, 5%, polypropylene capacitor WIMA MKP4, 68nF, 160V, 5%

1 C24 220µF, 16V, 20%, electrolytic capacitor Panasonic ECE-A16Z220

1 C25 47nF, 50V, 10%, ceramic capacitor AVX SR211C472KAA

1 C26 330pF, 50V, 10%, ceramic capacitor AVX SR151A331JAA

RESISTORS:

1 R1 0.33Ω, 5%, 1/2W, metal film resistor NTE HWD33

1 R2 4.3K, 1/4W, 5%, carbon film resistor Yageo 4.3K-Q

1 R3 47K, 1/4W, 5%, carbon film resistor Yageo 47K-Q

1 R4 12K, 1/4W, 5%, carbon film resistor Yageo 12K-Q

1 R5 20K, 1/4W, 1%, metal film resistor Dale SMA4-20K-1

1 R6 360K, 1/4W, 5%, carbon film resistor Yageo 360K-Q

1 R7 36K, 1W, 5%, carbon film resistor Yageo 36KW-1-ND

3 R8, 22, 11 22Ω, 1/4W, 5%, carbon film resistor Yageo 22-Q

1 R9 402K, 1/4W, 1%, metal film resistor Dale SMA4-402K-1

1 R10 17.8K, 1/4W, 1%, metal film resistor Dale SMA4-17.8K-1

1 R12 475K, 1/4W, 1%, metal film resistor Dale SMA4-475K-1

1 R13 5.49K, 1/4W, 1%, metal film resistor Dale SMA4-5.49K-1

ML4831

TABLE 1: PARTS LIST FOR ML4831EVAL EVALUATION KIT (Continued)

RESISTORS: (Continued)

QTY. REF. DESCRIPTION MFR. PART NUMBER

4 R14, 17, 24, 25 100K, 1/4W, 5%, carbon film resistor Yageo 100K-Q

1 R15 681K, 1/4W, 5%, carbon film resistor Yageo 681K-Q

1 R16 10K, 1/4W, 1%, metal film resistor Dale SMA4-10K-1

1 R21 33Ω, 1/4W, 5%, carbon film resistor Yageo 33-Q

1 R23 25K, pot (for dimming adjustment) Bourns 3386P-253-ND

DIODES:

4 D1, 2, 3, 4 1A, 600V, 1N4007 diode Motorola 1N4007TR

(or 1N5061 as a substitute)

2 D5, 6 1A, 50V (or more), 1N4001 diodes Motorola 1N4001TR

1 D7 3A, 400V, BYV26C or BYT03 400 fast recovery GI BYV26C

or MUR440 Motorola ultra Fast diode

5 D8, 9, 11, 0.1A, 75V, 1N4148 signal diode Motorola 1N4148TR

12, 13

IC’s:

1 IC1 ML4831, Electronic Ballast Controller IC Micro ML4831CP

Linear

TRANSISTORS:

3 Q1, 2, 3 3.3A, 400V, IRF720 power MOSFET IR IR720

MAGNETICS:

1 T1 T1 Boost Inductor, E24/25, 1mH, Custom Coils P/N 5039 or Coiltronics P/N CTX05-12538-1

E24/25 core set, TDK PC40 material

8-pin vertical bobbin (Cosmo #4564-3-419),

Wind as follows:

195 turns 25AWG magnet wire, start pin #1, end pin #4

1 layer mylar tape

14 turns 26AWG magnet wire, start pin #3, end pin #2

NOTE: Gap for 1mH ±5%

1 T2 T2 Gate Drive Xfmr, LPRI = 3mH, Custom Coils P/N 5037 or Coiltronics P/N CTX05-12539-1

Toroid Magnetics YW-41305-TC

Wind as follows:

Primary = 25 turns 30AWG magnet wire, start pin #1, end pin #4

Secondary = 50 turns 30AWG magnet wire, start pin #5, end pin #8

ML4831

TABLE 1: PARTS LIST FOR ML4831EVAL EVALUATION KIT (Continued)

MAGNETICS: (Continued)

QTY. REF. DESCRIPTION MFR. PART NUMBER

1 T3 T3 Inductor, LPRI = 1.66mH, Custom Ciols P/N 5041 or Coiltronics P/N CTX05-12547-1

E24/25 core set, TDK PC40 material

10 pin horizontal bobbin (Plastron #0722B-31-80)

Wind as follows:

1st: 170T of 25AWG magnet wire; start pin #10, end pin #9.

1 layer of mylar tape

2nd: 5T of #32 magnet wire; start pin #2, end pin #1

1 layer of mylar tape

3rd: 3T of #30 Kynar coated wire; start pin #4, end pin #5

4th: 3T of #30 Kynar coated wire; start pin #3, end pin #6

5th: 3T of #30 Kynar coated wire; start pin #7, end pin #8

NOTE: Gap for 1.66mH ±5% (pins 9 to 10)

1 T4 T4 Power Xfmr, LPRI = 3.87mH, Custom Ciols P/N 5038 or Coiltronics P/N CTX05-12545-1

E24/25 core set, TDK PC40 material

8 pin vertical bobbin (Cosmo #4564-3-419)

Wind as follows:

1st: 200T of 30AWG magnet wire; start pin #1, end pin #4.

1 layer of mylar tape

2nd: 300T of 32AWG magnet wire; start pin #5, end pin #8

NOTE: Gap for inductance primary: (pins 1 to 4) @ 3.87mH ±5%

1 T5 T5 Current Sense Inductor, Custom Coils P/N 5040 or Coiltronics P/N CTX05-12546-1

Toroid Magnetics YW-41305-TC

Wind as follows:

Primary = 3T 30AWG magnet coated wire, start pin #1, end pin #4

Secondary = 400T 35AWG magnet wire, start pin #5, end pin #8

INDUCTORS:

2 L1, 2 EMI/RFI Inductor, 600µH, DC resistance = 0.45ΩPrem. SPE116A

Magnetics

FUSES:

1 F1 2A fuse, 5 x 20mm miniature Littlefuse F948-ND

2 Fuse Clips, 5 x 20mm, PC Mount F058-ND

HARDWARE:

1 Single TO-220 Heatsink Aavid Eng. PB1ST-69

2 Double TO-220 Heatsink IERC PSE1-2TC

3 MICA Insulators Keystone 4673K-ND

ML4831

ORDERING INFORMATION

PART NUMBER TEMPERATURE RANGE PACKAGE

ML4831CP0°C to 85°CMolded PDIP (P18) (END OF LIFE)

Micro Linear reserves the right to make changes to any product herein to improve reliability, function or design.

Micro Linear does not assume any liability arising out of the application or use of any product described herein,

neither does it convey any license under its patent right nor the rights of others. The circuits contained in this

data sheet are offered as possible applications only. Micro Linear makes no warranties or representations as to

whether the illustrated circuits infringe any intellectual property rights of others, and will accept no responsibility

or liability for use of any application herein. The customer is urged to consult with appropriate legal counsel

before deciding on a particular application.

DS4831-01

2092 Concourse Drive

San Jose, CA 95131

Tel: 408/433-5200

Fax: 408/432-0295

SEATING PLANE

0.240 - 0.260

(6.09 - 6.61)

PIN 1 ID 0.295 - 0.325

(7.49 - 8.26)

0.890 - 0.910

(22.60 - 23.12)

0.016 - 0.022

(0.40 - 0.56)

0.100 BSC

(2.54 BSC)

0.008 - 0.012

(0.20 - 0.31)

0.015 MIN

(0.38 MIN)

0º - 15º

0.050 - 0.065

(1.27 - 1.65)

0.170 MAX

(4.32 MAX)

0.125 MIN

(3.18 MIN)

0.045 MIN

(1.14 MIN)

(4 PLACES)

Package: P18

18-Pin PDIP

Micro Linear

is a registered trademark of Micro Linear Corporation

Products described in this document may be covered by one or more of the following patents, U.S.: 4,897,611; 4,964,026; 5,027,116; 5,281,862; 5,283,483; 5,418,502; 5,508,570; 5,510,727; 5,523,940;

5,546,017; 5,559,470; 5,565,761; 5,592,128; 5,594,376; Japan: 2598946. Other patents are pending.

PHYSICAL DIMENSIONS inches (millimeters)