Rev. 1.5 December 2008 www.aosmd.com Page 1 of 16
AOZ1905
EZBoost 2A General Purpose Regulator
General Description
The AOZ1905 EZBoost is a high-performance, current-
mode, constant frequency step-up regulator with internal
MOSFET. 600kHz/1.2MHz switching frequency allows
the use of low-profile inductor and capacitors. The
current-mode control ensures easy loop compensation
and fast transient response. The AOZ1905 works from
a 2.7V to 5.5V input voltage range and generates an
output voltage as high as 24V. Other features include
input under-voltage lockout, cycle-by-cycle current limit,
thermal shutdown and soft-start.
The AOZ1905 is available in a tiny 3mm x 3mm 10-pin
DFN package and MSOP8 package and is rated over a
-40°C to +85°C operating temperature range.
Features
●2.7V to 5.5V input voltage range
●Adjustable output up to 24V
●600kHz/1.2MHz constant switching frequency
●Cycle-by-cycle current limit
●Thermal overload protection
●Programmable Soft-start
●Small 3mm x 3mm DFN 10L package
●MSOP-8L package
Applications
●LCD TV
●LCD Monitors
●Notebook Displays
●PCMCIA Cards
●Hand-Held Devices
●GPS Power
●TV Tuner
Typical Application
Figure 1. Typical Application Circuit
L1
4.7µH
LX
D1
R2
R1
C2
10µF
FB
IN
EN
VIN
SS
C1
10µF
GND
COMP
VOUT
OFF ON
FSEL
R3
C3
C4
AOZ1905
AOZ1905
Rev. 1.5 December 2008 www.aosmd.com Page 2 of 16
Ordering Information
All AOS products are offered in packages with Pb-free plating and compliant to RoHS standards.
Parts marked as Green Products (with “L” suffix) use reduced levels of Halogens, and are also RoHS compliant.
Please visit www.aosmd.com/web/quality/rohs_compliant.jsp for additional information.
Pin Configuration
Pin Description
Part Number Operating Temperature Range Package Environmental
AOZ1905DI -40°C to +85°C 3x3 DFN-10 Green Product
AOZ1905FI -40°C to +85°C MSOP-8 RoHS Compliant
AOZ1905FIL -40°C to +85°C MSOP-8 Green Product
Pin Name
Pin Number
Pin FunctionDFN-10 MSOP-8
COMP 1 1 Compensation Pin. COMP is the output of the internal transconductance error
amplifier. Connect a RC network from COMP to GND to compensate the loop.
FB 2 2 Feedback Input. Connect a resistive divider between the boost regulator output
and ground with the center tap connected to FB to set output voltage.
EN 3 3 Enable Input. Pull EN high to enable the boost regulator and pull EN low to dis-
able the regulator.
GND 4, 5 4 System Ground.
LX 6, 7 5 Boost Regulator Switching Node.
IN 8 6 Input Supply Pin.
FSEL 9 7 Frequency Select Pin. The switching frequency is 1.2MHz when FSEL is
connected to IN, and 600kHz when FSEL is connected to ground.
SS 10 8 Soft-Start Pin. Connect a capacitor from SS to GND to set the soft-start period.
SS
FSEL
IN
LX
1
2
3
4
COMP
FB
EN
GND
MSOP-8
(Top View)
DFN-10
(Top View)
8
7
6
5
SS
FSEL
IN
LX
LX
1
2
3
4
5
COMP
FB
EN
GND
GND
10
9
8
7
6
AOZ1905
Rev. 1.5 December 2008 www.aosmd.com Page 3 of 16
Absolute Maximum Ratings
Exceeding the Absolute Maximum ratings may damage the device.
Note:
1. Devices are inherently ESD sensitive, handling precautions are
required. Human body model rating: 1.5kΩ in series with 100pF.
Recommend Operating Ratings
The device is not guaranteed to operate beyond the Maximum
Operating Ratings.
Parameter Rating
IN to GND -0.3V to +6V
LX to GND -0.3V to +30V
COMP, EN, FB, FSEL, SS to GND -0.3V to +6V
Storage Temperature (TS) -65°C to +150°C
ESD Rating(1) 2kV
Parameter Rating
Supply Voltage (VIN) 2.7V to 5.5V
Output Voltage (VOUT)V
IN to 24V
Ambient Temperature (TA) -40°C to +85°C
Package Thermal Resistance
MSOP-8 (ΘJA)
DFN-10
150°C/W
48°C/W
Functional Block Diagram
VIN
10μF
OFF ON
IN Bias
Generator
EN
UVLO
Comp
PWM
Comp
OSC
R
S
Q
Error
Amp
Gm
UVLO
Threshold
Thermal
Shutdown
FSEL
EN
SS
FB
REF
ILIM
LX
COMP
Soft-Start
4.7µH
10µF
VOUT
AOZ1905
Rev. 1.5 December 2008 www.aosmd.com Page 4 of 16
Electrical Characteristics
TA = 25°C, VIN = 3.3V, unless otherwise specified. Specifications in BOLD indicate an ambient temperature range of -40°C to
+85°C.
Note:
2. Guaranteed by design.
Symbol Parameter Conditions Min. Typ. Max. Units
VIN IN Supply Voltage Range 2.7 5.5 V
VIN_UVLO IN UVLO Threshold IN rising 2.6 V
IN UVLO Hysteresis 200 mV
IIN_ON IN Quiescent Current EN = IN, FB = 1.4V 1mA
IIN_OFF IN Shutdowns Current EN = GND 1µA
VFB FB Voltage 1.143 1.17 1.197 V
FB Input Bias Current VIN = 2.7V 1 µA
FB Line Regulation 2.7V < VIN < 5.5V 0.15 % / V
FB Load Regulation 0.2A < Iswitch < 1.8A,
VOUT = 16V
1.5 %
ISS Soft-Start Charge Current 7 10 13 µA
ERROR AMPLIFIER
gmError Amplifier Transconductance 200 µS
AVError Amplifier Voltage Gain 340 V / V
OSCILLATOR
fSW Switching Frequency FSEL = VIN 960 1200 1440 kHz
FSEL = GND 480 600 720
DMAX(2) Maximum Duty Cycle VIN = 2.7V 89 %
DMIN(2) Minimum Duty Cycle FSEL = VIN 24 %
FSEL = GND 12
POWER SWITCH
RON_LX LX On Resistance 0.20 0.25 Ω
LX Leakage Current LX = 24V, EN = GND 2 µA
PROTECTIONS
ILIM Current Limit 2 2.7 3.5 A
TSD Thermal Shutdown Threshold 145 °C
Thermal Shutdown Hysteresis 35 °C
LOGIC INPUTS
EN Logic High Threshold 1.5 V
EN Logic Low Threshold 0.4 V
FSEL High 0.85 x VIN V
FSEL Low 0.15 x VIN V
EN, FSEL Input Current 0.1 1 µA
Rev. 1.5 December 2008 www.aosmd.com Page 5 of 16
AOZ1905
Typical Performance Characteristics
Switching Waveform
(I
OUT
= 400mA, f
LX
= 1.2MHz, L = 4.7μH)
Switching Waveform
(I
OUT
= 400mA, f
LX
= 600kHz, L = 10μH)
400ns/div 1μs/div
LVX
5V/div
IL
0.5A/div
LVX
5V/div
IL
0.5A/div
Load Transient Response
(I
OUT
= 40mA–400mA, f
LX
= 1.2MHz, L = 4.7μH)
Load Transient Response
(I
OUT
= 40mA–400mA, f
LX
= 600kHz, L = 10μH)
200μs/div 200μs/div
Vo Ripple
200mV/div
Io
0.2A/div
Vo Ripple
200mV/div
Io
0.2A/div
Startup Waveform
(R
OUT
= 200Ω, f
LX
= 1.2MHz, L = 4.7μH)
Startup Waveform
(R
OUT
= 200Ω, f
LX
= 600kHz, L = 4.7μH)
200
μ
s/div 200
μ
s/div
VEN
2V/div
Vo
5V/div
IL
0.5A/div
VEN
2V/div
Vo
5V/div
IL
0.5A/div
Rev. 1.5 December 2008 www.aosmd.com Page 6 of 16
AOZ1905
Efficiency
50
1 10 100 1,000
55
60
65
70
75
80
85
90
95
100
Efficiency (%)
Load Current (mA)
fSW=600kHz, L=10μH
fSW=1.2MHz, L=4.7μH
AOZ1905 Efficiency
(VIN = 3.3V, VOUT = 12V)
50
1 10 100 1,000
55
60
65
70
75
80
85
90
95
100
Efficiency (%)
Load Current (mA)
fSW=600kHz, L=10μH
fSW=1.2MHz, L=4.7μH
AOZ1905 Efficiency
(VIN = 5V, VOUT = 12V)
50
1 10 100 1,000
55
60
65
70
75
80
85
90
95
100
Efficiency (%)
Load Current
(
mA
)
fSW=600kHz, L=10μH
fSW=1.2MHz, L=4.7μH
AOZ1905 Efficiency
(VIN = 3.3V, VOUT = 8V)
AOZ1905
Rev. 1.5 December 2008 www.aosmd.com Page 7 of 16
Applications Information
The AOZ1905 is a current-mode step up regulator (Boost
Converter) with integrated NMOS switch. It operates
from a 2.7V to 5.5V input voltage range and supplies up
to 24V output voltage. The duty cycle can be adjusted to
obtain a wide range of output voltage up to 24V. Features
include enable control, cycle by cycle current limit, input
under voltage lockout, adjustable soft-start and thermal
shut down.
The AOZ1905 is available in MSOP-8 and DFN-10 3x3
packages.
Enable and Soft Start
The AOZ1905 has the adjustable soft start feature to limit
in-rush current and ensure the output voltage ramps up
smoothly to regulation voltage. A soft start process
begins when the input voltage rises to 2.6V and voltage
on EN pin is HIGH. In soft start process, a 10µA internal
current source charges the external capacitor at SS. As
the SS capacitor is charged, the voltage at SS rises. The
SS voltage clamps the reference voltage of the error
amplifier, therefore output voltage rising time follows the
SS pin voltage. With the slow ramping up output voltage,
the inrush current can be prevented.
The EN pin of the AOZ1905 is active high. Connect the
EN pin to VIN if enable function is not used. Pulling EN to
ground will disable the AOZ1905. Do not leave it open.
The voltage on EN pin must be above 1.5 V to enable the
AOZ1905. When voltage on EN pin falls below 0.4V, the
AOZ1905 is disabled. If an application circuit requires the
AOZ1905 to be disabled, an open drain or open collector
circuit should be used to interface to EN pin.
Steady-State Operation
Under steady-state conditions, the converter operates in
fixed frequency.
The AOZ1905 integrates an internal N-MOSFET as the
control switch. Inductor current is sensed by amplifying
the voltage drop across the drain to source of the control
power MOSFET. Output voltage is divided down by the
external voltage divider at the FB pin. The difference of
the FB pin voltage and reference is amplified by the
internal transconductance error amplifier. The error
voltage, which shows on the COMP pin, is compared
against the current signal, which is sum of inductor
current signal and ramp compensation signal, at PWM
comparator input. If the current signal is less than the
error voltage, the internal NMOS switch is on. The induc-
tor current ramps up. When the current signal exceeds
the error voltage, the switch is off. The inductor current is
freewheeling through the Schottky diode to output.
Switching Frequency
The AOZ1905 switching frequency is fixed and set by
an internal oscillator and FSEL. When the voltage of
FSEL is high (connected to VIN) The switching frequency
is 1.2MHz; when the voltage of FSEL is low (connected
to GND), the switching frequency is 600kHz.
Output Voltage Programming
Output voltage can be set by feeding back the output to
the FB pin with a resistor divider network. In the
application circuit shown in Figure 1. The resistor divider
network includes R1 and R2. Usually, a design is started
by picking a fixed R1 value and calculating the required
R2 with equation below.
Some standard value of R1, R2 for most commonly used
output voltage values are listed in Table 1.
Table 1.
The combination of R1 and R2 should be large enough to
avoid drawing excessive current from the output, which
will cause power loss.
Protection Features
The AOZ1905 has multiple protection features to prevent
system circuit damage under abnormal conditions.
Over Current Protection (OCP)
The sensed inductor current signal is also used for over
current protection. Since the AOZ1905 employs peak
current mode control, the COMP pin voltage is propor-
tional to the peak inductor current. The peak inductor
current is automatically limited cycle by cycle.
The cycle by cycle current limit threshold is set between
2A and 3A. When the current of control NMOS reaches
the current limit threshold, the cycle by cycle current limit
circuit turns off the NMOS immediately to terminate the
current duty cycle. The inductor current stop rising.
VO (V) R2 (kΩ) R1 (kΩ)
817030
12 270 30
16 370 30
18 420 30
25 595 30
VO1.2 1 R2
R1
-------
+
⎝⎠
⎜⎟
⎛⎞
×=
AOZ1905
Rev. 1.5 December 2008 www.aosmd.com Page 8 of 16
The cycle-by-cycle current limit protection directly limits
inductor peak current. The average inductor current is
also limited due to the limitation on peak inductor current.
When cycle by cycle current limit circuit is triggered, the
output voltage drops as the duty cycle decreasing.
Power-On Reset (POR)
A power-on reset circuit monitors the input voltage. When
the input voltage exceeds 2.6V, the converter starts
operation. When input voltage falls below 2.2V, the
converter will stop switching.
Thermal Protection
An internal temperature sensor monitors the junction
temperature. It shuts down the internal control circuit and
NMOS switch if the junction temperature exceeds 145°C.
Application Information
The basic AOZ1905 application circuit is shown in
Figure 1. Component selection is explained below.
Input capacitor
The input capacitor (C1 in Figure 1) must be connected to
the VIN pin and GND pin of the AOZ1905 to maintain
steady input voltage. The voltage rating of input capacitor
must be greater than maximum input voltage + ripple
voltage. The RMS current rating should be greater than
the inductor ripple current:
The input capacitor value should be greater than 4.7µF
for normal operation. The capacitor can be electrolytic,
tantalum or ceramic. The input capacitor should be
placed as close as possible to the IC; if not possible, put
a 0.1µF decoupling ceramics capacitor between IN pin
and GND.
Inductor
The inductor is used to supply higher output voltage
when the NMOS switch is off. For given input and output
voltage, inductance and switching frequency together
decide the inductor ripple current, which is,
The peak inductor current is:
High inductance gives low inductor ripple current but
requires larger size inductor to avoid saturation. Low
ripple current reduces inductor core losses. It also
reduces RMS current through inductor, switch and
freewheeling diode, which results in less conduction loss.
Usually, peak to peak ripple current on the inductor is
designed to be 30% to 50% of input current.
When selecting the inductor, make sure it is able to
handle the peak current without saturation even at the
highest operating temperature.
The inductor takes the highest current in a boost circuit.
The conduction loss on inductor needs to be checked for
thermal and efficiency requirements.
Surface mount inductors in different shape and styles are
available from Coilcraft, Elytone and Murata. Shielded
inductors are small and radiate less EMI noise. But they
cost more than unshielded inductors. The choice
depends on EMI requirement, price and size.
Output Capacitor
The output capacitor is selected based on the DC output
voltage rating, output ripple voltage specification and
ripple current rating.
The selected output capacitor must have a higher rated
voltage specification than the maximum desired output
voltage including ripple. De-rating needs to be consid-
ered for long term reliability.
Output ripple voltage specification is another important
factor for selecting the output capacitor. In a boost
converter circuit, output ripple voltage is determined by
load current, input voltage, output voltage, switching
frequency, output capacitor value and ESR. It can be
calculated by the equation below:
where;
ILOAD is the load current,
CO is the output capacitor value, and
ESRCO is the Equivalent Series Resistor of output capacitor.
When low ESR ceramic capacitor is used as output
capacitor, the impedance of the capacitor at the switch-
ing frequency dominates. Output ripple is mainly caused
by capacitor value and load current with the fixed fre-
ΔIL
VIN
fL×
-----------1VIN
VO
---------
–
⎝⎠
⎜⎟
⎛⎞
×=
ΔIL
VIN
fL×
-----------1VIN
VO
---------
–
⎝⎠
⎜⎟
⎛⎞
×=
ILpeak IIN
ΔIL
2
--------
+=
ΔVOILOAD
VO
VIN
---------ESRCO
1VIN
VOUT
---------------
–
⎝⎠
⎜⎟
⎛⎞
fC
O
×
------------------------------
+×
⎝⎠
⎜⎟
⎜⎟
⎜⎟
⎜⎟
⎜⎟
⎛⎞
×=
AOZ1905
Rev. 1.5 December 2008 www.aosmd.com Page 9 of 16
quency, input and output voltage. The output ripple volt-
age calculation can be simplified to:
Output capacitor with the range of 4.7µF to 22µF ceramic
capacitor usually can meet most applications.
Diode
The output rectifier diode freewheels the inductor current
to output when the internal MOSFET is off. To reduce
losses due to diode forward voltage and reverse recov-
ery, Schottky diode is preferred in AOZ1905. The reverse
voltage of selected diode should be higher than output
voltage, the average current rating should be higher than
the maximum load current and the peak current rating
should be greater than the peak current of inductor:
Loop Compensation
The AOZ1905 employs peak current mode control for
easy use and fast transient response. Peak current mode
control eliminates the double pole effect of the output
L&C filter. It greatly simplifies the compensation loop
design.
With peak current mode control, the boost power stage
can be simplified to be a one-pole, one left plane zero
and one right half plane (RHP) system in frequency
domain. The pole is dominant pole and can be
calculated by:
The zero is a ESR zero due to output capacitor and its
ESR. It is can be calculated by:
where;
CO is the output filter capacitor,
RL is load resistor value, and
ESRCO is the equivalent series resistance of output capacitor.
The RHP zero has the effect of a zero in the gain causing
an imposed +20dB/decade on the roll off, but has the
effect of a pole in the phase, subtracting 90° in the
phase.
The RHP zero can be calculated by:
The RHP zero obviously can cause the instable issue if
the bandwidth is higher. It is recommended to design the
bandwidth to lower than the one half frequency of RHP
zero.
The compensation design is actually to shape the
converter close loop transfer function to get desired gain
and phase. Several different types of compensation
network can be used for AOZ1905. For most cases,
a series capacitor and resistor network connected to the
COMP pin sets the pole-zero and is adequate for a stable
high-bandwidth control loop.
In the AOZ1905, FB pin and COMP pin are the inverting
input and the output of internal transconductance error
amplifier. A series R and C compensation network con-
nected to COMP provides one pole and one zero. The
pole is:
where;
GEA is the error amplifier transconductance, which is 200 x 10-6
A/V,
GVEA is the error amplifier voltage gain, which is 340 V/V, and
CC is compensation capacitor.
The zero given by the external compensation network,
capacitor CC (C3 in Figure 1) and resistor RC (R3 in
Figure 1), is located at:
Choosing the suitable CC and RC by trading-off stability
and bandwidth.
Thermal Management and Layout
Consideration
In the AOZ1905 boost regulator circuit, high pulsing
current flows through two circuit loops. The first loop
starts from the input capacitors, to the filter inductor, to
the LX pin, to the internal NMOS switch, to the ground
and back to the input capacitor, when the switch turns on.
The second loop starts from input capacitor, to the filter
inductor, to the LX pin to the external diode, to the
ground and back to the input capacitor, when the switch
is off.
ΔVOIL
1VIN
VOUT
---------------
–
⎝⎠
⎜⎟
⎛⎞
fC
O
×
------------------------------
×=
ILpeak IIN
ΔIL
2
--------
+=
fP1
1
2πCORL
××
-----------------------------------
=
fZ1
1
2πCOESRCO
××
------------------------------------------------
=
fZ2
VIN 2
2πLI
OVO
×××
-------------------------------------------
=
fP2
GEA
2πCCGVEA
××
-------------------------------------------
=
fZ2
1
2πCCRC
××
-----------------------------------
=
AOZ1905
Rev. 1.5 December 2008 www.aosmd.com Page 10 of 16
In PCB layout, minimizing the two loops area reduces the
noise of this circuit and improves efficiency. A ground
plane is recommended to connect input capacitor, output
capacitor, and GND pin of the AOZ1905.
In the AOZ1905 boost regulator circuit, the three major
power dissipating components are the AOZ1905 and
output inductor. The total power dissipation of converter
circuit can be measured by input power minus output
power.
The power dissipation of inductor can be approximately
calculated by input current and DCR of inductor.
The power dissipation in the diode can be calculated as:
where;
VFW is the forward voltage drop of the diode.
The actual AOZ1905 junction temperature can be
calculated with power dissipation in the AOZ1905 and
thermal impedance from junction to ambient.
The maximum junction temperature of AOZ1905 is
145°C, which limits the maximum load current capability.
The thermal performance of the AOZ1905 is strongly
affected by the PCB layout. Extra care should be taken
by users during design process to ensure that the IC
will operate under the recommended environmental
conditions.
Several layout tips are listed below for the best electric
and thermal performance. Figure 2 below illustrates the
PCB layout example as reference.
1. Do not use thermal relief connection to the VIN and
the GND pin. Pour a maximized copper area to the
GND pin and the VIN pin to help thermal dissipation.
2. A ground plane is preferred.
3. Make the current trace from LX pins to L to Co to the
GND as short as possible.
4. Pour copper plane on all unused board area and
connect it to stable DC nodes, like VIN, GND or
VOUT.
5. Keep sensitive signal trace such as trace connected
with FB pin and COMP pin far away from the LX pin.
Figure 3. AOZ1905 PCB Layout Example
Ptotal_loss VIN IIN VOIO
×–×=
Pinductor_loss IIN2Rinductor 1.1××=
Pdiode_loss IO1D–()VFW
××=
Tjunction Ptotal_loss Pinductor_loss Pdiode_loss
––()
×
=
ΘTambient
+×
L1
R2
L1
R2
(a) MSOP-8 (a) DFN-10 3x3
AOZ1905
Rev. 1.5 December 2008 www.aosmd.com Page 11 of 16
Application Case for AOZ1905: Multiple-Output, Low-Profile TFT LCD Power Supply
TFT-LCD (Thin Film Transistor Liquid Crystal Display) is
a variant of liquid crystal display (LCD) which uses thin
film transistor (TFT) technology to improve image quality.
TFT LCD is one type of active matrix LCD, which is used
in televisions, flat panel displays and projectors. For this
application, it usually needs several output sources –
Vo1 = 9V, Vo2 = -9V and Vo3 = 26V. Using one
AOZ1905 can easily supply the whole power solution to
obtain three outputs. The detailed schematic is shown in
Figure 4.
Figure 3. Multiple-Output, Low-Profile TFT LCD Power Solution
Rev. 1.5 December 2008 www.aosmd.com Page 12 of 16
AOZ1905
Package Dimensions, MSOP-8, MSOP-8L
Gauge Plane Seating Plane
Notes:
1. All dimensions are in millimeters.
2. Dimensions are inclusive of plating.
3. Package body sizes exclude mold flash and gate burrs. Mold flash at the non-lead sides should be less than 6 mils each.
4. Dimension L is measured in gauge plane.
5. Controlling dimension is millimeter, converted inch dimensions are not necessarily exact.
Symbols
A
A1
A2
b
c
D
E
e
E1
L1
L2
L3
θ
Dimensions in millimeters
Min.
—
0.05
0.81
0.25
0.13
2.95
2.95
0.40
0.90
0°
Nom.
—
—
0.86
0.30
0.15
3.00
3.00
0.65 TYP.
4.90 TYP.
0.55
0.95
0.25 BSC
—
Max.
1.10
0.15
0.91
0.40
0.25
3.05
3.05
0.70
1.00
6°
RECOMMENDED LAND PATTERN Symbols
A
A1
A2
b
c
D
E
e
E1
L1
L2
L3
θ
Dimensions in inches
Min.
—
0.002
0.032
0.010
0.005
0.116
0.116
0.016
0.035
0°
Nom.
—
—
0.034
0.012
0.006
0.118
0.118
0.026 TYP.
0.190 TYP.
0.022
0.037
0.010 BSC
—
Max.
0.043
0.006
0.036
0.016
0.010
0.120
0.120
0.028
0.039
6°
D
EE1
AA2
eb
A1
0.10mm
L3
L1 L2
c
0.75
4.35
0.65
0.35
Rev. 1.5 December 2008 www.aosmd.com Page 13 of 16
AOZ1905
Tape & Reel Dimensions, MSOP-8, MSOP-8L
Carrier Tape
Reel
Tape Size
12mm
Reel Size
ø330
M
ø330.00
±0.50
Package
MSOP-8
T
0.30
±0.05
B0
3.30
±0.10
A0
5.20
±0.10
K1
1.20
±0.10
K0
1.60
±0.10
D0
ø1.50
+0.1/-0.0
E
12.0
±0.3
E1
1.75
±0.10
E2
5.50
±0.05
P0
8.00
±0.10
P1
4.00
±0.05
N
ø97.00
±0.10
UNIT: mm
G
M
W1
S
K
H
N
W
V
R
Trailer Tape
300mm min.
Components Tape
Orientation in Pocket
Leader Tape
500mm min.
K1
W
13.00
±0.30
W1
17.40
±1.00
H
ø13.00
+0.50/-0.20
K
10.60
S
2.00
±0.50
G
—
R
—
V
—
Leader/Trailer and Orientation
UNIT: mm
T
R0.3
Max
B0
P2
P1
K0
K1 A0 P0
Section B-B'
Section B-B'
4.2
3.4
R0.3 Typ.
D0 D1
E
E2
E1
D1
ø1.50
Min.
P2
2.00
±0.05
Notes:
1. 10 sprocket hole pich cumulative tolerance ±0.2.
2. Camber not to exceed 1mm in 100mm.
3. A0 and B0 measured on a plane 0.3mm above the bottom of the pocket.
4. K0 measured from a plane on the inside bottom of the pocket to the top surface of the carrier.
5. Pocket position relative to sprocket hole measured as tue position of pocket, not pocket hole.
6. All dimensions in mm.
Feeding Direction
Rev. 1.5 December 2008 www.aosmd.com Page 14 of 16
AOZ1905
Package Dimensions, DFN 3x3 EP 10L
TOP VIEW
BOTTOM VIEW
SIDE VIEW
RECOMMENDED LAND PATTERN
Notes:
1. Dimensions and tolerances conform to ASME Y14.5M-1994.
2. Controlling dimension is millimeter, converted inch dimensions are not necessarily exact.
3. Dimension b applied to metallized terminal and is measured between 0.15mm and 0.30mm from the terminal tip. If the terminal
has the optional radius on the other end of the terminal, dimension b should not be measured in that radius area.
4. Coplanarity ddd applies to the terminals and all other bottom surface metallization.
Symbols
A
A1
b
c
D
D1
E
E1
e
L
R
aaa
bbb
ccc
ddd
Dimensions in millimeters
Min.
0.70
0.00
0.18
—
2.23
1.50
0.30
Nom.
0.75
0.02
0.25
0.15
3.00 BSC
2.38
3.00 BSC
1.65
0.50 BSC
0.30
0.20
0.15
0.10
0.10
0.08
Max.
0.80
0.05
0.30
0.20
2.48
1.75
0.50
Symbols
A
A1
b
c
D
D1
E
E1
e
L
R
aaa
bbb
ccc
ddd
Dimensions in inches
Min.
0.028
0.000
0.007
—
0.088
0.059
0.012
Nom.
0.030
0.001
0.010
0.006
0.118 BSC
0.094
0.118 BSC
0.065
0.020 BSC
0.016
0.008
0.006
0.004
0.004
0.003
Max.
0.031
0.002
0.012
0.008
0.098
0.069
0.020
UNIT: mm
E
D
10
1
10
1
10x
E
L
D1
A1
Seating
Plane
A
0.50
0.25
2.60
1.65
2.38
0.40
1.30
c
E1
R
Pin #1 ID
Option 2
10
1
Pin #1 ID
Option 1
b
R
Rev. 1.5 December 2008 www.aosmd.com Page 15 of 16
AOZ1905
Tape and Reel Dimensions, DFN 3x3 EP 10L
Package A0 B0 K0 E E1 E2D0 D1 P0 P1 P2 T
3.40
±0.10 ±0.10
3.35
±0.10
1.10
±0.10
1.50 1.00 8.00
±0.10
1.75
±0.05
3.50
±0.10
4.00
±0.10
4.00
±0.05
2.00
±0.20
0.23
UNIT: mm
Tape
Leader/Trailer and Orientation
+0.30/-0.10
Trailer Tape
300mm min.
Components Tape
Orientation in Pocket
Leader Tape
500mm min.
K0
B0
P0 A0
P1
P2
D0 D1
E1
E2 E
T
Feeding Direction
+0.25/-0.00
Reel
Tape Size
8mm
Reel Size
ø180
M
ø180.00
±0.50
N
60.0
±0.50
W1
R
M
S
K
H
N
UNIT: mm
W1
8.4
+1.5/-0.0
H
13.0
±0.20
S
1.5
Min.
K
13.5
Min.
R
3.0
±0.50
DFN 3x3 EP
Rev. 1.5 December 2008 www.aosmd.com Page 16 of 16
AOZ1905
Package Marking
AOZ1905FI
(MSOP-8)
1905
I0AW
LT
1905I
0FAYW
LT
Part Number Code, Underscore Denotes Green Product
Part Number Code, Underscore
Denotes Green Product
No Option
Industrial Temperature Range
No Option
Industrial Temperature Range
Assembly Location
Fab & Assembly Location
Assembly Year & Week
Assembly Lot Number
Assembly Lot Number
AOZ1905DI
(3x3 DFN-10)
Week (Year code is embedded by using upper bar, upper dot,
under bar, under dot on “W”)
As used herein:
1. Life support devices or systems are devices or
systems which, (a) are intended for surgical implant into
the body or (b) support or sustain life, and (c) whose
failure to perform when properly used in accordance
with instructions for use provided in the labeling, can be
reasonably expected to result in a significant injury of
the user.
2. A critical component in any component of a life
support, device, or system whose failure to perform can
be reasonably expected to cause the failure of the life
support device or system, or to affect its safety or
effectiveness.
Alpha & Omega Semiconductor reserves the right to make changes at any time without notice.
LIFE SUPPORT POLICY
ALPHA & OMEGA SEMICONDUCTOR PRODUCTS ARE NOT AUTHORIZED FOR USE AS CRITICAL
COMPONENTS IN LIFE SUPPORT DEVICES OR SYSTEMS.
