MCP3911 3.3V Two-Channel Analog Front End Features Description * Two Synchronous Sampling 16/24-bit Resolution Delta-Sigma A/D Converters * 94.5 dB SINAD, -106.5 dBc Total Harmonic Distortion (THD) (up to 35th harmonic), 111 dB SFDR for Each Channel * 2.7V - 3.6V AVDD, DVDD * Programmable Data Rate up to 125 ksps - 4 MHz Maximum Sampling Frequency * Oversampling Ratio up to 4096 * Ultra Low Power Shutdown Mode with <2 A * -122 dB Crosstalk between the Two Channels * Low Drift 1.2V Internal Voltage Reference: 7 ppm/C * Differential Voltage Reference Input Pins * High Gain PGA on Each Channel (up to 32V/V) * Phase Delay Compensation with 1 s Time Resolution * Separate Modulator Output Pins for Each Channel * Separate Data Ready Pin for Easy Synchronization * Individual 24-bit Digital Offset and Gain Error Correction for Each Channel * High-Speed 20 MHz SPI Interface with Mode 0,0 and 1,1 Compatibility * Continuous Read/Write Modes for Minimum Communication * Low Power Consumption (8.9 mW at 3.3V, 5.6 mW at 3.3V in low-power mode, typical) * Available in Small 20-lead QFN and SSOP Packages, Pin-to-pin Compatible with MCP3901 * Extended Temperature Range: -40C to +125C The MCP3911 is a 2.7V to 3.6V dual channel Analog Front End (AFE) containing two synchronous sampling Delta-Sigma Analog-to-Digital Converters (ADC), two PGAs, phase delay compensation block, low-drift internal voltage reference, modulator output block, digital offset and gain errors calibration registers, and high-speed 20 MHz SPI compatible serial interface. * * * * * Energy Metering and Power Measurement Automotive Portable Instrumentation Medical and Power Monitoring Audio/Voice Recognition The MCP3911 is capable of interfacing a large variety of voltage and current sensors including shunts, current transformers, Rogowski coils and Hall effect sensors. Package Type RESET DVDD AVDD CH0+ CH0CH1CH1+ AGND SDI SDO SCK CS OSC2 OSC1/CLKI REFIN- 10 11 DGND 20-Lead QFN SDO DR MDAT0 MDAT1 SDI 20 19 18 17 16 15 14 13 12 RESET REFIN+/OUT 1 2 3 4 5 6 7 8 9 DVDD 20-Lead SSOP AVDD Applications The MCP3911 ADCs are fully configurable with features such as: 16/24-bit resolution, OSR from 32 to 4096, gain from 1x to 32x, independent shutdown and reset, dithering and auto-zeroing. The communication is largely simplified with the one-byte-long commands including various continuous read/write modes that can be accessed by the Direct Memory Access (DMA) of an MCU, and with a separate data ready pin that can be directly connected to an Interrupt Request (IRQ) input of an MCU. 20 19 18 17 16 15 SCK CH0+ 1 CH0- 2 14 CS EP 21 CH1- 3 13 OSC2 12 OSC1/CLKI CH1+ 4 11 DR (c) 2012 Microchip Technology Inc. 7 8 9 10 REFIN- DGND MDAT1 MDAT0 6 REFIN+/OUT AGND 5 DS22286A-page 1 MCP3911 Functional block diagram REFIN+/OUT AVDD Voltage Reference + DVDD Vref REFIN- Clock Generation DMCLK/DRCLK Vref- Vref+ ANALOG CH0+ + CH0- PGA CH1+ + CH1- PGA DMCLK OSC1 OSC2 + X Phase PHASE <11:0> Shifter OFFCAL_CH1 GAINCAL_CH1 <23:0> <23:0> DATA_CH1 <23:0> + MOD<7:4> OSR<2:0> PRE<1:0> OFFCAL_CH0 GAINCAL_CH0 <23:0> <23:0> DATA_CH0 <23:0> MOD<3:0> - Modulator - Modulator MCLK DIGITAL SINC3+ SINC1 DR SDO Digital SPI Interface X RESET SDI SCK CS SINC3+ SINC1 MODOUT<1:0> DUAL - ADC Modulator Output Block MOD<7:0> POR AVDD Monitoring MDAT0 MDAT1 POR DVDD Monitoring AGND DS22286A-page 2 Xtal Oscillator AMCLK VREFEXT DGND (c) 2012 Microchip Technology Inc. MCP3911 1.0 ELECTRICAL CHARACTERISTICS ABSOLUTE MAXIMUM RATINGS VDD ..................................................................... -0.3V to 4.0V Digital inputs and outputs w.r.t. AGND ................ --0.3V to 4.0V Analog input w.r.t. AGND ..................................... ....-2V to +2V VREF input w.r.t. AGND ............................... -0.6V to VDD +0.6V Storage temperature .....................................-65C to +150C Ambient temp. with power applied ................-65C to +125C Soldering temperature of leads (10 seconds) ............. +300C ESD on the analog inputs (HBM,MM) ................. 4.0 kV, 200V Notice: Stresses above those listed under "Absolute Maximum Ratings" may cause permanent damage to the device. This is a stress rating only and functional operation of the device at those or any other conditions, above those indicated in the operational listings of this specification, is not implied. Exposure to maximum rating conditions for extended periods may affect device reliability. ESD on all other pins (HBM,MM) ........................ 4.0 kV, 200V 1.1 ELECTRICAL SPECIFICATIONS TABLE 1-1: ANALOG SPECIFICATIONS TARGET TABLE Electrical Specifications: Unless otherwise indicated, all parameters apply at AVDD = DVDD = 2.7V to 3.6V, MCLK = 4 MHz; PRE<1:0> = 00; OSR = 256; GAIN = 1; VREFEXT=0, CLKEXT=1, AZ_FREQ=0, DITHER<1:0>=11, BOOST<1:0> = 10; VCM=0V; TA = -40C to +125C; VIN = 1.2 VPP = 424 mVRMS @ 50/60 Hz on both channels. Sym Characteristic Min Typ Max Units Test Conditions Resolution (No Missing Codes) 24 -- -- bits OSR = 256 or greater ADC Performance fS(DMCLK) Sampling Frequency 1 4 MHz For maximum condition, BOOST<1:0> = 11 fD(DRCLK) Output Data Rate 4 125 ksps For maximum condition, BOOST<1:0> = 11, OSR = 32 +1 V All analog input channels, measured to AGND nA RESET<1:0>=11, MCLK running continuously +600/ GAIN mV VREF=1.2V, proportional to VREF +1 mV (Note 4) CH0+/- Analog Input Absolute Voltage on CH0+, CH0-, CH1+, CH1pins IIN Analog Input Leakage Current (CHn+-CHn-) Differential Input Voltage Range VOS Offset Error -1 +/-1 -600/GAIN -1 Offset Error Drift GE Gain Error 0.2 0.5 -4 V/C +4 % (Note 4) Note 1: This specification implies that the ADC output is valid over this entire differential range and that there is no distortion or instability across this input range. Dynamic Performance specified at -0.5 dB below the maximum signal range, VIN = 1.2VPP = 424 mVRMS, VREF = 1.2V @ 50/60 Hz. See terminology section for definition. This parameter is established by characterization and not 100% tested. See performance graphs for other than default settings provided here. 2: For these operating currents the following configuration bit settings apply: SHUTDOWN<1:0>=00, RESET<1:0>=00, VREFEXT=0, CLKEXT=0. For these operating currents the following configuration bit settings apply: SHUTDOWN<1:0>=11, VREFEXT=1, CLKEXT=1. Applies to all gains. Offset and gain errors depend on PGA gain setting, see typical performance curves for typical performance. Outside of this range, ADC accuracy is not specified. An extended input range of +/-2 V can be applied continuously to the part with no damage. For proper operation, and for optimizing ADC accuracy, AMCLK should be limited to the maximum frequency defined in the Table 5-2 as a function of the BOOST and PGA setting chosen. MCLK can take larger values as long as the prescaler settings (PRE<1:0>) limit AMCLK=MCLK/PRESCALE in the defined range in the Table 5-2. 3: 4: 5: 6: (c) 2012 Microchip Technology Inc. DS22286A-page 3 MCP3911 TABLE 1-1: ANALOG SPECIFICATIONS TARGET TABLE (CONTINUED) Electrical Specifications: Unless otherwise indicated, all parameters apply at AVDD = DVDD = 2.7V to 3.6V, MCLK = 4 MHz; PRE<1:0> = 00; OSR = 256; GAIN = 1; VREFEXT=0, CLKEXT=1, AZ_FREQ=0, DITHER<1:0>=11, BOOST<1:0> = 10; VCM=0V; TA = -40C to +125C; VIN = 1.2 VPP = 424 mVRMS @ 50/60 Hz on both channels. Sym Characteristic Min Gain Error Drift INL Integral Non-Linearity ZIN Differential Input Impedance SINAD Signal-to-Noise and Distortion Ratio (Note 1) THD Total Harmonic Distortion (Note 1) SNR Signal to Noise Ratio (Note 1) SFDR Spurious Free Dynamic Range (Note 1) CTALK Typ Max 1 Units Test Conditions ppm/C 5 ppm 232 -- -- k G=1, proportional to 1/ AMCLK 142 -- -- k G=2, proportional to 1/ AMCLK 72 -- -- k G=4, proportional to 1/ AMCLK 38 -- -- k G=8, proportional to 1/ AMCLK 36 -- -- k G=16, proportional to 1/ AMCLK 33 -- -- k G=32, proportional to 1/ AMCLK 92 94.5 -- dB -106.5 -103 dBc 92 95 dB 111 dBFS Includes the first 35 harmonics Crosstalk (50, 60 Hz) -- -122 -- dB AC PSRR AC Power Supply Rejection -- -73 -- dB AVDD = DVDD = 3.3V + 0.6Vpp, 50/60 Hz, 100/120 Hz DC PSRR DC Power Supply Rejection -- -73 -- dB AVDD = DVDD = 2.7V to 3.6V DC CMRR DC Common Mode Rejection -- -105 -- dB VCM from -1V to +1V 1.176 1.2 1.224 V VREFEXT = 0, TA = 25C only -- 7 -- Internal Voltage Reference VREF TCVREF Tolerance Temperature Coefficient ppm/C TA = -40C to +125C, VREFEXT = 0 Note 1: This specification implies that the ADC output is valid over this entire differential range and that there is no distortion or instability across this input range. Dynamic Performance specified at -0.5 dB below the maximum signal range, VIN = 1.2VPP = 424 mVRMS, VREF = 1.2V @ 50/60 Hz. See terminology section for definition. This parameter is established by characterization and not 100% tested. See performance graphs for other than default settings provided here. 2: For these operating currents the following configuration bit settings apply: SHUTDOWN<1:0>=00, RESET<1:0>=00, VREFEXT=0, CLKEXT=0. For these operating currents the following configuration bit settings apply: SHUTDOWN<1:0>=11, VREFEXT=1, CLKEXT=1. Applies to all gains. Offset and gain errors depend on PGA gain setting, see typical performance curves for typical performance. Outside of this range, ADC accuracy is not specified. An extended input range of +/-2 V can be applied continuously to the part with no damage. For proper operation, and for optimizing ADC accuracy, AMCLK should be limited to the maximum frequency defined in the Table 5-2 as a function of the BOOST and PGA setting chosen. MCLK can take larger values as long as the prescaler settings (PRE<1:0>) limit AMCLK=MCLK/PRESCALE in the defined range in the Table 5-2. 3: 4: 5: 6: DS22286A-page 4 (c) 2012 Microchip Technology Inc. MCP3911 TABLE 1-1: ANALOG SPECIFICATIONS TARGET TABLE (CONTINUED) Electrical Specifications: Unless otherwise indicated, all parameters apply at AVDD = DVDD = 2.7V to 3.6V, MCLK = 4 MHz; PRE<1:0> = 00; OSR = 256; GAIN = 1; VREFEXT=0, CLKEXT=1, AZ_FREQ=0, DITHER<1:0>=11, BOOST<1:0> = 10; VCM=0V; TA = -40C to +125C; VIN = 1.2 VPP = 424 mVRMS @ 50/60 Hz on both channels. Sym Characteristic ZOUTVREF AIDDVREF Min Typ Max Units Test Conditions Output Impedance 2 -- k VREFEXT = 0 Internal Voltage Reference Operating Current 25 -- A VREFEXT=0, SHUTDOWN<1:0>=11 Voltage Reference Input Input Capacitance -- -- 10 pF VREF Differential Input Voltage Range (VREF+ - VREF -) 1.1 -- 1.3 V VREFEXT = 1 VREF+ Absolute Voltage on REFIN+ pin VREF- + 1.1 -- VREF- + 1.3 V VREFEXT = 1 VREF- Absolute Voltage REFIN- pin -0.1 -- +0.1 V REFIN- should be connected to AGND when VREFEXT=0 -- 20 MHz CLKEXT = 1, (Note 6) Master Clock Input fMCLK Master Clock Input Frequency Range fXTAL Crystal Oscillator Operating Frequency Range 1 -- 20 MHz CLKEXT = 0, (Note 6) Analog Master Clock -- -- 16 MHz (Note 6) AMCLK Power Supply AVDD Operating Voltage, Analog 2.7 -- 3.6 V DVDD Operating Voltage, Digital 2.7 -- 3.6 V IDD,A Operating Current, Analog (Note 2) -- 1.5 2.3 mA BOOST<1:0>=00 -- 1.8 2.8 mA BOOST<1:0>=01 -- 2.5 3.5 mA BOOST<1:0>=10 -- 4.4 6.25 mA BOOST<1:0>= 11 -- 0.2 0.3 mA MCLK = 4 MHz, proportional to MCLK -- 0.7 -- mA MCLK = 16 MHz, proportional to MCLK Shutdown Current, Analog -- -- 1 A AVDD pin only (Note 3) Shutdown Current, Digital -- -- 1 A DVDD pin only (Note 3) IDD,D IDDS,A IDDS,D Operating Current, Digital Note 1: This specification implies that the ADC output is valid over this entire differential range and that there is no distortion or instability across this input range. Dynamic Performance specified at -0.5 dB below the maximum signal range, VIN = 1.2VPP = 424 mVRMS, VREF = 1.2V @ 50/60 Hz. See terminology section for definition. This parameter is established by characterization and not 100% tested. See performance graphs for other than default settings provided here. 2: For these operating currents the following configuration bit settings apply: SHUTDOWN<1:0>=00, RESET<1:0>=00, VREFEXT=0, CLKEXT=0. For these operating currents the following configuration bit settings apply: SHUTDOWN<1:0>=11, VREFEXT=1, CLKEXT=1. Applies to all gains. Offset and gain errors depend on PGA gain setting, see typical performance curves for typical performance. Outside of this range, ADC accuracy is not specified. An extended input range of +/-2 V can be applied continuously to the part with no damage. For proper operation, and for optimizing ADC accuracy, AMCLK should be limited to the maximum frequency defined in the Table 5-2 as a function of the BOOST and PGA setting chosen. MCLK can take larger values as long as the prescaler settings (PRE<1:0>) limit AMCLK=MCLK/PRESCALE in the defined range in the Table 5-2. 3: 4: 5: 6: (c) 2012 Microchip Technology Inc. DS22286A-page 5 MCP3911 1.2 SERIAL INTERFACE CHARACTERISTICS TABLE 1-2: SERIAL DC CHARACTERISTICS TABLE Electrical Specifications: Unless otherwise indicated, all parameters apply at DVDD = 2.7 to 3.6V, TA = -40C to +125C, CLOAD = 30pF, applies to all digital I/O. Sym Characteristics VIH High-level Input voltage VIL Low-level Input voltage ILI Input leakage current ILO Min Typ 0.7 DVDD -- Max Units Test Conditions V Schmitt Triggered -- 0.3 DVDD V Schmitt Triggered -- -- 1 A CS = DVDD, VIN = DGND TO DVDD Output leakage current -- -- 1 A CS = DVDD, VOUT = DGND OR DVDD VHYS Hysteresis of Schmitt Trigger Inputs -- 200 mV (Note 2), DVDD = 3.3V only VOL Low-level output voltage -- -- 0.4 V IOL = +2.1mA, DVDD = 3.3V VOH High-level output voltage DVDD -0.5 -- -- V IOH = -2.1mA, DVDD = 3.3V CINT Internal capacitance (all inputs and outputs) -- -- 7 pF TA = 25C, SCK = 1.0 MHz, DVDD =3.3V (Note 1) Note 1: This parameter is periodically sampled and not 100% tested. 2: This parameter is established by characterization and not production tested. TABLE 1-3: SERIAL AC CHARACTERISTICS TABLE Electrical Specifications: Unless otherwise indicated, all parameters apply at DVDD = 2.7 to 3.6V, TA = -40C to +125C, GAIN = 1, CLOAD = 30pF. Sym Characteristics Min Typ Max Units -- 20 MHz Test Conditions fSCK Serial Clock frequency -- tCSS CS setup time 25 -- -- ns tCSH CS hold time 50 -- -- ns tCSD CS disable time 50 -- -- ns tsu Data setup time 5 -- -- ns tHD Data hold time 10 -- -- ns tHI Serial Clock high time 20 -- -- ns tLO Serial Clock low time 20 -- -- ns tCLD Serial Clock delay time 50 -- -- ns tCLE Serial Clock enable time 50 -- -- ns tDO Output valid from SCK low -- -- 25 ns tDOMDAT Modulator output valid from AMCLK high -- -- 1/(2*AMCLK) s tHO Output hold time 0 -- -- ns (Note 1) tDIS Output disable time -- -- 25 ns (Note 1) tMCLR Reset Pulse Width (RESET) 100 -- -- ns tDODR Data Transfer Time to DR (Data Ready) -- 25 ns (Note 2) Note 1: This parameter is periodically sampled and not 100% tested. 2: This parameter is established by characterization and not production tested. DS22286A-page 6 (c) 2012 Microchip Technology Inc. MCP3911 TABLE 1-3: SERIAL AC CHARACTERISTICS TABLE (CONTINUED) Electrical Specifications: Unless otherwise indicated, all parameters apply at DVDD = 2.7 to 3.6V, TA = -40C to +125C, GAIN = 1, CLOAD = 30pF. Sym Characteristics Min tMODSU Modulator Mode Entry to Modulator Data Present tDRP Data Ready Pulse Low Time Typ Max Units -- 100 ns 1/DMCLK -- s Test Conditions Note 1: This parameter is periodically sampled and not 100% tested. 2: This parameter is established by characterization and not production tested. TABLE 1-4: TEMPERATURE SPECIFICATIONS TABLE Electrical Specifications: Unless otherwise indicated, all parameters apply at AVDD = 2.7 to 3.6V, DVDD = 2.7 to 3.6V. Parameters Sym Min Typ Max Units Conditions Operating Temperature Range TA -40 -- +125 C (Note 1) Storage Temperature Range TA -65 -- +150 C Thermal Resistance, 20L SSOP JA -- 89.3 -- C/W Thermal Resistance, 20L QFN JA -- 43 -- C/W Temperature Ranges Thermal Package Resistances Note 1: The internal junction temperature (TJ) must not exceed the absolute maximum specification of +150C. CS fSCK tHI tCSH tLO Mode 1,1 SCK Mode 0,0 tDO SDO MSB out tDIS LSB out DON'T CARE SDI FIGURE 1-1: tHO Serial Output Timing Diagram. (c) 2012 Microchip Technology Inc. DS22286A-page 7 MCP3911 tCSD CS tHI Mode 1,1 SCK tCLE fSCK tCSS tCSH tLO tCLD Mode 0,0 tSU SDI tHD MSB in LSB in HI-Z SDO FIGURE 1-2: Serial Input Timing Diagram. 1 / fD tDRP DR tDODR SCK SDO FIGURE 1-3: DS22286A-page 8 Data Ready Pulse / Sampling Timing Diagram. (c) 2012 Microchip Technology Inc. MCP3911 H Waveform for tDIS Timing Waveform for tDO SCK CS VIH tDO 90% SDO SDO tDIS HI-Z 10% Timing Waveform for MDAT0/1 Modulator Output Function OSC1/CLKI tDOMDAT MDAT FIGURE 1-4: Timing Diagrams, continued. (c) 2012 Microchip Technology Inc. DS22286A-page 9 MCP3911 NOTES: DS22286A-page 10 (c) 2012 Microchip Technology Inc. MCP3911 2.0 TYPICAL PERFORMANCE CURVES Note: The graphs and tables provided following this note are a statistical summary based on a limited number of samples and are provided for informational purposes only. The performance characteristics listed herein are not tested or guaranteed. In some graphs or tables, the data presented may be outside the specified operating range (e.g., outside specified power supply range) and therefore outside the warranted range. Note: Unless otherwise indicated, AVDD = 3.3V, DVDD = 3.3V; TA = 25C, MCLK = 4 MHz; PRESCALE = 1; OSR = 256; GAIN = 1; Dithering = Maximum; VIN = -0.5 dBFS @ 60 Hz, VREFEXT = 0; CLKEXT = 1, AZ_FREQ = 0; BOOST = 1X. Spectral Response. FIGURE 2-4: Spectral Response. FIGURE 2-2: Spectral Response. FIGURE 2-5: Spectral Response. Frequen ncy of Occurrence Freque ency of Occurrence FIGURE 2-1: -107.3 -107.1 -107.0 -106.8 -106.7 -106.5 -106.4 -106.2 -106.1 -105.9 -105.8 Total Harmonic Distortion (-dBc) FIGURE 2-3: THD Histogram. (c) 2012 Microchip Technology Inc. 94.2 94.3 94.5 94.6 94.8 94.9 95.1 95.2 95.4 95.5 Signal-to-Noise and Distortion Ratio (dB) FIGURE 2-6: SINAD Histogram. DS22286A-page 11 MCP3911 Unless otherwise indicated, AVDD = 3.3V, DVDD = 3.3V; TA = 25C, MCLK = 4 MHz; PRESCALE = 1; OSR = 256; GAIN = 1; Dithering = Maximum; VIN = -0.5 dBFS @ 60 Hz, VREFEXT = 0; CLKEXT = 1, AZ_FREQ = 0; BOOST = 1X. Freq quencyofOccurrence Freque ency of Occurrence Note: 104.5 15.3 15.4 15.4 15.4 15.5 15.5 15.5 15.5 15.6 15.6 106 107.5 109 110.5 112 113.5 115 Spurious Free Dynamic Range (dBFS) FIGURE 2-10: 15.4 94.5 94.6 94.8 94.9 95.1 95.2 95.4 95.5 95.6 95.8 95.9 Signal to Noise Ratio (dB) 5000 4500 4000 3500 3000 2500 2000 1500 1000 500 0 SNR Histogram. Channel 1 VIN = 0V TA = 25 C 16384 Consecutive Readings 15.4 15.5 FIGURE 2-11: 0 -10 -20 -30 -40 -50 -60 -70 -80 80 -90 -100 -110 -120 DS22286A-page 12 15.5 15.6 15.6 15.6 15.6 ENOB SNR Histogram. Dithering = None Dithering t e g = Medium ed u Dithering = Maximum 32 Noise Histogram. 15.5 Dithering = Minimum Output Code (LSB) FIGURE 2-9: 15.5 EffectiveNumberofBits(SNR) Total Harm monic Distortion (dBc) FIGURE 2-8: Frequ uency Of Occurrence ENOB SINAD Histogram. Freq quencyofOccurrence Frequ uency of Occurrence FIGURE 2-7: Spurious Free Dynamic Range Histogram. EffectiveNumberofBits(SINAD) 64 128 256 512 1024 2048 4096 Oversampling Ratio (OSR) FIGURE 2-12: THD vs. OSR. (c) 2012 Microchip Technology Inc. MCP3911 Unless otherwise indicated, AVDD = 3.3V, DVDD = 3.3V; TA = 25 C, MCLK = 4 MHz; PRESCALE = 1; OSR = 256; GAIN = 1; Dithering = Maximum; VIN = -0.5 dBFS @ 60 Hz, VREFEXT = 0; CLKEXT = 1, AZ_FREQ = 0; BOOST = 1X. 120 110 100 90 80 70 60 50 40 30 20 10 0 Dithering = Maximum Dithering = None Total Harmonic Distortion (dBc) Signal-to o-Noise and Distortion Ratio (dB) Note: Dithering = Medium Dithering = Minimum 32 64 128 256 512 0 -10 -20 -30 -40 -50 -60 -70 -80 -90 90 -100 -110 -120 Boost = 0.5x Boost = 0.66x Boost = 1x Boost = 2x 0 1024 2048 4096 5 10 15 20 MCLK Frequency (MHz) Oversampling Ratio (OSR) FIGURE 2-13: SINAD vs. OSR. FIGURE 2-16: 25 30 THD vs. MCLK. 120 110 100 90 80 70 60 50 40 30 20 10 0 Dithering = Maximum Dithering = None Signal-to--Noise and Distortion Ratio (dB) Signal--to-Noise Ratio (dB) L Dithering = Medium Dithering = Minimum 32 64 128 256 512 1024 120 110 100 90 80 70 60 50 40 30 20 10 0 Boost = 2x Boost = 0.66x Boost = 1x Boost = 0.5x 0 5x 0 2048 4096 5 Oversampling Ratio (OSR) SNR vs.OSR. 140 130 120 110 100 90 80 70 60 50 40 30 20 10 0 Dithering = Maximum Dithering = Medium Dithering = Minimum Dithering = None 32 64 128 256 512 1024 2048 4096 FIGURE 2-17: Signal to Noise Ratio (dB) Spurious Frree Dynamic Range (dBFS) FIGURE 2-14: 120 110 100 90 80 70 60 50 40 30 20 10 0 SFDR vs. OSR. (c) 2012 Microchip Technology Inc. 30 SINAD vs. MCLK. Boost = 2x Boost = 0.66x Boost = 1x Boost = 0.5x 0 Oversampling Ratio (OSR) FIGURE 2-15: 10 15 20 25 MCLK Frequency (MHz) FIGURE 2-18: 5 10 15 20 MCLK Frequency (MHz) 25 30 SNR vs. MCLK. DS22286A-page 13 MCP3911 Unless otherwise indicated, AVDD = 3.3V, DVDD = 3.3 V; TA = 25C, MCLK = 4 MHz; PRESCALE = 1; OSR = 256; GAIN = 1; Dithering = Maximum; VIN = -0.5 dBFS @ 60 Hz, VREFEXT = 0; CLKEXT = 1, AZ_FREQ = 0; BOOST = 1X. 120 110 100 90 80 70 60 50 40 30 20 10 0 Signal to Noise and Distortion Ratio (dB) Spurious Free Dynamic Range (dBFS) Note: Boost = 2x Boost = 0.66x Boost = 1x Boost = 0.5x 0 5 10 15 20 Frequency (MHz) FIGURE 2-19: 25 100 95 Auto Zero Speed = Fast 90 85 Auto Zero Speed = Slow 80 75 70 1 30 2 FIGURE 2-22: Speed Chart. Total Harmo onic Distortion (dBc) 0 -10 -20 -30 -40 -50 -60 -70 80 -80 -90 -100 -110 -120 1 FIGURE 2-21: Off). DS22286A-page 14 2 OSR = 256 4 8 Gain (V/V) 16 OSR = 512 32 SINAD vs. GAIN (Dithering Signal to Noise and Distortion Ratio (dB) Signal to N Noise and Distortion Ratio (dB) R OSR = 4096 OSR = 2048 OSR = 1024 OSR = 128 -5 32 Channel 0 -4 -3 -2 -1 0 1 Input Signal Amplitude (dBFS) FIGURE 2-23: Amplitude. SINAD vs. GAIN. OSR = 32 OSR = 64 16 SINAD vs. GAIN vs. AZ Channel 1 -6 120 110 100 90 80 70 60 50 40 30 20 10 0 8 Gain (V/V) SFDR vs. MCLK. FIGURE 2-20: 4 120 110 100 90 80 70 60 50 40 30 20 10 0 2 3 THD vs. Input Signal Channel 1 Channel 0 -6 -5 FIGURE 2-24: Amplitude. -4 -3 -2 -1 0 1 Input Signal Amplitude (dBFS) 2 3 SINAD vs. Input Signal (c) 2012 Microchip Technology Inc. MCP3911 Unless otherwise indicated, AVDD = 3.3V, DVDD = 3.3V; TA = 25C, MCLK = 4 MHz; PRESCALE = 1; OSR = 256; GAIN = 1; Dithering = Maximum; VIN = -0.5 dBFS @ 60 Hz, VREFEXT = 0; CLKEXT = 1, AZ_FREQ = 0; BOOST = 1X. 100 90 80 70 60 50 40 30 20 10 0 Signal to Noise and Distortion Ration (dB) 120 110 100 90 80 70 60 50 40 30 20 10 0 Channel 1 Channel 0 -6 -5 -4 -3 -2 -1 0 1 Input Signal Amplitude (dBFS) Spurious s Free Dyanmic Raneg (dBFS) FIGURE 2-25: Amplitude. -4 -3 -2 -1 0 1 2 Input Signal Amplitude (dBFS) FIGURE 2-26: Amplitude. 3 -25 FIGURE 2-27: 100 90 80 70 60 50 40 30 20 10 0 Spurious Free Dynamic Range (dBFS) 120 110 100 90 80 70 60 50 40 30 20 10 0 25 50 75 100 Temperature (C) 125 THD vs. Temperature. (c) 2012 Microchip Technology Inc. 150 25 50 75 100 Temperature (C) 125 150 SINAD vs. Temperature. -25 0 FIGURE 2-29: SFDR vs. Input Signal 0 0 G=1 G=2 G=4 G=8 G=16 G=32 -50 G=32 G=8 G=16 G=4 G=2 G=1 -50 -25 FIGURE 2-28: Channel 0 -5 G=1 G=2 G=4 G=8 G=16 G=32 -50 Channel 1 -6 Total Harominc Distortion (dBc) 3 SNR vs. Input Signal 120 110 100 90 80 70 60 50 40 30 20 10 0 0 -10 -20 -30 -40 -50 -60 -70 -80 -90 -100 -110 -120 2 Signal to Noise Ratio (dB) Signal to Noise Ratio (dB) Note: 25 50 75 100 Temperature (C) 125 150 SNR vs. Temperature. G=2 G=1 G=4 G=16 G=8 G=32 -50 -25 FIGURE 2-30: 0 25 50 75 100 Temperature (C) 125 150 SFDR vs. Temperature. DS22286A-page 15 MCP3911 Note: Unless otherwise indicated, AVDD = 3.3V, DVDD = 3.3V; TA = 25C, MCLK = 4 MHz; PRESCALE = 1; OSR = 256; GAIN = 1; Dithering = Maximum; VIN = -0.5 dBFS @ 60 Hz, VREFEXT = 0; CLKEXT = 1, AZ_FREQ = 0; BOOST = 1X. 400 Cha annel 0 Offset (PV) 350 300 G=32 250 G=16 200 G=8 150 G=4 100 50 0 G=1 G=2 -50 -100 -50 -25 0 FIGURE 2-31: Temperature. 25 50 75 Temperature (C) 100 125 150 Channel 0 Offset vs. FIGURE 2-34: Gain Error vs. Temperature. FIGURE 2-35: vs. Temperature. Internal Voltage Reference 400 Cha annel 1 Offset (PV) 350 300 G=32 250 G=16 G=8 G=4 200 150 100 50 0 G=2 -50 G=1 -100 -50 -25 0 FIGURE 2-32: Temperature. 25 50 75 Temperature (C) 100 125 150 Channel 1 Offset vs. Internal Voltage Reference (V) 0 O Offset Error (PV) -20 -40 CHANNEL 1 -60 -80 CHANNEL 0 -100 -120 -50 -25 0 25 50 75 Temperature (C) 100 125 150 1.2003 1.2002 1.2001 1.2000 1.1999 1.1998 1.1997 2.5 2.6 2.7 2.8 2.9 3 3.1 3.2 3.3 3.4 3.5 3.6 VDD (V) FIGURE 2-33: Channel to Channel Offset Match vs. Temperature. DS22286A-page 16 FIGURE 2-36: Internal Voltage Reference vs. Supply Voltage. (c) 2012 Microchip Technology Inc. MCP3911 Note: Unless otherwise indicated, AVDD = 3.3V, DVDD = 3.3V; TA = 25C, MCLK = 4 MHz; PRESCALE = 1; OSR = 256; GAIN = 1; Dithering = Maximum; VIN = -0.5 dBFS @ 60 Hz, VREFEXT = 0; CLKEXT = 1, AZ_FREQ = 0; BOOST = 1X. 4.5 Frequency of Occurrence 4 AIDD, Boost = 2x 3.5 IDD (mA) 3 2.5 2 AIDD, Boost = 1x AIDD, Boost = 0.6x 1.5 5 1 AIDD, Boost = 0.5x 0.5 DIDD, All Boost Settings 0 0 3 6 9 12 15 18 21 Internal Voltage Reference Drift (ppm/C) VREF Drift Data Histogram 25 4 20 3.5 Channel 1 15 10 3 5 2.5 0 -5 10 -10 Channel 0 -15 AIDD, Boost = 1x 1.5 0.5 -25 -0.6 -0.3 0 Input Voltage (V) 0.3 0.6 AIDD, Boost = 2x 2 1 -20 AIDD, Boost = 0.6x AIDD, Boost = 0.5x DIDD, All Boost Settings 0 0 2.5 5 7.5 10 12.5 15 17.5 20 22.5 25 27.5 30 MCLK Frequency (MHz) FIGURE 2-38: Integral Non-Linearity (Dithering Maximum). Integral Non Linearity Error (ppm) FIGURE 2-40: Operating Current vs. MCLK, VDD = 3.3V. IDD (mA) Integral Non Linearity Error (ppm) FIGURE 2-37: Chart. 0 2.5 5 7.5 10 12.5 15 17.5 20 22.5 25 27.5 30 MCLK Frequency (MHz) 24 FIGURE 2-41: Operating Current vs. MCLK, VDD = 2.7V. 25 20 15 Channel 0 10 5 0 -5 10 -10 Channel 1 -15 -20 -25 -0.6 FIGURE 2-39: (Dithering Off). -0.3 0 Input Voltage (V) 0.3 0.6 Integral Non-Linearity (c) 2012 Microchip Technology Inc. DS22286A-page 17 MCP3911 NOTES: DS22286A-page 18 (c) 2012 Microchip Technology Inc. MCP3911 3.0 PIN DESCRIPTION The descriptions of the pins are listed in Table 3-1. TABLE 3-1: PIN FUNCTION TABLE Pin No. SSOP Pin No. QFN Symbol 1 18 RESET 2 19 DVDD 3 20 AVDD Analog Power Supply Pin 4 1 CH0+ Non-Inverting Analog Input Pin for Channel 0 5 2 CH0- Inverting Analog Input Pin for Channel 0 6 3 CH1- Inverting Analog Input Pin for Channel 1 7 4 CH1+ Non-Inverting Analog Input Pin for Channel 1 8 5 AGND Analog Ground Pin, Return Path for internal analog circuitry 9 6 REFIN+/OUT 10 7 REFIN- 3.1 Function Master Reset Logic Input Pin Digital Power Supply Pin Non-Inverting Voltage Reference Input and Internal Reference Output Pin Inverting Voltage Reference Input Pin 11 8 DGND Digital Ground Pin, Return Path for internal digital circuitry 12 9 MDAT1 Modulator Data Output Pin for Channel 1 13 10 MDAT0 Modulator Data Output Pin for Channel 0 14 11 DR 15 12 OSC1/CLKI 16 13 OSC2 17 14 CS Serial Interface Chip Select Pin 18 15 SCK Serial Interface Clock Input Pin 19 16 SDO Serial Interface Data Input Pin 20 17 SDI Serial Interface Data Input Pin - 21 EP Exposed Thermal Pad. Must be connected to AGND. Data Ready Signal Output Pin Oscillator Crystal Connection Pin or External Clock Input Pin Oscillator Crystal Connection Pin Master Reset (RESET) This pin is active low and places the entire chip in a reset state when active. When RESET=0, all registers are reset to their default value, no communication can take place, and no clock is distributed inside the part, except in the input structure if MCLK is applied (if idle, then no clock is distributed). This state is equivalent to a POR state. Since the default state of the ADCs is on, the analog power consumption, when RESET=0, is equivalent to when RESET=1. Only the digital power consumption is largely reduced because this current consumption is essentially dynamic and is reduced drastically when there is no clock running. All the analog biases are enabled during a reset so that the part is fully operational just after a RESET rising edge, if the MCLK is applied during the rising edge. If not applied, there is a small time after RESET where the conversion may not be accurate corresponding to the startup of the charge pump of the input structure. 3.2 Digital VDD (DVDD) DVDD is the power supply pin for the digital circuitry within the MCP3911. This pin requires appropriate bypass capacitors and should be maintained between 2.7V and 3.6V for specified operation. 3.3 Analog VDD (AVDD) AVDD is the power supply pin for the analog circuitry within the MCP3911. This pin requires appropriate bypass capacitors and should be maintained to 2.7V and 3.6V for specified operation. 3.4 ADC Differential Analog inputs (CHn+/CHn-) CH0- and CH0+, and CH1- and CH1+, are the two fully-differential analog voltage inputs for the Delta-Sigma ADCs. This input is Schmitt triggered. (c) 2012 Microchip Technology Inc. DS22286A-page 19 MCP3911 The linear and specified region of the channels are dependent on the PGA gain. This region corresponds to a differential voltage range of 600 mV/GAIN with VREF=1.2V. The maximum differential voltage is proportional to the VREF voltage. The maximum absolute voltage, with respect to AGND, for each CHn+/- input pin is +/-1V with no distortion and 2V with no breaking after continuous voltage. This maximum absolute voltage is not proportional to the VREF voltage. 3.5 Analog Ground (AGND) AGND is the ground connection to internal analog circuitry (See the "Functional block diagram"). To ensure accuracy and noise cancellation, this pin must be connected to the same ground as DGND, preferably with a star connection. If an analog ground plane is available, it is recommended that this pin be tied to this plane of the PCB. This plane should also reference all other analog circuitry in the system. 3.6 Non-inverting Reference Input, Internal Reference Output (REFIN+/OUT) This pin is the non-inverting side of the differential voltage reference input for both ADCs or the internal voltage reference output. When VREFEXT=1, an external voltage reference source can be used, the internal voltage reference is disabled. When using an external differential voltage reference, it should be connected to its VREF+ pin. When using an external single-ended reference, it should be connected to this pin. When VREFEXT=0, the internal voltage reference is enabled and connected to this pin through a switch. This voltage reference has minimal drive capability and thus needs proper buffering and bypass capacitances (a 0.1 F ceramic capacitor is sufficient in most cases) if used as a voltage source. If the voltage reference is only used as an internal VREF, adding bypass capacitance on REFIN+/OUT is not necessary for keeping ADC accuracy, but a minimal 0.1 F ceramic capacitance can be connected to avoid EMI/EMC susceptibility issues due to the antenna created by the REFIN+/OUT pin if left floating. 3.8 DGND is the ground connection to internal digital circuitry (See the MCP3911 Block diagram). To ensure optimal accuracy and noise cancellation, DGND must be connected to the same ground as AGND, preferably with a star connection. If a digital ground plane is available, it is recommended that this pin be tied to this plane of the Printed Circuit Board (PCB). This plane should also reference all other digital circuitry in the system. 3.9 Inverting Reference Input (REFIN-) This pin is the inverting side of the differential voltage reference input for both ADCs. When using an external differential voltage reference, it should be connected to its VREF- pin. When using an external single-ended voltage reference, or when VREFEXT=0 (Default) and using the internal voltage reference, this pin should be directly connected to AGND. DS22286A-page 20 Modulator Data Output Pin for Channel 1 and Channel 0 (MDAT1/ MDAT0) MDAT0 and MDAT1 are the output pins for the modulator serial bitstreams of ADC channels 0 and 1, respectively. These pins are high impedance when their corresponding MODOUT bit is logic low. When the MODOUT<1:0> are enabled, the modulator bitstream of the corresponding channel is present on the pin and updated at the AMCLK frequency. (See Section 5.4 "Modulator Output Block" for a complete description of the modulator outputs). These pins can be directly connected to a MCU or DSP when a specific digital filtering is needed. 3.10 Data Ready Output (DR) The data ready pin indicates if a new conversion result is ready to be read. The default state of this pin is high when DR_HIZ=1 and is high impedance when DR_HIZ=0 (Default). After each conversion is finished, a logic low pulse will take place on the data ready pin to indicate the conversion result is ready as an interrupt. This pulse is synchronous with the master clock and has a defined and constant width. The data ready pin is independent of the SPI interface and acts like an interrupt output. The data ready pin state is not latched and the pulse width (and period) are both determined by the MCLK frequency, over-sampling rate, and internal clock pre-scale settings. The DR pulse width is equal to one DMCLK period and the frequency of the pulses is equal to DRCLK (see Figure 1-3). Note: 3.7 Digital Ground Connection (DGND) This pin should not be left floating when DR_HIZ bit is low; a 100 k pull-up is resistor connected to DVDD recommended. (c) 2012 Microchip Technology Inc. MCP3911 3.11 Oscillator And Master Clock Input Pins (OSC1/CLKI, OSC2) OSC1/CLKI and OSC2 provide the master clock (MCLK) for the device. When CLKEXT=0, a resonant crystal or clock source with a similar sinusoidal waveform must be placed across these pins to ensure proper operation. The typical clock frequency specified is 4 MHz. For proper operation, and for optimizing ADC accuracy, AMCLK should be limited to the maximum frequency defined in the Table 5-3 in function of the BOOST and PGA setting chosen. MCLK can take larger values as long as the prescaler settings (PRE<1:0>) limit AMCLK=MCLK/PRESCALE in the defined range in the Table 5-3. Appropriate load capacitance should be connected to these pins for proper operation. 3.12 Chip Select (CS) This pin is the SPI chip select that enables the serial communication. When this pin is high, no communication can take place. A chip select falling edge initiates the serial communication and a chip select rising edge terminates the communication. No communication can take place even when CS is low when RESET is low. 3.14 Serial Data Output (SDO) This is the SPI data output pin. Data is clocked out of the device on the FALLING edge of SCK. This pin stays high impedance during the first command byte. It also stays high impedance during the whole communication for write commands and when CS pin is high or when RESET pin is low. This pin is active only when a read command is processed. Each read is processed by packet of 8 bits. 3.15 Serial Data Input (SDI) This is the SPI data input pin. Data is clocked into the device on the RISING edge of SCK. When CS is low, this pin is used to communicate with a series of 8-bit commands. The interface is half-duplex (inputs and outputs do not happen at the same time). Each communication starts with a chip select falling edge followed by an 8-bit command word entered through the SDI pin. Each command is either a Read or a Write command. Toggling SDI during a Read command has no effect. This input is Schmitt triggered. This input is Schmitt-triggered. 3.13 Serial Data Clock (SCK) This is the serial clock pin for SPI communication. Data is clocked into the device on the RISING edge of SCK. Data is clocked out of the device on the FALLING edge of SCK. The MCP3911 interface is compatible with both SPI 0,0 and 1,1 modes. SPI modes can be changed during a CS high time. The maximum clock speed specified is 20 MHz. This input is Schmitt triggered. (c) 2012 Microchip Technology Inc. DS22286A-page 21 MCP3911 NOTES: DS22286A-page 22 (c) 2012 Microchip Technology Inc. MCP3911 4.0 TERMINOLOGY AND FORMULAS This section defines the terms and formulas used throughout this data sheet. The following terms are defined: MCLK - Master Clock 4.1 MCLK - Master Clock This is the fastest clock present in the device. This is the frequency of the crystal placed at the OSC1/OSC2 inputs when CLKEXT=0 or the frequency of the clock input at the OSC1/CLKI when CLKEXT=1. See Figure 4-1. AMCLK - Analog Master Clock 4.2 DMCLK - Digital Master Clock This is the clock frequency that is present on the analog portion of the device, after prescaling has occurred via the CONFIG PRE<1:0> register bits. The analog portion includes the PGAs and the two Delta-Sigma modulators. DRCLK - Data Rate Clock OSR - Oversampling Ratio Offset Error AMCLK - Analog Master Clock Gain Error MCLK AMCLK = ------------------------------PRESCALE Integral Non-Linearity Error Signal-To-Noise Ratio (SNR) Signal-To-Noise Ratio And Distortion (SINAD) TABLE 4-1: Total Harmonic Distortion (THD) Spurious-Free Dynamic Range (SFDR) MCP3911 Delta-Sigma Architecture Idle Tones MCP3911 OVERSAMPLING RATIO SETTINGS Config PRE<1:0> Dithering Crosstalk PSRR Analog Master Clock Prescale 0 0 AMCLK = MCLK/ 1 (default) 0 1 AMCLK = MCLK/ 2 1 0 AMCLK = MCLK/ 4 1 1 AMCLK = MCLK/ 8 CMRR ADC Reset Mode Hard Reset Mode (RESET = 0) ADC Shutdown Mode Full Shutdown Mode FIGURE 4-1: 4.3 Clock Sub-circuitry. DMCLK - Digital Master Clock This is the clock frequency that is present on the digital portion of the device, after prescaling and division by 4. This is also the sampling frequency, that is the rate at which the modulator outputs are refreshed. Each period of this clock corresponds to one sample and one modulator output. See Figure 4-1. EQUATION 4-1: AMCLK MCLK DMCLK = --------------------- = ---------------------------------------4 4 x PRESCALE (c) 2012 Microchip Technology Inc. 4.4 DRCLK - Data Rate Clock This is the output data rate, i.e., the rate at which the ADCs output new data. Each new data is signaled by a data ready pulse on the DR pin. This data rate is depending on the OSR and the prescaler with the following formula: EQUATION 4-2: DMCLK AMCLK MCLK DRCLK = ---------------------- = --------------------- = ----------------------------------------------------------OSR 4 x OSR 4 x OSR x PRESCALE DS22286A-page 23 MCP3911 Since this is the output data rate, and since the decimation filter is a SINC (or notch) filter, there is a notch in the filter transfer function at each integer multiple of this rate. TABLE 4-2: PRE <1:0> The following table describes the various combinations of OSR and PRESCALE and their associated AMCLK, DMCLK and DRCLK rates. DEVICE DATA RATES IN FUNCTION OF MCLK, OSR, AND PRESCALE, MCLK=4MHZ OSR <2:0> OSR AMCLK DMCLK DRCLK DRCLK (ksps) SINAD (dB) Note 1 MCLK/8 MCLK/32 MCLK/131072 0.035 98 ENOB from SINAD (bits) Note 1 16 1 1 1 1 1 4096 1 1 1 1 1 2048 MCLK/8 MCLK/32 MCLK/65536 0.061 98 16 1 1 1 1 1 1024 MCLK/8 MCLK/32 MCLK/32768 0.122 97 15.8 1 1 1 1 1 512 MCLK/8 MCLK/32 MCLK/16384 0.244 96 15.6 1 1 0 1 1 256 MCLK/8 MCLK/32 MCLK/8192 0.488 95 15.5 1 1 0 1 0 128 MCLK/8 MCLK/32 MCLK/4096 0.976 90 14.7 1 1 0 0 1 64 MCLK/8 MCLK/32 MCLK/2048 1.95 83 13.5 1 1 0 0 0 32 MCLK/8 MCLK/32 MCLK/1024 3.9 70 11.3 1 0 1 1 1 4096 MCLK/4 MCLK/16 MCLK/65536 0.061 98 16 1 0 1 1 1 2048 MCLK/4 MCLK/16 MCLK/32768 0.122 98 16 1 0 1 1 1 1024 MCLK/4 MCLK/16 MCLK/16384 0.244 97 15.8 1 0 1 1 1 512 MCLK/4 MCLK/16 MCLK/8192 0.488 96 15.6 1 0 0 1 1 256 MCLK/4 MCLK/16 MCLK/4096 0.976 95 15.5 1 0 0 1 0 128 MCLK/4 MCLK/16 MCLK/2048 1.95 90 14.7 1 0 0 0 1 64 MCLK/4 MCLK/16 MCLK/1024 3.9 83 13.5 1 0 0 0 0 32 MCLK/4 MCLK/16 MCLK/512 7.8125 70 11.3 0 1 1 1 1 4096 MCLK/2 MCLK/8 MCLK/32768 0.122 98 16 0 1 1 1 1 2048 MCLK/2 MCLK/8 MCLK/16384 0.244 98 16 0 1 1 1 1 1024 MCLK/2 MCLK/8 MCLK/8192 0.488 97 15.8 0 1 1 1 1 512 MCLK/2 MCLK/8 MCLK/4096 0.976 96 15.6 0 1 0 1 1 256 MCLK/2 MCLK/8 MCLK/2048 1.95 95 15.5 0 1 0 1 0 128 MCLK/2 MCLK/8 MCLK/1024 3.9 90 14.7 0 1 0 0 1 64 MCLK/2 MCLK/8 MCLK/512 7.8125 83 13.5 0 1 0 0 0 32 MCLK/2 MCLK/8 MCLK/256 15.625 70 11.3 0 0 1 1 1 4096 MCLK MCLK/4 MCLK/16384 0.244 98 16 0 0 1 1 0 2048 MCLK MCLK/4 MCLK/8192 0.488 98 16 0 0 1 0 1 1024 MCLK MCLK/4 MCLK/4096 0.976 97 15.8 0 0 1 0 0 512 MCLK MCLK/4 MCLK/2048 1.95 96 15.6 0 0 0 1 1 256 MCLK MCLK/4 MCLK/1024 3.9 95 15.5 0 0 0 1 0 128 MCLK MCLK/4 MCLK/512 7.8125 90 14.7 0 0 0 0 1 64 MCLK MCLK/4 MCLK/256 15.625 83 13.5 0 0 0 0 0 32 MCLK MCLK/4 MCLK/128 31.25 70 11.3 Note 1: For OSR = 32 and 64, DITHER = None. For OSR = 128 and higher, DITHER = Maximum. The SINAD values are given from GAIN = 1. DS22286A-page 24 (c) 2012 Microchip Technology Inc. MCP3911 4.5 OSR - Oversampling Ratio 4.8 Integral Non-Linearity Error This is the ratio of the sampling frequency to the output data rate. OSR= DMCLK/DRCLK. The default OSR is 256, or with MCLK = 4 MHz, PRESCALE = 1, AMCLK = 4 MHz, fS = 1 MHz, fD = 3.90625 ksps. The following bits in the CONFIG register are used to change the oversampling ratio (OSR). Integral non-linearity error is the maximum deviation of an ADC transition point from the corresponding point of an ideal transfer function, with the offset and gain errors removed, or with the end points equal to zero. TABLE 4-3: 4.9 MCP3911 OVERSAMPLING RATIO SETTINGS CONFIG OSR<2:0> OVER SAMPLING RATIO OSR 0 0 0 32 0 0 1 64 0 1 0 128 0 1 1 256 (DEFAULT) 1 0 0 512 1 0 1 1024 1 1 0 2048 1 1 1 4096 It is the maximum remaining error after calibration of offset and gain errors for a DC input signal. For the MCP3911 ADCs, the signal-to-noise ratio is a ratio of the output fundamental signal power to the noise power (not including the harmonics of the signal), when the input is a sinewave at a predetermined frequency. It is measured in dB. Usually, only the maximum signal to noise ratio is specified. The SNR figure depends mainly on the OSR and DITHER settings of the device. EQUATION 4-3: Offset Error SIGNAL-TO-NOISE RATIO SignalPower SNR ( dB ) = 10 log ---------------------------------- NoisePower 4.10 4.6 Signal-To-Noise Ratio (SNR) Signal-To-Noise Ratio And Distortion (SINAD) This is the error induced by the ADC when the inputs are shorted together (VIN = 0V). The specification incorporates both PGA and ADC offset contributions. This error varies with PGA and OSR settings. The offset is different on each channel and varies from chip to chip. The offset is specified in V. The offset error can be digitally compensated independently on each channel through the OFFCAL registers with a 24-bit calibration word. The most important figure of merit for the analog performance of the ADCs present on the MCP3911 is the Signal-to-Noise And Distortion (SINAD) specification. The offset on the MCP3911 has a low temperature coefficient, see typical performance curves for more information, Figure 2-33. EQUATION 4-4: 4.7 Signal-to-noise and distortion ratio is similar to signalto-noise ratio, with the exception that you must include the harmonics power in the noise power calculation. The SINAD specification depends mainly on the OSR and DITHER settings. SINAD EQUATION SignalPower SINAD ( dB ) = 10 log -------------------------------------------------------------------- Noise + HarmonicsPower Gain Error This is the error induced by the ADC on the slope of the transfer function. It is the deviation expressed in % compared to the ideal transfer function defined by Equation 5-3. The specification incorporates both PGA and ADC gain error contributions, but not the VREF contribution (it is measured with an external VREF). This error varies with PGA and OSR settings. The gain error can be digitally compensated independently on each channel through the GAINCAL registers with a 24-bit calibration word. The calculated combination of SNR and THD per the following formula also yields SINAD: EQUATION 4-5: SINAD, THD, AND SNR RELATIONSHIP SINAD ( dB ) = 10 log 10 SNR - ---------10 + 10 THD - --------------10 The gain error on the MCP3911 has a low temperature coefficient; for more information, see Figure 2-34. (c) 2012 Microchip Technology Inc. DS22286A-page 25 MCP3911 4.11 Total Harmonic Distortion (THD) The total harmonic distortion is the ratio of the output harmonics power to the fundamental signal power for a sinewave input and is defined by the following equation. EQUATION 4-6: HarmonicsPower THD ( dB ) = 10 log ----------------------------------------------------- FundamentalPower The THD calculation includes the first 35 harmonics for the MCP3911 specifications. The THD is usually only measured with respect to the 10 first harmonics. THD is sometimes expressed in %. For converting the THD in %, here is the formula: EQUATION 4-7: THD ( % ) = 100 x 10 THD ( dB ) -----------------------20 This specification depends mainly on the DITHER setting. 4.12 Spurious-Free Dynamic Range (SFDR) The ratio between the output power of the fundamental and the highest spur in the frequency spectrum. The spur frequency is not necessarily a harmonic of the fundamental even though it is usually the case. This figure represents the dynamic range of the ADC when a full-scale signal is used at the input. This specification depends mainly on the DITHER setting. EQUATION 4-8: FundamentalPower SFDR ( dB ) = 10 log ----------------------------------------------------- HighestSpurPower 4.13 MCP3911 Delta-Sigma Architecture The MCP3911 incorporates two Delta-Sigma ADCs with a multi-bit architecture. A Delta-Sigma ADC is an oversampling converter that incorporates a built-in modulator which is digitizing the quantity of charge integrated by the modulator loop (see Figure 5-1). The quantizer is the block that is performing the analog-to-digital conversion. The quantizer is typically 1-bit, or a simple comparator which helps to maintain the linearity performance of the ADC (the DAC structure is, in this case, inherently linear). modulator or the OSR which leads to better SNR figures. However, typically, the linearity of such architectures is more difficult to achieve since the DAC is no more simple to realize and its linearity limits the THD of such ADCs. The MCP3911's 5-level quantizer is a flash ADC composed of four comparators arranged with equally spaced thresholds and a thermometer coding. The MCP3911 also includes proprietary 5-level DAC architecture that is inherently linear for improved THD figures. 4.14 Idle Tones A Delta-Sigma converter is an integrating converter. It also has a finite quantization step (LSB) which can be detected by its quantizer. A DC input voltage that is below the quantization step should only provide an all zeros result since the input is not large enough to be detected. As an integrating device, any Delta-Sigma will show in this case idle tones. This means that the output will have spurs in the frequency content that are depending on the ratio between quantization step voltage and the input voltage. These spurs are the result of the integrated sub-quantization step inputs that will eventually cross the quantization steps after a long enough integration. This will induce an AC frequency at the output of the ADC and can be shown in the ADC output spectrum. These idle tones are residues that are inherent to the quantization process and the fact that the converter is integrating at all times without being reset. They are residues of the finite resolution of the conversion process. They are very difficult to attenuate and they are heavily signal dependent. They can degrade both SFDR and THD of the converter, even for DC inputs. They can be localized in the baseband of the converter and thus difficult to filter from the actual input signal. For power metering applications, idle tones can be very disturbing because energy can be detected even at the 50 or 60 Hz frequency, depending on the DC offset of the ADCs, while no power is really present at the inputs. The only practical way to suppress or attenuate idle tones phenomenon is to apply dithering to the ADC. The idle tones amplitudes are a function of the order of the modulator, the OSR and the number of levels in the quantizer of the modulator. A higher order, a higher OSR or a higher number of levels for the quantizer will attenuate the idle tones amplitude. Multi-bit quantizers help to lower the quantization error (the error fed back in the loop can be very large with 1-bit quantizers) without changing the order of the DS22286A-page 26 (c) 2012 Microchip Technology Inc. MCP3911 4.15 Dithering In order to suppress, or attenuate, the idle tones present in any Delta-Sigma ADCs, dithering can be applied to the ADC. Dithering is the process of adding an error to the ADC feedback loop in order to "decorrelate" the outputs and "break" the idle tones behavior. Usually a random or pseudo-random generator adds an analog or digital error to the feedback loop of the Delta-Sigma ADC in order to ensure that no tonal behavior can happen at its outputs. This error is filter by the feedback loop and typically has a zero average value so that the converter static transfer function is not disturbed by the dithering process. However, the dithering process slightly increases the noise floor (it adds noise to the part) while reducing its tonal behavior and thus improving SFDR and THD. (See Figure 2-14 and Figure 2-18). The dithering process scrambles the idle tones into baseband white noise and ensures that dynamic specs (SNR, SINAD, THD, SFDR) are less signal dependent. The MCP3911 incorporates a proprietary dithering algorithm on both ADCs in order to remove idle tones and improve THD, which is crucial for power metering applications. 4.16 Crosstalk The crosstalk is defined as the perturbation caused by one ADC channel on the other ADC channel. It is a measurement of the isolation between the two ADCs present in the chip. Step 2 * CH0+=CH0-=AGND * CH1+ - CH1-=1.2VP-P @ 50/60 Hz (Full-scale sine wave) The crosstalk is then calculated with the following formula: EQUATION 4-9: CH0Power CTalk ( dB ) = 10 log --------------------------------- CH1Power 4.17 This is the ratio between a change in the power supply voltage and the ADC output codes. It measures the influence of the power supply voltage on the ADC outputs. The PSRR specification can be DC (the power supply is taking multiple DC values) or AC (the power supply is a sinewave at a certain frequency with a certain common mode). In AC, the amplitude of the sinewave is representing the change in the power supply. It is defined as: EQUATION 4-10: V OUT PSRR ( dB ) = 20 log ------------------- AVDD This measurement is a two-step procedure: 1. 2. Measure one ADC input with no perturbation on the other ADC (ADC inputs shorted). Measure the same ADC input with a perturbation sine wave signal on the other ADC at a certain predefined frequency. The crosstalk is then the ratio between the output power of the ADC when the perturbation is present and when it is not divided by the power of the perturbation signal. A lower crosstalk value implies more independence and isolation between the two channels. The measurement of this signal is performed under the default conditions at MCLK = 4 MHz: * * * * GAIN = 1, PRESCALE = 1, OSR = 256, MCLK = 4 MHz Step 1 PSRR Where VOUT is the equivalent input voltage that the output code translates to with the ADC transfer function. In the MCP3911 specification, AVDD varies from 2.7V to 3.6V, and for AC PSRR a 50/60 Hz sinewave is chosen centered around 3.3V with a maximum 300 mV amplitude. The PSRR specification is measured with AVDD = DVDD. 4.18 CMRR This is the ratio between a change in the common-mode input voltage and the ADC output codes. It measures the influence of the common-mode input voltage on the ADC outputs. The CMRR specification can be DC (the common-mode input voltage is taking multiple DC values) or AC (the common-mode input voltage is a sinewave at a certain frequency with a certain common mode). In AC, the amplitude of the sinewave is representing the change in the power supply. It is defined as: * CH0+=CH0-=AGND * CH1+=CH1-=AGND (c) 2012 Microchip Technology Inc. DS22286A-page 27 MCP3911 EQUATION 4-11: VOUT CMRR ( dB ) = 20 log ----------------- VCM input leakage currents can be observed for highly negative input voltages (typically below -0.6V referred to AGND). 4.20 Where VCM= (CHn+ + CHn-)/2 is the common-mode input voltage and VOUT is the equivalent input voltage that the output code translates to with the ADC transfer function. In the MCP3911 specification, VCM varies from -1V to +1V. 4.19 ADC Reset Mode ADC Reset mode (called also soft reset mode) can only be entered through setting high the RESET<1:0> bits in the configuration register. This mode is defined as the condition where the converters are active but their output is forced to 0. The registers are not affected in this reset mode and retain their except the data registers of the corresponding channel which are reset to 0. The ADCs can immediately output meaningful codes after leaving reset mode (and after the sinc filter settling time). This mode is both entered and exited through setting of bits in the configuration register. Each converter can be placed in soft reset mode independently. The configuration registers are not modified by the soft reset mode. A data ready pulse will not be generated by any ADC while in reset mode. Reset mode also effects the modulator output block, i.e., the MDAT pin, corresponding to the channel in reset. If enabled, it provides a bitstream corresponding to a zero output (a series of 0011 bits continuously repeated). When an ADC exits ADC reset mode, any phase delay present before reset was entered will still be present. If one ADC was not in reset, the ADC leaving reset mode will resynchronize automatically the phase delay relative to the other ADC channel per the phase delay register block and give data ready pulses accordingly. If an ADC is placed in Reset mode while the other is converting, it is not shutting down the internal clock. When going back out of reset, it will be resynchronized automatically with the clock that did not stop during reset. Hard Reset Mode (RESET = 0) This mode is only available during a POR or when the RESET pin is pulled low. The RESET pin low state places the device in a hard reset mode. In this mode all internal registers are reset to their default state. The DC biases for the analog blocks are still active, i.e., the MCP3911 is ready to convert. However, this pin clears all conversion data in the ADCs. In this mode, the MDAT outputs are in high impedance. The comparator's outputs of both ADCs are forced to their reset state (0011). The SINC filters are all reset, as well as their double output buffers. See serial timing for minimum pulse low time, in Section 1.0 "Electrical Characteristics". During a hard reset, no communication with the part is possible. The digital interface is maintained in a reset state. During this state, the clock MCLK can be applied to the part in order to properly bias the input structures of both channels. If not applied, large analog input leakage currents can be observed for highly negative input signals and after removing the RESET state a certain start up time is necessary to bias the input structure properly. During this delay the ADC conversions can be inaccurate. 4.21 ADC Shutdown Mode ADC shutdown mode is defined as a state where the converters and their biases are off, consuming only leakage current. When Shutdown bit is reset to 0, the analog biases will be enabled, as well as the clock and the digital circuitry. The ADC will give a data ready after the SINC filter settling time has occurred. However, since the analog biases are not completely settled at the beginning of the conversion, the sampling may not be accurate during about 1 ms (corresponding to the settling time of the biasing in worst case conditions). In order to guarantee the accuracy, the data ready pulse, coming within the delay of 1 ms + settling time of the SINC filter, should be discarded. If both ADCs are in soft reset the clock is no longer distributed to the digital core for low power operation. Once any of the ADC is back to normal operation, the clock is automatically distributed again. Each converter can be placed in shutdown mode independently. The CONFIG registers are not modified by the shutdown mode. This mode is only available through programming of the SHUTDOWN<1:0> bits the CONFIG register. However, when the two channels are in soft reset, the input structure is still clocking if MCLK is applied in order to bias properly the inputs so that no leakage current is observed. If MCLK is not applied, large analog The output data is flushed to all zeros while in ADC shutdown. No data ready pulses are generated by any ADC while in ADC shutdown mode. DS22286A-page 28 (c) 2012 Microchip Technology Inc. MCP3911 ADC shutdown mode also effects the modulator output block, i.e., if MDAT of the channel in shutdown mode is enabled, this pin will provide a bitstream corresponding to a zero output (series of 0011 bits continuously repeated). When an ADC exits ADC shutdown mode, any phase delay present before shutdown was entered will still be present. If one ADC was not in shutdown, the ADC leaving shutdown mode will automatically resynchronize the phase delay, relative to the other ADC channel, per the phase delay register block and give data ready pulses accordingly. If an ADC is placed in shutdown mode while the other is converting, it is not shutting down the internal clock. When going back out of shutdown, it will be resynchronized automatically with the clock that did not stop during reset. If both ADCs are ADC shutdown modes, the clock is no more distributed to the digital core for low power operation. The clock is no more distributed to the input structure too. This can cause potential high analog input leakage currents at the analog inputs if the input voltage is highly negative (typically below -0.6V, referred to AGND). Once any of the ADC is back to normal operation, the clock is automatically distributed again. 4.22 Full Shutdown Mode The lowest power consumption can be achieved when SHUTDOWN<1:0>=11, VREFEXT=CLKEXT=1. This mode is called "Full shutdown mode", and no analog circuitry is enabled. In this mode, both AVDD and DVDD POR monitoring are also disabled. No clock is propagated throughout the chip. Both ADCs are in shutdown, and the internal voltage reference is disabled. The clock is no more distributed to the input structure too. This can cause potential high analog inputs leakage currents at the analog inputs if the input voltage is highly negative (typically below -0.6V, referred to AGND). The only circuit that remains active is the SPI interface but this circuit does not induce any static power consumption. If SCK is idle, the only current consumption comes from the leakage currents induced by the transistors and is less than 1 A on each power supply. This mode can be used to power down the chip completely and avoid power consumption when there is no data to convert at the analog inputs. Any SCK or MCLK edge coming while in this mode will induce dynamic power consumption. Once any of the SHUTDOWN, CLKEXT and VREFEXT bits return to 0, the two POR monitoring blocks are back to operation and AVDD and DVDD monitoring can take place. When exiting full Shutdown mode, the device resets to its default configuration state. The Configuration bits all reset to their default value, and the ADCs reset to their initial state, requiring 3 DRCLK periods for an initial data ready pulse. Exiting full Shutdown mode is effectively identical to an internal reset or returning from a POR condition. (c) 2012 Microchip Technology Inc. DS22286A-page 29 MCP3911 NOTES: DS22286A-page 30 (c) 2012 Microchip Technology Inc. MCP3911 5.0 DEVICE OVERVIEW 5.1 Analog Inputs (CHn+/-) The MCP3911 analog inputs can be connected directly to current and voltage transducers (such as shunts, current transformers, or Rogowski coils). Each input pin is protected by specialized ESD structures that are certified to pass 4.0 kV HBM and 200V MM contact charge. These structures allow bipolar 2V continuous voltage with respect to AGND, to be present at their inputs without the risk of permanent damage. Both channels have fully differential voltage inputs for better noise performance. The absolute voltage at each pin, relative to AGND, should be maintained in the 1V range during operation, in order to ensure the specified ADC accuracy. The common-mode signals should be adapted to respect both the previous conditions and the differential input voltage range. For best performance, the common-mode signals should be maintained to AGND. Note: 5.2 If the analog inputs are held to a potential of -0.6 to -1V, for extended periods of time, the clock MCLK must be present inside the device in order to avoid large leakage currents at the analog inputs. This is true even during the hard reset mode or the soft reset of both ADCs. However during shutdown mode of the two ADCs or POR state, the clock is not distributed inside the circuit. During these states, it is recommended to keep the analog input voltages above -0.6V referred to AGND, to avoid high analog inputs leakage currents. Programmable Gain Amplifiers (PGA) TABLE 5-1: PGA CONFIGURATION SETTING Gain PGA_CHn<2:0> Gain (dB) 0 VIN Range (V) 0 0 0 1 0 0 1 2 6 0.3 0 1 0 4 12 0.15 0 1 1 8 18 0.075 1 0 0 16 24 0.0375 0.6 1 0 1 32 30 0.01875 Note: The 2 undefined settings are G=1; this table is defined with VREF = 1.2V. 5.3 Delta-Sigma Modulator 5.3.1 ARCHITECTURE Both ADCs are identical in the MCP3911, and they include a proprietary second-order modulator with a multi-bit 5-level DAC architecture (see Figure 5-1). The quantizer is a flash ADC composed of four comparators, with equally spaced thresholds, and a thermometer output coding. The proprietary 5-level architecture ensures minimum quantization noise at the outputs of the modulators without disturbing linearity or inducing additional distortion. The sampling frequency is DMCLK (typically 1 MHz with MCLK=4 MHz) so the modulator outputs are refreshed at a DMCLK rate. The modulator outputs are available in the MOD register or serially transferred on each MDAT pin. Figure 5-1 represents a simplified block diagram of the Delta-Sigma ADC present on MCP3911. Loop Filter Quantizer Output Differential SecondOrder Integrator The two Programmable Gain Amplifiers (PGAs) reside at the front-end of each Delta-Sigma ADC. They have two functions: translate the common-mode of the input from AGND to an internal level between AGND and AVDD, and amplify the input differential signal. The translation of the common mode does not change the differential signal but recenters the common-mode so that the input signal can be properly amplified. Voltage Input The PGA block can be used to amplify very low signals, but the differential input range of the Delta-Sigma modulator must not be exceeded. The PGA is controlled by the PGA_CHn<2:0> bits in the GAIN register. The following table represents the gain settings for the PGA: FIGURE 5-1: Block Diagram. (c) 2012 Microchip Technology Inc. Gain (V/V) Bitstream 5-level Flash ADC DAC MCP3911 Delta-Sigma Modulator 5.3.2 Simplified Delta-Sigma ADC MODULATOR INPUT RANGE AND SATURATION POINT For a specified voltage reference value of 1.2V, the modulators specified differential input range is 600 mV. The input range is proportional to VREF and scales according to the VREF voltage. This range is guaranteeing the stability of the modulator over amplitude and frequency. Outside of this range, the DS22286A-page 31 MCP3911 modulator is still functional, however its stability is no longer guaranteed and therefore it is not recommended to exceed this limit (see FIGURE 2-24: "SINAD vs. Input Signal Amplitude." for extended dynamic range performance limitations). The saturation point for the modulator is VREF/1.5 since the transfer function of the ADC includes a gain of 1.5 by default (independent from the PGA setting. See Section 5.6 "ADC Output Coding"). 5.3.3 MCLK. This can be programmed through the BOOST<1:0> bits which are applied to both channels simultaneously. The maximum achievable analog master clock speed (AMCLK) and the maximum sampling frequency (DMCLK), and therefore the maximum achievable data rate (DRCLK), highly depend on BOOST<1:0> and PGA_CHn<2:0> settings. The following table specifies the maximum AMCLK possible to keep optimal accuracy in function of BOOST<1:0> and PGA_CHn<2:0> settings. BOOST SETTINGS The Delta-Sigma modulators include a programmable biasing circuit in order to further adjust the power consumption to the sampling speed applied through the TABLE 5-2: MAXIMUM AMCLK LIMITS AS A FUNCTION OF BOOST AND PGA GAIN Conditions VDD = 3.0V to 3.6V, TA from -40C to 125C VDD = 2.7V to 3.6V, TA from -40C to 125C Maximum AMCLK Maximum AMCLK (MHz) (SINAD (MHz) (SINAD within within -3 dB from 5 dB from its its maximum) maximum) Boost Gain Maximum AMCLK (MHz) (SINAD within -3 dB from its maximum) Maximum AMCLK (MHz) (SINAD within -5 dB from its maximum) 0.5x 1 3 3 0.66x 1 4 4 4 4 1x 1 10 10 10 10 3 3 2x 1 16 16 16 16 0.5x 2 2.5 3 3 3 0.66x 2 4 4 4 4 1x 2 10 10 10 10 2x 2 14.5 16 13.3 14.5 0.5x 4 2.5 2.5 2.5 2.5 0.66x 4 4 4 4 4 1x 4 10 10 8 10 2x 4 13.3 16 10.7 11.4 0.5x 8 2.5 2.5 2.5 2.5 0.66x 8 4 4 4 4 1x 8 10 11.4 6.7 8 2x 8 10 14.5 8 8 0.5x 16 2 2 2 2 0.66x 16 4 4 4 4 1x 16 10.6 10.6 8 10 2x 16 12.3 16 8 10.7 0.5x 32 2 2 2 2 0.66x 32 4 4 4 4 1x 32 10 11.4 8 10 2x 32 13.3 16 8 10 DS22286A-page 32 (c) 2012 Microchip Technology Inc. MCP3911 5.3.4 AUTOZEROING FREQUENCY SETTING (AZ_FREQ) The MCP3911 modulators include an autozeroing algorithm to improve the offset error performance and greatly diminish 1/f noise in the ADC. This algorithm permits it to reach very high SNR and flattens the noise spectrum at the output of the ADC (see performance graphs Figure 2-1, Figure 2-2, Figure 2-3 and Figure 24). This autozeroing algorithm is performed synchronously with the MCLK coming to the device, and its rate can be adjusted throughout the AZ_FREQ bit in the CONFIG register. When AZ_FREQ=0 (default) the autozeroing is happening at the slowest rate, which diminishes the 1/f noise while not impacting the THD performance. This mode is recommended for low values of the PGA gain (GAIN=1x or 2x). When AZ_FREQ=1, the autozeroing is happening at the fastest rate, which further diminishes the 1/f noise and further improves the SNR, especially at higher gain settings. The THD may slightly be impacted in this mode (see Figure 2-22). This mode is recommended for higher PGA gain settings to improve SNR (GAIN superior or equal to 4x). 5.3.5 DITHER SETTINGS Both modulators also include a dithering algorithm that can be enabled through the DITHER<1:0> bits in the configuration register. This dithering process improves THD and SFDR (for high OSR settings) while increasing slightly the noise floor of the ADCs. For power metering applications and applications that are distortion-sensitive, it is recommended to keep DITHER at maximum settings for best THD and SFDR performance. In the case of power metering applications, THD and SFDR are critical specifications. Optimizing SNR (noise floor) is not really problematic due to large averaging factor at the output of the ADCs, therefore even for low OSR settings, the dithering algorithm will show a positive impact on the performance of the application. (c) 2012 Microchip Technology Inc. 5.4 Modulator Output Block If the user wishes to use the modulator output of the device, the appropriate bits to enable the modulator output must be set in the configuration register. When MODOUT<1:0> bits are enabled, the modulator output of the corresponding channel is present at the corresponding MDAT output pin as soon as the command is placed. Additionally, the corresponding SINC filter is disabled in order to consume less current. The corresponding DR pulse is also not present at the DR output pin. When MODOUT<1:0> bits are cleared, the corresponding SINC filters are back to normal operation and the corresponding MDAT outputs are in high impedance. Since the Delta-Sigma modulators have a 5-level output given by the state of four comparators with thermometer coding, their outputs can be represented on four bits, each bit giving the state of the corresponding comparator (See Table 5-3). These bits are present on the MOD register and are updated at the DMCLK rate. In order to output the comparators result on a separate pin (MDAT0 and MDAT1), these comparator output bits have been arranged to be serially output at the AMCLK rate (See Figure 5-2). This 1-bit serial bitstream is the same that would be produced by a 1-bit DAC modulator with a sampling frequency of AMCLK. The modulator can either be considered like a 5 level-output at DMCLK rate, or 1-bit output at AMCLK rate. These two representations are interchangeable. The MDAT outputs can therefore be used in any application that requires 1-bit modulator outputs. These applications will often integrate and filter the 1-bit output with SINC, or more complex decimation filters computed by a MCU or a DSP. TABLE 5-3: DELTA-SIGMA MODULATOR CODING Comp<3:0> Code Modulator Output Code MDAT Serial Stream 1111 +2 1111 0111 +1 0111 0011 0 0011 0001 -1 0001 0000 -2 0000 DS22286A-page 33 MCP3911 Since the reset and shutdown SPI commands are asynchronous, the MDAT pins are resynchronized with DMCLK after each time the part goes out of reset and shutdown. This means that the first output of MDAT, after a soft reset or a shutdown, is always 0011 after the first DMCLK rising edge. The two MDAT output pins are in high impedance if the RESET pin is low. COMP COMP COMP COMP <0> <1> <3> <2> AMCLK DMCLK 5.5 MDAT+2 SINC3 + SINC1 Filter The decimation filter present in both channels of the MCP3911 is a cascade of two sinc filters (sinc3+sinc1): a third order sinc filter with a decimation ratio of OSR3 followed by first order sinc filter with a decimation ratio of OSR1 (moving average of OSR1 values). Figure 5-3 represents the decimation filter architecture. MDAT+1 MDAT+0 MDAT-1 MDAT-2 FIGURE 5-2: MDAT Serial Outputs in Function of the Modulator Output Code. OSR1=1 Modulator Output SINC3 SINC1 4 Decimation Filter Output 16 (WIDTH=0) 24 (WIDTH=1) OSR3 OSR1 Decimation Filter FIGURE 5-3: MCP3911 Decimation Filter Block Diagram. The formula for calculating the transfer function of the digital decimation filter and settling time of the ADC is as follows: EQUATION 5-1: SINC FILTER TRANSFER FUNCTION 3 1 - z - OSR1 x OSR 3 1 - z - OSR 3 H ( z ) = --------------------------------------------- x -----------------------------------------------------------, where 3 - 1 - OSR 3 ( OSR 3 ( 1 - z ) ) OSR x 1 - z 1 z = EXP ( 2 j f in DMCLK ) DS22286A-page 34 (c) 2012 Microchip Technology Inc. MCP3911 EQUATION 5-2: SETTING TIME OF THE ADC AS A FUNCTION OF DMCLK PERIODS SettlingTime ( DMCLKPeriods ) = 3 x OSR3 + ( OSR1 - 1 ) x OSR 3 The SINC1 filter following the SINC3 filter is only enabled for the high OSR settings. This SINC1 filter provides additional rejection at a low cost with little modification to the -3 dB bandwidth. For 24-Bit Output mode (WIDTH = 1), the output of the sinc filter is padded on the right with least significant zeros, up to 24 bits, for any resolution less than 24 bits. For 16-Bit Output modes, the output of the sinc filter is rounded to the closest 16-bit number, in order to conserve only 16-bit words and to minimize truncation error. Any unsettled data is automatically discarded to avoid data corruption. Each data ready pulse corresponds to fully settled data at the output of the decimation filter. The first data available at the output of the decimation filter is present after the complete settling time of the filter (see Table 5-4). After the first data has been processed, the delay between two data ready pulses is 1/ DRCLK. The data stream from input to output is delayed by an amount equal to the settling time of the filter (which is the group delay of the filter). The gain of the transfer function of this filter is 1 at each multiple of DMCLK (typically 1 MHz) so a proper antialiasing filter must be placed at the inputs. This will attenuate the frequency content around DMCLK and keep the desired accuracy over the baseband of the converter. This anti-aliasing filter can be a simple, firstorder RC network with a sufficiently low time constant to generate high rejection at DMCLK frequency. The achievable resolution, the -3 dB bandwidth and the settling time at the output of the decimation filter (the output of the ADC), is dependent on the OSR of each sinc filter and is summarized with the following table: TABLE 5-4: OVERSAMPLING RATIO AND SINC FILTER SETTLING TIME OSR<2:0> OSR3 OSR1 TOTAL OSR RESOLUTION IN BITS (NO MISSING CODES) SETTLING TIME -3 dB BANDWIDTH 32 1 32 17 96/DMCLK 0.26*DRCLK 0 0 0 0 0 1 64 1 64 20 192/DMCLK 0.26*DRCLK 0 1 0 128 1 128 23 384/DMCLK 0.26*DRCLK 0 1 1 256 1 256 24 768/DMCLK 0.26*DRCLK 1 0 0 512 1 512 24 1536/DMCLK 0.26*DRCLK 1 0 1 512 2 1024 24 2048/DMCLK 0.37*DRCLK 1 1 0 512 4 2048 24 3072/DMCLK 0.42*DRCLK 1 1 1 512 8 4096 24 5120/DMCLK 0.43*DRCLK (c) 2012 Microchip Technology Inc. DS22286A-page 35 MCP3911 FIGURE 5-4: SINC Filter Frequency Response, OSR = 256, MCLK = 4 MHz, PRE<1:0> = 00. FIGURE 5-5: SINC Filter Frequency Response, OSR = 4096 (pink), OSR = 512 (blue), MCLK = 4 MHz, PRE<1:0> = 00. DS22286A-page 36 (c) 2012 Microchip Technology Inc. MCP3911 5.6 ADC Output Coding In case of positive saturation (CHn+ - CHn- > VREF/ 1.5), the output is locked to 7FFFFF for 24 bit mode (7FFF for 16 bit mode). In case of negative saturation (CHn+ - CHn- <-VREF/1.5), the output code is locked to 800000 for 24-bit mode (8000 for 16 bit mode). The second order modulator, SINC3+SINC1 filter, PGA, VREF and analog input structure, all work together to produce the device transfer function for the analog to digital conversion, Equation 5-3. Equation 5-3 is only true for DC inputs. For AC inputs, this transfer function needs to be multiplied by the transfer function of the SINC3+SINC1 filter (see Equation 5-1 and Equation 5-3). The channel data is either a 16-bit or 24-bit word, presented in 23-bit or 15-bit plus sign, two's complement format and is MSB (left) justified. The ADC data is two or three bytes wide depending on the WIDTH bit of the associated channel. The 16-bit mode includes a round to the closest 16-bit word (instead of truncation), in order to improve the accuracy of the ADC data. EQUATION 5-3: ( CH n+ - CH n- ) DATA_CHn = ------------------------------------ x 8,388,608 x G x 1.5 V REF+ - V REF- (For 24-bit Mode Or WIDTH = 1) ( CH n+ - CH n- ) DATA_CHn = ------------------------------------- x 32, 768 x G x 1.5 VREF+ - V REF- (For 16-bit Mode Or WIDTH = 0) The ADC resolution is a function of the OSR (Section 5.5 "SINC3 + SINC1 Filter"). The resolution is the same for both channels. No matter what the resolution is, the ADC output data is always presented in 24-bit words, with added zeros at the end, if the OSR is not large enough to produce 24-bit resolution (left justification). TABLE 5-5: OSR = 256 (AND HIGHER) OUTPUT CODE EXAMPLES ADC Output Code (MSB First) 0 0 0 1 1 1 1 1 0 1 0 0 1 1 0 1 0 0 1 1 0 1 0 0 1 1 0 1 0 0 1 1 0 1 0 0 TABLE 5-6: 1 1 0 1 0 0 1 1 0 1 0 0 1 1 0 1 0 0 1 1 0 1 0 0 1 1 0 1 0 0 1 1 0 1 0 0 1 1 0 1 0 0 1 1 0 1 0 0 1 1 0 1 0 0 1 1 0 1 0 0 1 1 0 1 0 0 1 1 0 1 0 0 1 1 0 1 0 0 1 1 0 1 0 0 1 1 0 1 0 0 1 1 0 1 0 0 1 1 0 1 0 0 1 0 0 1 1 0 1 1 0 1 0 0 1 1 0 1 0 0 1 1 0 1 0 0 Decimal, 24-bit Resolution 0x7FFFFF 0x7FFFFE 0x000000 0xFFFFFF 0x800001 0x800000 + 8,388,607 + 8,388,606 0 -1 - 8,388,607 - 8,388,608 OSR = 128 OUTPUT CODE EXAMPLES ADC Output Code (MSB First) 0 0 0 1 1 1 Hexadecimal 1 1 0 1 0 0 1 1 0 1 0 0 1 1 0 1 0 0 1 1 0 1 0 0 1 1 0 1 0 0 1 1 0 1 0 0 (c) 2012 Microchip Technology Inc. 1 1 0 1 0 0 1 1 0 1 0 0 1 1 0 1 0 0 1 1 0 1 0 0 1 1 0 1 0 0 1 0 0 1 0 0 1 1 0 1 0 0 1 1 0 1 0 0 1 1 0 1 0 0 1 1 0 1 0 0 1 1 0 1 0 0 1 1 0 1 0 0 1 0 0 1 1 0 0 0 0 0 0 0 Hexadecimal Decimal 23-bit Resolution 0x7FFFFE 0x7FFFFC 0x000000 0xFFFFFE 0x800002 0x800000 + 4,194,303 + 4,194,302 0 -1 - 4,194,303 - 4,194,304 DS22286A-page 37 MCP3911 TABLE 5-7: OSR = 64 OUTPUT CODE EXAMPLES ADC Output code (MSB First) 0 0 0 1 1 1 1 1 0 1 0 0 1 1 0 1 0 0 1 1 0 1 0 0 1 1 0 1 0 0 1 1 0 1 0 0 TABLE 5-8: 1 1 0 1 0 0 1 1 0 1 0 0 1 1 0 1 0 0 1 1 0 1 0 0 1 1 0 1 0 0 1 1 0 1 0 0 1 1 0 1 0 0 1 1 0 1 0 0 1 1 0 1 0 0 1 1 0 1 0 0 1 1 0 1 0 0 1 1 0 1 0 0 1 1 0 1 0 0 1 0 0 1 1 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 1 1 0 1 0 0 5.7 5.7.1 1 1 0 1 0 0 1 1 0 1 0 0 Decimal 20-bit resolution 0x7FFFF0 0x7FFFE0 0x000000 0xFFFFF0 0x800010 0x800000 + 524, 287 + 524, 286 0 -1 - 524, 287 - 524, 288 Hexadecimal Decimal 17-bit resolution 0x7FFF80 0x7FFF00 0x000000 0xFFFF80 0x800080 0x800000 + 65, 535 + 65, 534 0 -1 - 65, 535 - 65, 536 OSR = 32 OUTPUT CODE EXAMPLES ADC Output code (MSB First) 0 0 0 1 1 1 Hexadecimal 1 1 0 1 0 0 1 1 0 1 0 0 1 1 0 1 0 0 1 1 0 1 0 0 1 1 0 1 0 0 1 1 0 1 0 0 1 1 0 1 0 0 1 1 0 1 0 0 1 1 0 1 0 0 1 1 0 1 0 0 1 1 0 1 0 0 1 1 0 1 0 0 1 0 0 1 1 0 Voltage Reference INTERNAL VOLTAGE REFERENCE The MCP3911 contains an internal voltage reference source specially designed to minimize drift over temperature. In order to enable the internal voltage reference, the VREFEXT bit in the configuration register must be set to 0 (default mode). This internal VREF supplies reference voltage to both channels. The typical value of this voltage reference is 1.2V 2%. The internal reference has a very low typical temperature coefficient of 7 ppm/C, allowing the output to have minimal variation with respect to temperature since they are proportional to (1/VREF). The noise of the internal voltage reference is low enough not to significantly degrade the SNR of the ADC if compared to a precision external low-noise voltage reference. The output pin for the internal voltage reference is REFIN+/OUT. If the voltage reference is only used as an internal VREF, adding bypass capacitance on REFIN+/OUT is not necessary for keeping ADC accuracy, but a minimal 0.1 F ceramic capacitance can be connected to avoid EMI/EMC susceptibility issues, due to the antenna created by the REFIN+/OUT pin if left floating. 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 5.7.2 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 0 DIFFERENTIAL EXTERNAL VOLTAGE INPUTS When the VREFEXT bit is high, the two reference pins (REFIN+/OUT, REFIN-) become a differential voltage reference input. The internal voltage reference circuit is placed into shutdown and the switch connecting this circuit to the reference voltage input of the ADC is opened. The internal voltage reference circuit is placed into shutdown and the switch connecting this circuit to the reference voltage input of the ADC is opened. The voltage at the REFIN+/OUT is noted VREF+ and the voltage at the REFIN- pin is noted VREF-. The differential voltage input value is given by the following equation: EQUATION 5-4: VREF=VREF+ - VREFThe specified VREF range is from 1.1V to 1.3V. The REFIN- pin voltage (VREF-) should be limited to 0.1V, with respect to AGND. Typically, for single-ended reference applications, the REFIN- pin should be directly connected to AGND, with its own separate track to avoid any spike due to switching noise. The bypass capacitors also help applications where the voltage reference output is connected to other circuits. In this case, additional buffering may be needed as the output drive capability of this output is low. Adding too much capacitance on the REFIN+/OUT pin may slightly degrade the THD performance of the ADCs. DS22286A-page 38 (c) 2012 Microchip Technology Inc. MCP3911 5.7.3 TEMPERATURE COMPENSATION (VREFCAL REGISTER) 5.8 The MCP3911 contains an internal POR circuit that monitors both analog and digital supply voltages during operation. The typical threshold for a power-up event detection is 2.1 V 5% and a typical start-up time (tPOR) of 50 s. The POR circuit has a built-in hysteresis for improved transient spikes immunity that has a typical value of 200 mV. Proper decoupling capacitors (0.1 F ceramic and 10 F tantalum) should be mounted as close as possible to the AVDD and DVDD pins, providing additional transient immunity. The internal voltage reference comprises a proprietary circuit and algorithm to compensate first order and second order temperature coefficients. The compensation allows very low temperature coefficients (typically 7 ppm/C) on the entire range of temperatures from -40C to 125C. This temperature coefficient varies from part to part. This temperature coefficient can be adjusted on each part through the VREFCAL register (address 0x1A). This register is only for advanced users. This register should not be written unless the user wants to calibrate the temperature coefficient of the whole system or application. The default value of this register is set to 0x42. The typical variation of the temperature coefficient of the internal voltage reference, with respect to VREFCAL register code, is given by Figure 5-6. Modifying the value stored in the VREFCAL register may also vary the output voltage, in addition to the temperature coefficient. Figure 5-7 illustrates the different conditions at power-up and a power-down event in typical conditions. All internal DC biases are not settled until at least 1 ms, in worst case conditions, after system POR. Any data ready pulse that occurs within 1 ms, plus the sinc filter settling time after system reset, should be ignored to guarantee proper accuracy. After POR, data ready pulses are present at the pin with all the default conditions in the configuration registers. 60 Both AVDD and DVDD are monitored so either power supply can sequence first. 50 VREF Drift (ppm) Power-on Reset 40 30 20 10 0 0 64 128 192 256 VREFCAL Register Trim Code (decimal) FIGURE 5-6: Trimcode Chart. VREF Tempco vs. VREFCAL Voltage (AVDD, DVDD) POR Threshold up (2.1V typ.) (1.9V typ.) tPOR Analog biases SINC filter settling settling time time POR State Power-Up POR Normal Operation State Time Biases are settled. Biases are Conversions started unsettled. here are accurate. Conversions started here may not be accurate. Any data read pulse occuring during this time can yield inaccurate output data. It is recommended to discard them. FIGURE 5-7: Power-on Reset Operation. (c) 2012 Microchip Technology Inc. DS22286A-page 39 MCP3911 5.9 RESET Effect On Delta-Sigma Modulator/SINC Filter When the RESET pin is logic low, both ADCs will be in Reset and output code 0x0000h. The RESET pin performs a hard reset (DC biases still on, part ready to convert) and clears all charges contained in the DeltaSigma modulators. The comparator's output is 0011 for each ADC. The SINC filters are all reset, as well as their double output buffers. This pin is independent of the serial interface. It brings all the registers to the default state. When RESET is logic low, any write with the SPI interface, will be disabled and will have no effect. All output pins (SDO, DR, MDAT0/1) are high impedance. If MCLK is applied, the input structure is enabled and is properly biasing the substrate of the input transistors. In this case, the leakage current on the analog inputs is low, if the analog inputs are between -1V and +1V. If MCLK is not applied, when in reset mode, the leakage can be high if the analog inputs are below -0.6V, referred to AGND. 5.10 Phase Delay Block The MCP3911 incorporates a phase delay generator, which ensures that the two ADCs are converting the inputs with a fixed delay between them. The two ADCs are synchronously sampling but the averaging of modulator outputs is delayed, so that the SINC filter outputs (thus the ADC outputs), show a fixed phase delay, as determined by the PHASE register's setting. The phase value (PHASE<11:0>) is a 11 bit + sign, MSB first, two's complement code that indicates how much phase delay there is to be between Channel 0 and Channel 1. The four MSB of the first phase register (address 0x07) are undefined and set to 0. The reference channel for the delay is Channel 1 (typically the voltage channel for power metering applications). When PHASE<11:0> is positive, Channel 0 is lagging versus Channel 1. When PHASE<11:0> is negative, Channel 0 is leading versus Channel 1. The amount of delay between two ADC conversions is shown in the following formula. EQUATION 5-5: Phase Register Code Delay = -------------------------------------------------DMCLK The timing resolution of the phase delay is 1/DMCLK, or 1 s in the default configuration with MCLK = 4 MHz. DS22286A-page 40 The data ready signals are affected by the phase delay settings. Typically, the time difference between the data ready pulses of channel 0 and channel 1, is equal to the phase delay setting. Note: 5.10.1 A detailed explanation of the data ready pin (DR) with phase delay is Figure 6-9. PHASE DELAY LIMITS The Phase delay can only go from -OSR/2 to +OSR/2 1. This sets the fine phase resolution. The phase register is coded with two's complement. If larger delays between the two channels are needed, they can be implemented externally to the chip with an MCU. A FIFO in the MCU can save incoming data from the leading channel for a number N of DRCLK clocks. In this case, DRCLK would represent the coarse timing resolution, and DMCLK the fine timing resolution. The total delay will then be equal to: Delay = N/DRCLK + PHASE/DMCLK Note: Re-writing the PHASE registers with the same value resets and automatically restarts both ADCs. The Phase delay register can be programmed once, with the OSR=4096 setting, and will adjust to the OSR automatically afterwards without the need to change the value of the PHASE register. * OSR=4096: the delay can go from -2048 to +2047.PHASE<11> is the sign bit. Phase<10> is the MSB and PHASE<0> the LSB. * OSR=2048: the delay can go from -1024 to +1023. PHASE<10> is the sign bit. Phase<9> is the MSB and PHASE<0> the LSB. * OSR=1024: the delay can go from -512 to +511. PHASE<9> is the sign bit. Phase<8> is the MSB and PHASE<0> the LSB. * OSR=512: the delay can go from -256 to +255. PHASE<8> is the sign bit. Phase<7> is the MSB and PHASE<0> the LSB. * OSR=256: the delay can go from -128 to +127. PHASE<7> is the sign bit. Phase<6> is the MSB and PHASE<0> the LSB. * OSR=128: the delay can go from -64 to +63. PHASE<6> is the sign bit. Phase<5> is the MSB and PHASE<0> the LSB. * OSR=64: the delay can go from -32 to +31. PHASE<5> is the sign bit. Phase<4> is the MSB and PHASE<0> the LSB. * OSR=32: the delay can go from -16 to +15. PHASE<4> is the sign bit. Phase<3> is the MSB and PHASE<0> the LSB. (c) 2012 Microchip Technology Inc. MCP3911 TABLE 5-9: PHASE VALUES WITH MCLK = 4 MHZ, OSR = 4096 Hex Delay (CH0 relative to CH1) 011111111111 0x7FF + 2047 s 011111111110 0x7FE + 2046 s 000000000001 0x001 + 1 s 000000000000 0x000 0 s 111111111111 0xFFF - 1 s 100000000001 0x801 - 2048 s 100000000000 0x800 -2048 s Phase Register Value 5.11 When CLKEXT=1, the crystal oscillator is bypassed by a digital buffer to allow direct clock input for an external clock (see Figure 4-1). When CLKEXT=1, it is recommended to connect OSC2 pin to DGND directly at all times. The external clock should not be higher than 20 MHz before prescaler (MCLK < 20 MHz) for proper operation. Note: Crystal Oscillator The MCP3911 includes a Pierce-type crystal oscillator with very high stability and ensures very low tempco and jitter for the clock generation. This oscillator can handle up to 20 MHz crystal frequencies, provided that proper load capacitances and quartz quality factor are used. For a proper start-up, the load capacitors of the crystal should be connected between OSC1 and DGND and between OSC2 and DGND. They should also respect the following equation: EQUATION 5-6: 2 6 1 R M < 1.6 x 10 x ------------------------ f * CLOAD Where: f = crystal frequency in MHz CLOAD = load capacitance in pF including parasitics from the PCB RM = motional resistance in ohms of the quartz EQUATION 5-7: 5.12 In addition to the conditions defining the maximum MCLK input frequency range, the AMCLK frequency should be maintained inferior to the maximum limits defined in Table 5-2 to guarantee the accuracy of the ADCs. If these limits are exceeded, it is recommended to either choose a larger OSR, or a large prescaler value, so that AMCLK can respect these limits. Digital System Offset and Gain Errors The MCP3911 incorporates two sets of additional registers per channel, to perform system digital offset and gain errors calibration. Each channel has its own set of registers associated that will modify the output result of the channel, if the calibration is enabled. The gain and offset calibrations can be enabled or disabled through two configuration bits (EN_OFFCAL and EN_GAINCAL). These two bits enable or disable system calibration on both channels at the same time. When both calibrations are enabled, the output of the ADC is modified as follows: DIGITAL OFFSET AND GAIN ERROR CALIBRATION REGISTERS CALCULATIONS DATA_CHn ( post - cal ) = ( DATA_CHn ( pre - cal ) + OFFCAL_CHn ) x ( 1 + GAINCAL_CHn ) (c) 2012 Microchip Technology Inc. DS22286A-page 41 MCP3911 5.12.1 DIGITAL OFFSET ERROR CALIBRATION The OFFCAL_CHn registers are 23-bit plus sign two's complement register, which LSB value is the same as the Channel ADC Data. These two registers are then added bit-by-bit to the ADC output codes, if the EN_OFFCAL bit is enabled. Enabling the EN_OFFCAL bit does not create any pipeline delay, the offset addition is instantaneous. For low OSR values, only the significant digits are added to the output (up to the resolution of the ADC. For example, at OSR=32, only the 17 first bits are added). The offset is not added when the corresponding channel is in reset or shutdown mode. The corresponding input voltage offset value added by each LSB in these 24-bit registers is: OFFSET(1LSB)= VREF /(PGA_CHn*1.5*8388608) This register is a Don't Care if EN_OFFCAL=0 (Offset calibration disabled), but its value is not cleared by the EN_OFFCAL bit. 5.12.2 DIGITAL GAIN ERROR CALIBRATION This register is 24-bit signed MSB first coding with a range of -1x to +0.9999999x (from 0x80000 to 0x7FFFFF). The gain calibration adds 1x to this register and multiplies it to the output code of the channel bit-by-bit, after offset calibration. The range of the gain calibration is thus from 0x to 1.9999999x (from 0x80000 to 0x7FFFFF). The LSB corresponds to a 2-23 increment in the multiplier. Enabling EN_GAINCAL creates a pipeline delay of 24 DMCLK periods on both channels. All data ready pulses are delayed by 24 DMCLK periods, starting from the data ready, following the command enabling EN_GAINCAL bit. The gain calibration is effective on the next data ready, following the command enabling EN_GAINCAL bit. The digital gain calibration does not function when the corresponding channel is in reset or shutdown mode. The gain multiplier value for an LSB in these 24-bit registers is: GAIN (1LSB)= 1/8388608 This register is a Don't Care if EN_GAINCAL=0 (Offset calibration disabled) but its value is not cleared by the EN_GAINCAL bit. The output data on each channel is kept to either 7FFF or 8000 (16-bit mode) or 7FFFFF or 800000 (24-bit mode) if the output result is out of bounds, after all calibrations are performed. DS22286A-page 42 (c) 2012 Microchip Technology Inc. MCP3911 6.0 6.1 SERIAL INTERFACE DESCRIPTION A5 A4 A3 A2 A1 A0 Overview The MCP3911 device is compatible with SPI Modes 0,0 and 1,1. Data is clocked out of the MCP3911 on the falling edge of SCK and data is clocked into the MCP3911 on the rising edge of SCK. In these modes, SCK can Idle either high or low. Each SPI communication starts with a CS falling edge and stops with the CS rising edge. Each SPI communication is independent. When CS is high, SDO is in high-impedance, transitions on SCK, and SDI have no effect. Additional controls: RESET, DR and MDAT0/1 are also provided on separate pins for advanced communication. The MCP3911 interface has a simple command structure. The first byte transmitted is always the CONTROL byte and is followed by data bytes that are 8-bits wide. Both ADCs are continuously converting data by default and can be reset or shut down through a CONFIG register setting. Since each ADC data is either 16 or 24 bits (depending on the WIDTH bits), the internal registers can be grouped together with various configurations (through the READ bits) in order to allow easy data retrieval within only one communication. For device reads, the internal address counter can be automatically incremented in order to loop through groups of data within the register map. The SDO will then output the data located at the ADDRESS (A<4:0>) defined in the control byte and then ADDRESS + 1 depending on the READ<1:0> bits, which select the groups of registers. These groups are defined in Section 7.1 "CHANNEL REGISTERS - ADC Channel Data Output Registers" (Register Map). The Data Ready pin (DR) can be used as an interrupt for an MCU and outputs pulses when a new ADC channel data is available. The RESET pin acts like a Hard Reset and can reset the part to its default powerup configuration. The MDAT0/1 pins give the modulator outputs (see Section 5.4 "Modulator Output Block"). 6.2 A6 Control Byte The control byte of the MCP3911 contains two device Address bits, A<6:5>, 5 register Address bits, A<4:0>, and a Read/Write bit (R/W). The first byte transmitted to the MCP3911 is always the control byte. Device Address Bits FIGURE 6-1: R/W Read/ Write Bit Register Address Bits Control Byte. The default device address bits are `00'. Contact the Microchip factory for additional device address bits. For more information, please see the Product Identification System section. A read on undefined addresses will give an all zeros output on the first, and all subsequent transmitted bytes. A write on an undefined address will have no effect, and also will not increment the address counter. The register map is defined in Table 7-1. 6.3 Reading from the Device The first data byte read is the one defined by the address given in the CONTROL byte. After this first byte is transmitted, if the CS pin is maintained low, the communication continues and the address of the next transmitted byte is determined by the status of the READ bits in the STATUSCOM register. Multiple looping configurations can be defined through the READ<1:0> bits for the address increment (see Section 6.6 "SPI MODE 0,0 - Clock Idle Low, Read/ Write Examples"). 6.4 Writing to the Device The first data byte written is the one defined by the address given in the control byte. Two write mode configurations for the address increment can be defined through the WRITE bit in the STATUSCOM register. When WRITE = 1, the write communication automatically increments the address for subsequent bytes. The address of the next transmitted byte within the same communication (CS stays logic low) is the next address defined on the register map. At the end of the register map, the address loops to the beginning of the writable part of the register map (address 0x06). Writing a nonwritable register has no effect. When WRITE = 0, the address is not incremented on the subsequent writes. The SDO pin stays in high-impedance during a write communication. The MCP3911 interface is device addressable (through A<6:5>) so that multiple MCP3911 chips can be present on the same SPI bus with no data bus contention. This functionality enables three-phase power metering systems, containing three MCP3911 chips, controlled by a single SPI bus (single CS, SCK, SDI and SDO pins). (c) 2012 Microchip Technology Inc. DS22286A-page 43 MCP3911 6.5 SPI MODE 1,1 - Clock Idle High, Read/Write Examples In this SPI mode, SCK idles high. For the MCP3911, this means that there will be a falling edge on SCK before there is a rising edge. Note: Changing from an SPI Mode 1,1 to an SPI Mode 0,0 is possible and can be done while CS pin is logic high. : CS Data Transitions on the Falling Edge MCU and MCP3911 Latch Bits on the Rising Edge SCK SDI SDO A6 A5 A4 A3 A2 A1 A0 R/W HI-Z HI-Z D7 D6 D5 D4 D3 D2 D1 HI-Z D0 D7 D6 D5 D4 D3 D2 D1 (ADDRESS) DATA FIGURE 6-2: D0 (ADDRESS + 1) DATA Device Read (SPI Mode 1,1 - SCK Idles High). CS Data Transitions on the Falling Edge MCU and MCP3911 Latch Bits on the Rising Edge SCK A6 A5 A4 A3 A2 A1 SDI HI-Z SDO FIGURE 6-3: DS22286A-page 44 A0 R/W D7 D6 D5 D4 D3 D2 D1 (ADDRESS) DATA D7 D6 D5 D4 D3 D0 D2 D1 (ADDRESS + 1) DATA D0 HI-Z HI-Z Device Write (SPI Mode 1,1 - SCK Idles High). (c) 2012 Microchip Technology Inc. MCP3911 6.6 SPI MODE 0,0 - Clock Idle Low, Read/Write Examples In this SPI mode, SCK idles low. For the MCP3911, this means that there will be a rising edge on SCK before there is a falling edge. CS Data Transitions on the Falling Edge MCU and MCP3911 Latch Bits on the Rising Edge SCK SDI A6 A5 A4 A3 A2 A1 HI-Z SDO A0 R/W HI-Z D6 D5 D4 D3 D2 D1 D7 D0 (ADDRESS) DATA FIGURE 6-4: D7 D6 D5 D4 D3 D2 D1 D0 D7 OF (ADDRESS + 2) DATA HI-Z (ADDRESS + 1) DATA Device Read (SPI Mode 0,0 - SCK Idles Low). CS Data Transitions on the Falling Edge MCU and MCP3911 Latch Bits on the Rising Edge SCK SDI A6 A5 A4 A3 A2 A1 D7 D6 D5 D4 D3 D2 D1 D0 D7 (ADDRESS) DATA HI-Z SDO FIGURE 6-5: A0 R/W D6 D5 D4 D3 D2 D1 D0 (ADDRESS + 1) DATA D7 OF (ADDRESS + 2) DATA HI-Z HI-Z Device Write (SPI Mode 0,0 - SCK Idles Low). (c) 2012 Microchip Technology Inc. DS22286A-page 45 MCP3911 6.7 Continuous Communication, Looping on Address Sets If the user wishes to read back either of the ADC channels continuously, or both channels continuously, the internal address counter of the MCP3911 can be set to loop on specific register sets. In this case, there is only one control byte on SDI to start the communication. The part stays within the same loop until CS pin returns logic high. This internal address counter allows the following functionality: * Read one ADC channel data continuously * Read both ADC channels data continuously (both ADC data can be independent or linked with DRMODE settings) * Continuously read/write the entire register map * Continuously read/write each separate register * Continuously read all Configuration registers * Write all Configuration registers in one communication (see Figure 6-8) 6.7.1 Note: For continuous reading of ADC data in SPI Mode 0,0 (see Figure 6-6), once the data has been completely read after a data ready, the SDO pin will take the MSB value of the previous data at the end of the reading (falling edge of the last SCK clock). If SCK stays idle at logic low (by definition of Mode 0,0), the SDO pin will be updated at the falling edge of the next data ready pulse (synchronously with the DR pin falling edge with an output timing of tDODR) with the new MSB of the data corresponding to the data ready pulse. This mechanism allows the MCP3911 to continuously use read mode seamlessly in SPI Mode 0,0. In SPI Mode 1,1, the SDO stays in the last state (LSB of previous data) after a complete reading which also allows seamless continuous read mode. (see Figure 6-7). CONTINUOUS READ The STATUSCOM register contains the loop settings for the internal address counter (READ<1:0> bits and WRITE bit). The internal address counter can either stay constant (READ<1:0> = 00) and continuously read the same byte, or it can auto-increment and loop through the register groups defined below (READ<1:0> = 01), register types (READ<1:0> = 10) or the entire register map (READ<1:0> = 11). Each ADC channel is configured independently as either a 16-bit or 24-bit data word, depending on the setting of the corresponding WIDTH bit in the STATUSCOM register. For continuous reading, in the case of WIDTH = 0 (16-bit), the lower byte of the ADC data is not accessed and the part jumps automatically to the following address (the user does not have to clock out the lower byte since it becomes undefined for WIDTH = 0). Figure 6-6 and Figure 6-7 represent a typical, continuous read communication with the default settings (DRMODE<1:0> = 00, READ<1:0> = 10) for both WIDTH settings in case of the SPI Mode 0,0 (Figure 66) and SPI Mode 1,1 (Figure 6-7). This configuration is typically used for power metering applications. DS22286A-page 46 (c) 2012 Microchip Technology Inc. MCP3911 CS SCK CH0 ADC ADDR/R SDI SDO CH0 ADC CH0 ADC CH0 ADC CH1 ADC CH1 ADC CH1 ADC Upper byte Middle byte Lower byte Upper byte Middle byte Lower byte HiZ CH0 ADC MSB Old ADC data CH0 ADC Upper byte CH0 ADC CH0 ADC CH1 ADC CH1 ADC CH1 ADC CH0 ADC Upper byte New ADC data Middle byte Lower byte Upper byte Middle byte Lower byte Old ADC data DR These bytes are not present when WIDTH=0 (16-bit mode) FIGURE 6-6: CH0 ADC Old MSB data - Previous MSB data present on SDO until the data ready pulse updates the SDO with the new incoming MSB data dta Typical Continuous Read Communication (SPI Mode 0,0). CS SCK CH0 ADC ADDR/R SDI SDO HiZ CH0 ADC CH0 ADC CH0 ADC CH1 ADC CH1 ADC Upper byte Middle byte Lower byte Upper byte Middle byte CH1 ADC Lower byte CH0 ADC CH0 ADC CH0 ADC CH1 ADC CH1 ADC Upper byte Middle byte Lower byte Upper byte Middle byte CH1 ADC Lower byte DR These bytes are not present when WIDTH=0 (16-bit mode) FIGURE 6-7: Typical Continuous Read Communication (SPI Mode 1,1). (c) 2012 Microchip Technology Inc. DS22286A-page 47 MCP3911 6.7.2 CONTINUOUS WRITE The following register sets are defined as types: Both ADCs are powered up with their default configurations, and begin to output data ready pulses immediately (RESET<1:0> and SHUTDOWN<1:0> bits are off by default). TABLE 6-2: Type The default output codes for both ADCs are all zeros. The default modulator output for both ADCs is `0011' (corresponding to a theoretical zero voltage at the inputs). The default phase is zero between the two channels. 0x00-0x05 CONFIGURATION 0x06-0x1A Situations that Reset ADC Data Immediately after the following actions, the ADCs are reset and automatically restarted in order to provide proper operation: 1. 2. 3. 4. 5. 6. 7. Change in PHASE register Change in the OSR setting Change in the PRESCALE setting Overwrite of the same PHASE register value Change in the CLKEXT setting Change in the VREFEXT setting Change in the MODOUT setting After these temporary resets, the ADCs go back to the normal operation, with no need for an additional command. The PHASE register can be used to serially Soft Reset the ADCs, without using the RESET bits in the Configuration register, if the same value is written in the PHASE register. REGISTER GROUPS AND TYPES The following register sets are defined as groups: TABLE 6-1: Addresses ADC DATA (both channels) 6.8 It is recommended to enter into ADC Reset mode for both ADCs, just after power-up, because the desired MCP3911 register configuration may not be the default one, and in this case, the ADC would output undesired data. Within the ADC Reset mode (RESET<1:0> = 11), the user can configure the whole part with a single communication. The write commands automatically increment the address so that the user can start writing the PHASE register and finish with the CONFIG register in only one communication (see Figure 6-8). The RESET<1:0> bits are in the last byte of the CONFIG register to allow exiting the Soft Reset mode, and have the whole part configured and ready to run in only one command. 6.7.3 REGISTER TYPES REGISTER GROUPS Group Addresses ADC DATA CH0 0x00-0x02 ADC DATA CH1 0x03-0x05 MOD, PHASE, GAIN 0x06-0x09 CONFIG, STATUSCOM 0x0A-0x0D OFFCAL_CH0, GAINCAL_CH0 0x0E-0x13 OFFCAL_CH1, GAINCAL_CH1 0x14-0x19 VREFCAL 0x1A AVDD, DVDD CS SCK SDI 00011010 11XXXXXX CONFIG2 CONFIG2 00001110 PHASE ADDR/W xxxxxxxx xxxxxxxx PHASE xxxxxxxx GAIN xxxxxxxx xxxxxxxx xxxxxxxx STATUSCOM xxxxxxxx CONFIG ADDR/W Optional RESET of both ADCs FIGURE 6-8: DS22286A-page 48 One command for writing complete configuration (without calibration) Recommended Configuration Sequence at Power-up. (c) 2012 Microchip Technology Inc. MCP3911 6.9 Data Ready Pin (DR) To signify when channel data is ready for transmission, the data ready signal is available on the Data Ready pin (DR) through an active-low pulse at the end of a channel conversion. The data ready pin outputs an active-low pulse with a period that is equal to the DRCLK clock period, and with a width equal to one DMCLK period. When not active-low, this pin can either be in highimpedance (when DR_HIZ = 0) or in a defined logic high state (when DR_HIZ = 1). This is controlled through the STATUSCOM register. This allows multiple devices to share the same data ready pin (with a pull-up resistor connected between DR and DVDD) in 3-phase, energy meter designs to reduce pin count. A single device on the bus does not require a pull-up resistor and therefore it is recommended to use DR_HIZ = 1 configuration for such applications. After a data ready pulse has occurred, the ADC output data can be read through SPI communication. Two sets of latches at the output of the ADC prevent the communication from outputting corrupted data (see Section 6.10 "ADC Data Latches and Data Ready Modes (DRMODE<1:0>)"). The CS pin has no effect on the DR pin, which means even if CS is logic high, data ready pulses will be provided (except when the configuration prevents them from outputting data ready pulses). The DR pin can be used as an interrupt when connected to an MCU or DSP. While the RESET pin is logic low, the DR pin is not active. 6.10 ADC Data Latches and Data Ready Modes (DRMODE<1:0>) To ensure that both channels' ADC data is present at the same time for SPI read, regardless of phase delay settings for either or both channels, there are two sets of ADC data latches in series with both the data ready and the `read start' triggers. The first set of latches holds each output when the data is ready and latches both outputs together when DRMODE<1:0> = 00. When this mode is on, both ADCs work together and produce one set of available data after each data ready pulse (that corresponds to the lagging ADC data ready). The second set of latches ensures that when reading starts on an ADC output, the corresponding data is latched so that no data corruption can occur. 6.10.1 DATA READY PIN (DR) CONTROL USING DRMODE BITS There are four modes that control the data ready pulses and these modes are set with the DRMODE<1:0> bits in the STATUSCOM register. For power metering applications, DRMODE<1:0> = 00 is recommended (Default mode). The position of the data ready pulses vary, with respect to this mode, to the OSR and to the PHASE settings: * DRMODE<1:0> = 11: Both data ready pulses from ADC Channel 0 and ADC Channel 1 are output on the DR pin. * DRMODE<1:0> = 10: Data ready pulses from ADC Channel 1 are output on the DR pin. The data ready pulse from ADC Channel 0 is not present on the pin. * DRMODE<1:0> = 01: Data ready pulses from ADC Channel 0 are output on the DR pin. The data ready pulse from ADC Channel 1 is not present on the pin. * DRMODE<1:0> = 00 (Recommended and Default mode): Data ready pulses from the lagging ADC between the two are output on the DR pin. The lagging ADC depends on the PHASE register and on the OSR. In this mode, the two ADCs are linked together so their data is latched together when the lagging ADC output is ready. 6.10.2 DATA READY PULSES WITH SHUTDOWN OR RESET CONDITIONS There will be no data ready pulses if DRMODE<1:0> = 00 when either one or both of the ADCs are in Reset or shutdown. In Mode 0,0, a data ready pulse only happens when both ADCs are ready. Any data ready pulse will correspond to one data on both ADCs. The two ADCs are linked together and act as if there was only one channel with the combined data of both ADCs. This mode is very practical when both ADC channels' data retrieval and processing need to be synchronized, as in power metering applications. Note: If DRMODE<1:0> = 11, the user will still be able to retrieve the data ready pulse for the ADC not in shutdown or Reset (i.e., only 1 ADC channel needs to be awake). Figure 6-9 represents the behavior of the data ready pin with the different DRMODE configurations, while shutdown or reset are applied. If an ADC read has started, in order to read the following ADC output, the current reading needs to be completed (all bits must be read from the ADC Output Data registers). (c) 2012 Microchip Technology Inc. DS22286A-page 49 MCP3911 RESET RESET<0> or RESET<1> or SHUTDOWN<0> SHUTDOWN<1> DRMODE=00; DR DRMODE=01; DR DRMODE=10; DR DRMODE=11; DR DRMODE=00; DR DRMODE=01; DR DRMODE=10; DR DRMODE=11; DR DRMODE=00; DR DRMODE=01; DR DRMODE=10; DR DRMODE=11; DR 3*DRCLK period DRCLK Period 1 DMCLK Period D5 DRCLK Period D6 D9 D4 D8 D16 D17 D3 D7 D14 D15 D2 D6 D12 D13 D6 D1 D5 D10 D11 D5 D6 D0 D4 D8 D9 D4 D5 D9 D7 D3 D7 D3 D4 D8 D6 D2 D6 D3 D7 D5 D1 D5 D6 D4 D0 D3 D4 D5 D3 D1 D2 D2 D4 D2 D0 D1 D2 D3 D9 D1 D0 D1 D2 D8 D0 D0 D1 D7 D10 D7 D0 D6 D7 D5 D6 D4 D5 D3 D4 D2 D3 D1 D2 D0 D1 D9 D17 D0 D8 D15 D16 D7 D7 D13 D14 D6 D6 D11 D12 D5 D5 D9 D10 D4 D4 D8 D3 D3 D7 D2 D2 D5 D6 D1 D1 D3 D4 D0 D0 D1 D2 Internal data ready pulse (filtered because it corresponds to unsettled data) D0 DRMODE=00: Select the lagging Data Ready DRMODE=01: Select the Data Ready on channel 0 DRMODE=10: Select the Data Ready on channel 1 DRMODE=11: Select both Data ready D8 D18 D8 D18 D8 D11 D9 D19 D9 D19 D9 D12 Internal reset synchronisation (1 DMCLK period) D11 3*DRCLK period DRCLK period D12 D13 D14 D17 D10 D16 D34 D9 D15 D32 D33 D8 D30 D31 D13 D7 D29 D12 D16 D16 D14 D11 D15 D16 D15 D28 D14 D15 D14 D10 D26 D27 D13 D13 D14 D13 D9 D24 D25 D12 D12 D13 D12 D8 D22 D23 D11 D11 D12 D11 D7 D11 D10 D10 D20 D21 D10 D10 D19 D14 D18 D13 D17 D12 D16 D11 D15 D10 D14 D9 D13 D8 D16 D34 D17 D15 D32 D33 D16 D14 D30 D31 D15 D29 D14 D13 D28 D13 D12 D26 D27 D12 D11 D24 D25 D11 D10 D22 D23 D10 D20 D21 (c) 2012 Microchip Technology Inc. DS22286A-page 50 Data Ready Behavior. FIGURE 6-9: PHASE > 0 PHASE = 0 PHASE < 0 MCP3911 7.0 INTERNAL REGISTERS The addresses associated with the internal registers are listed below. A detailed description of the registers follows. All registers are split in 8-bit long registers, which can be addressed and read separately. Read and Write modes define the groups and types of registers for continuous read/write communication or looping on address sets as shown in Register 7-2. TABLE 7-1: REGISTER MAP Address Name Bits R/W Description 0x00 CHANNEL0 24 R Channel 0 ADC 24-bit Data <23:0>, MSB first 0x03 CHANNEL1 24 R Channel 1 ADC 24-bit Data <23:0>, MSB first 0x06 MOD 8 0x07 PHASE 16 R/W Phase Delay Configuration Register 0x09 GAIN 8 R/W Gain and Boost Configuration Register 0x0A STATUSCOM 16 R/W Status and Communication Register 0x0C CONFIG 16 R/W Configuration Register 0x0E OFFCAL_CH0 24 R/W Offset Correction Register - Channel 0 0x11 GAINCAL_CH0 24 R/W Gain Correction Register - Channel 0 R/W Modulator Output Register for both ADC channels 0x14 OFFCAL_CH1 24 R/W Offset Correction Register - Channel 1 0x17 GAINCAL_CH1 24 R/W Gain Correction Register - Channel 1 0x1A VREFCAL 8 R/W Internal Voltage reference Temperature Coefficient Adjustment Register (c) 2012 Microchip Technology Inc. DS22286A-page 51 MCP3911 . TABLE 7-2: REGISTER MAP GROUPING FOR ALL CONTINUOUS READ/WRITE MODES READ<1:0> 0x00 0x01 TYPE CHANNEL 0 0x02 0x03 CHANNEL 1 0x04 0x05 PHASE 0x06 0x07 0x0D 0x0E OFFCAL_CH0 0x0F 0x10 0x11 GAINCAL_CH0 OFFCAL_CH1 Static Static = "1" = "0" Static Static Static Static Static Static Static Static Static Static Static Static GROUP CONFIG 0x0B 0x0C Static Static Static Static Static Static Static Static Static Static Static Static Static Static TYPE STATUSCOM 0x09 0x0A LOOP ENTIRE REGISTER MAP 0x08 GAIN = "00" GROUP MOD WRITE = "01" GROUP = "10" GROUP = "11" GROUP Address Static Static LOOP ENTIRE REGISTER MAP Static Static Static Static Static Static Static Static 0x13 Static Static 0x14 Static Static 0x15 Static Static Static Static 0x12 0x16 Static Static GAINCAL_CH1 0x18 Static Static 0x19 Static Static VREFCAL 0x1A Static Static DS22286A-page 52 GROUP 0x17 GROUP Function (c) 2012 Microchip Technology Inc. MCP3911 7.1 CHANNEL REGISTERS - ADC CHANNEL DATA OUTPUT REGISTERS REGISTER 7-1: CHANNEL REGISTER Name Bits Address R/W CHANNEL0 24 0x00 R CHANNEL1 24 0x03 R The ADC Channel Data Output registers always contain the most recent A/D conversion data for each channel. These registers are read-only. They can be accessed independently or linked together (with READ<1:0> bits). These registers are latched when an ADC read communication occurs. When a data ready event occurs during a read communication, the most current ADC data is also latched to avoid data corruption issues. The three bytes of each channel are updated synchronously at a DRCLK rate. The three bytes can be accessed separately if needed, but are refreshed synchronously. R-0 R-0 R-0 R-0 R-0 R-0 R-0 R-0 DATA_CHn <23> (MSB) DATA_CHn <22> DATA_CHn <21> DATA_CHn <20> DATA_CHn <19> DATA_CHn <18> DATA_CHn <17> DATA_CHn <16> bit 23 bit 16 R-0 R-0 R-0 R-0 R-0 R-0 R-0 R-0 DATA_CHn <15> DATA_CHn <14> DATA_CHn <13> DATA_CHn <12> DATA_CHn <11> DATA_CHn <10> DATA_CHn <9> DATA_CHn <8> bit 15 bit 8 R-0 R-0 R-0 R-0 R-0 R-0 R-0 R-0 DATA_CHn <7> DATA_CHn <6> DATA_CHn <5> DATA_CHn <4> DATA_CHn <3> DATA_CHn <2> DATA_CHn <1> DATA_CHn <0> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as `0' -n = Value at POR `1' = Bit is set `0' = Bit is cleared bit 23:0 x = Bit is unknown DATA_CHn: Output code from ADC Channel n. This data is post-calibration if the EN_OFFCAL or EN_GAINCAL bits are enabled. (c) 2012 Microchip Technology Inc. DS22286A-page 53 MCP3911 7.2 MOD REGISTER - MODULATORS OUTPUT REGISTER MOD Register REGISTER 7-2: Name Bits Address Cof MOD 8 0x06 R/W The MOD register contains the most recent modulator data output. The default value corresponds to an equivalent input of 0V on both ADCs. Each bit in this register corresponds to one comparator output on one of the channels. . Comparator3 Channel 1 Comparator2 Channel 1 Comparator1 Channel 1 Comparator0 Channel 1 Comparator3 Channel 0 Comparator2 Channel 0 Comparator1 Channel 0 Comparator0 Channel 0 R/W-0 R/W-0 R/W-1 R/W-1 R/W-0 R/W-0 R/W-1 R/W-1 COMP3_CH1 COMP2_CH1 COMP1_CH1 COMP0_CH1 COMP3_CH0 COMP2_CH0 COMP1_CH0 COMP0_CH0 bit 7 bit 6 bit 5 bit 4 bit 3 bit 2 bit 1 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as `0' -n = Value at POR `1' = Bit is set `0' = Bit is cleared bit 7:4 COMPn_CH1: Comparator Outputs from ADC Channel 1 bit 3:0 COMPn_CH0: Comparator Outputs from ADC Channel 0 DS22286A-page 54 x = Bit is unknown (c) 2012 Microchip Technology Inc. MCP3911 7.3 PHASE Register - Phase Configuration Register PHASE Register REGISTER 7-3: Name Bits Address Cof PHASE 16 0x07 R/W Any write to one of these two addresses (0x07 and 0x08) creates an internal reset and restart sequence. U-0 U-0 U-0 U-0 R/W-0 R/W-0 R/W-0 R/W-0 -- -- -- -- PHASE<11> PHASE<10> PHASE<9> PHASE<8> bit 11 R/W-0 R/W-0 PHASE<7> PHASE<6> R/W-0 R/W-0 PHASE<5> PHASE<4> bit 8 R/W-0 R/W-0 R/W-0 R/W-0 PHASE<3> PHASE<2> PHASE<1> PHASE<0> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as `0' -n = Value at POR `1' = Bit is set `0' = Bit is cleared bit 15:12 Unimplemented, read as `0' bit 11:0 CH0 relative to CH1 phase delay x = Bit is unknown PHASE<11:0>: CH0 Relative to CH1 Phase Delay bits Delay = PHASE Register's two's complement code/DMCLK (Default PHASE = 0). (c) 2012 Microchip Technology Inc. DS22286A-page 55 MCP3911 7.4 Gain - GAIN AND BOOST CONFIGURATION REGISTER GAIN Register REGISTER 7-4: Name Bits Address Cof GAIN 8 0x09 R/W R/W-1 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 R/W-0 BOOST<1> BOOST<0> PGA_CH1<2> PGA_CH1<1> PGA_CH1<0> PGA_CH0<2> R/W-0 PGA_CH0<1> PGA_CH0<0> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as `0' -n = Value at POR `1' = Bit is set `0' = Bit is cleared bit 7:6 BOOST<1:0> Bias Current Selection 11 = Both channels have current x 2 10 = Both channels have current x 1(DEFAULT) 01 = Both channels have current x 0.66 00 = Both channels have current x 0.5 bit 5:3 PGA_CH1<2:0>: PGA Setting for Channel 1 111 = Reserved (Gain = 1) 110 = Reserved (Gain = 1) 101 = Gain is 32 100 = Gain is 16 011 = Gain is 8 010 = Gain is 4 001 = Gain is 2 000 = Gain is 1 (DEFAULT) bit 2:0 PGA_CH0<2:0>: PGA Setting for Channel 0 111 = Reserved (Gain = 1) 110 = Reserved (Gain = 1) 101 = Gain is 32 100 = Gain is 16 011 = Gain is 8 010 = Gain is 4 001 = Gain is 2 000 = Gain is 1 (DEFAULT) DS22286A-page 56 x = Bit is unknown (c) 2012 Microchip Technology Inc. MCP3911 7.5 STATUSCOM Register - Status And Communication Register REGISTER 7-5: STATUSCOM Register Name Bits Address Cof STATUSCOM 16 0x0A R/W R/W-0 R/W-0 U-0 R/W-0 R/W-0 R/W-0 MODOUT<1> MODOUT<0> -- DR_HIZ DRMODE<1> DRMODE<0> R/W-1 R/W-1 DRSTATUS<1> DRSTATUS<0> bit 15 bit 8 U-0 R/W-1 R/W-0 R/W-1 R/W-1 R/W-1 R/W-0 R/W-0 READ<1> READ<0> WRITE WIDTH<1> WIDTH<0> EN_OFFCAL EN_GAINCAL bit 7 -- bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as `0' -n = Value at POR `1' = Bit is set `0' = Bit is cleared bit 15:14 x = Bit is unknown MODOUT<1:0>: Modulator Output Setting for MDAT pins 11 = Both CH0 and CH1 modulator outputs are present on MDAT1 and MDAT0 pins, both SINC filters are off, no data ready pulse is present 10 = CH1 ADC Modulator output present on MDAT1 pin, SINC filter on channel 1 is off, data ready pulse from channel 1 is not present on DR pin 01 = CH0 ADC Modulator output present on MDAT0 pin, SINC filter on channel 0 is off, data ready pulse from channel 0 is not present on DR pin 00 = No Modulator output is enabled, SINC filters are on, data readys are present on DR pin for both channels (DEFAULT) bit 13 Unimplemented, read as 0 bit 12 DR_HIZ: Data Ready Pin Inactive State Control 1 = The DR pin state is a logic high when data is NOT ready 0 = The DR pin state is high impedance when data is NOT ready(DEFAULT) bit 11:10 DRMODE<1:0>: Data Ready Pin (DR) mode configuration bits 11 = Both Data Ready pulses from CH0 and CH1 are output on DR pin 10 = Data Ready pulses from CH1 ADC are output on DR pin. Data ready pulses from CH0 are not present on the DR pin. 01 = Data Ready pulses from CH0 ADC are output on DR pin. Data ready pulses from CH1 are not present on the DR pin. 00 = Data Ready pulses from the lagging ADC between the two are output on DR pin. The lagging ADC depends on the PHASE register and on the OSR. (DEFAULT) bit 9:8 DRSTATUS<1:0>: Data Ready Status 11 = ADC Channel 1 and Channel 0 data not ready (DEFAULT) 10 = ADC Channel 1 data not ready, ADC Channel 0 data ready 01 = ADC Channel 0 data not ready, ADC Channel 1 data ready 00 = ADC Channel 1 and Channel 0 data ready bit 7:6 READ<1:0>: Address Loop Setting 11 = Address counter incremented, cycle through entire register set 10 = Address counter loops on register types (DEFAULT) 01 = Address counter loops on register groups 00 = Address not incremented, continually read single register bit 5 WRITE: Address Loop Setting for Write mode 1 = Address counter loops on entire register map (DEFAULT) 0 = Address not incremented, continually write same single register (c) 2012 Microchip Technology Inc. DS22286A-page 57 MCP3911 bit 4:3 WIDTH<1:0> ADC Channel output data word width 11 = Both channels are in 24-bit mode(DEFAULT) 10 = Channel1 in 24-bit mode, Channel0 in 16-bit mode 01 = Channel1 in 16-bit mode, Channel0 in 24-bit mode 00 = Both channels are in 16-bit mode bit 2 EN_OFFCAL Enables or disables the 24-bit digital offset calibration on both channels 1 = Enabled; this mode does not add any group delay 0 = Disabled (DEFAULT) bit 1 EN_GAINCAL Enables or disables the 24-bit digital offset calibration on both channels 1 = Enabled; this mode adds a group delay on both channels of 24 DMCLK periods. All data ready pulses are delayed by 24 clock periods compared to the mode with EN_GAINCAL=0 0 = Disabled(DEFAULT) bit 0 Unimplemented, read as 0 DS22286A-page 58 (c) 2012 Microchip Technology Inc. MCP3911 7.6 CONFIG Register - Configuration Register CONFIG Register REGISTER 7-6: Name Bits Address Cof CONFIG 16 0x0C R/W R/W-0 R/W-0 R/W-0 R/W-1 R/W-1 R/W-1 R/W-1 R/W-0 PRE<1> PRE<0> OSR<2> OSR<1> OSR<0> DITHER<1> DITHER<0> AZ_FREQ R/W-0 R/W-0 R/W-0 R/W-0 U-0 R/W-0 R/W-1 U-0 RESET<1> RESET<0> SHUTDOWN<1> SHUTDOWN<0> -- VREFEXT CLKEXT -- bit 15 bit 8 bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as `0' -n = Value at POR `1' = Bit is set `0' = Bit is cleared x = Bit is unknown bit 15:14 PRE<1:0> Analog Master Clock (AMCLK) Prescaler Value 11 = AMCLK = MCLK / 8 10 = AMCLK = MCLK / 4 01 = AMCLK = MCLK / 2 00 = AMCLK = MCLK (DEFAULT) bit 13:11 OSR<2:0> Oversampling Ratio for Delta-Sigma A/D Conversion (ALL CHANNELS, fd / fS) 111 = 4096 (fd = 244 sps for MCLK = 4 MHz, fs = AMCLK = 1 MHz) 110 = 2048 (fd = 488 sps for MCLK = 4 MHz, fs = AMCLK = 1 MHz) 101 = 1024 (fd = 976 sps for MCLK = 4 MHz, fs = AMCLK = 1 MHz) 100 = 512 (fd = 1.953 ksps for MCLK = 4 MHz, fs = AMCLK = 1 MHz) 011 = 256 (fd = 3.90625 ksps for MCLK = 4 MHz, fs = AMCLK = 1 MHz) (DEFAULT) 010 = 128 (fd = 7.8125 ksps for MCLK = 4 MHz, fs = AMCLK = 1 MHz) 001 = 64 (fd = 15.625 ksps for MCLK = 4 MHz, fs = AMCLK = 1 MHz) 000 = 32 (fd = 31.25 ksps for MCLK = 4 MHz, fs = AMCLK = 1 MHz) bit 10:9 DITHER<1:0> Control for dithering circuit for idle tones cancellation and improved THD 11 = Dithering ON, both channels, Strength = Maximum(MCP3901 Equivalent) - (DEFAULT) 10 = Dithering ON, both channels, Strength = Medium 01 = Dithering ON, both channels, Strength = Minimum 00 = Dithering turned OFF bit 8 AZ_FREQ Auto-zero frequency setting 1 = Auto-zeroing algorithm running at higher speed 0 = Auto-zeroing algorithm running at lower speed (Default) bit 7:6 RESET<1:0>: Reset mode setting for ADCs 11 = Both CH0 and CH1 ADC are in reset mode 10 = CH1 ADC in reset mode 01 = CH0 ADC in reset mode 00 = Neither ADC in reset mode(default) bit 5:4 SHUTDOWN<1:0>: Shutdown mode setting for ADCs 11 = Both CH0 and CH1 ADC in Shutdown 10 = CH1 ADC in Shutdown 01 = CH0 ADC in Shutdown 00 = Neither Channel in Shutdown(default) bit 3 Not implemented, read as 0 (c) 2012 Microchip Technology Inc. DS22286A-page 59 MCP3911 bit 2 VREFEXT Internal Voltage Reference Shutdown Control 1 = Internal Voltage Reference Disabled 0 = Internal Voltage Reference Enabled (Default) bit 1 CLKEXT Internal Clock selection bits 1 = External clock drive by MCU on OSC1 pin (crystal oscillator disabled, no internal power consumption) (Default) 0 = Crystal oscillator is enabled. A crystal must be placed between OSC1 and OSC2 pins. bit 0 Not implemented, read as 0 7.7 OFFCAL_CHn REGISTERS DIGITAL OFFSET ERROR CALIBRATION REGISTERS REGISTER 7-7: OFFCAL_CHn REGISTERS Name Bits Address Cof OFFCAL_CH0 24 0x0E R/W OFFCAL_CH1 24 0x14 R/W R/W-0 OFFCAL_CHn <23> R/W-0 R/W-0 OFFCAL_CHn OFFCAL_CHn <22> <21> ... R/W-0 R/W-0 R/W-0 R/W-0 ... OFFCAL_CHn <3> OFFCAL_CHn <2> OFFCAL_CHn <1> OFFCAL_CHn <0> bit 23 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as `0' -n = Value at POR `1' = Bit is set `0' = Bit is cleared bit 23:0 x = Bit is unknown Digital Offset calibration value for the corresponding channel CHn. This register simply is added to the output code of the channel bit-by-bit. This register is 24-bit two's complement MSB first coding. CHn Output Code = OFFCAL_CHn + ADC CHn Output Code. This register is a Don't Care if EN_OFFCAL=0 (Offset calibration disabled) but its value is not cleared by the EN_OFFCAL bit. DS22286A-page 60 (c) 2012 Microchip Technology Inc. MCP3911 7.8 GAINCAL_CHn REGISTERS DIGITAL GAIN ERROR CALIBRATION REGISTERS REGISTER 7-8: GAINCAL_CHn REGISTERS Name Bits Address Cof GAINCAL_CH0 24 0x11 R/W GAINCAL_CH1 24 0x17 R/W R/W-0 R/W-0 R/W-0 GAINCAL_CHn GAINCAL_CHn GAINCAL_CHn <23> <22> <21> ... ... R/W-0 R/W-0 R/W-0 R/W-0 GAINCAL_CHn GAINCAL_CHn GAINCAL_CHn GAINCAL_CHn <3> <2> <1> <0> bit 23 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as `0' -n = Value at POR `1' = Bit is set `0' = Bit is cleared bit 23:0 x = Bit is unknown Digital gain error calibration value for the corresponding channel CHn. This register is 24-bit signed MSB first coding with a range of -1x to +0.9999999x (from 0x80000 to 0x7FFFFF). The gain calibration adds 1x to this register and multiplies it to the output code of the channel bit by bit, after offset calibration. The range of the gain calibration is thus from 0x to 1.9999999x (from 0x80000 to 0x7FFFFF). The LSB corresponds to a 2-23 increment in the multiplier. CHn Output Code = (GAINCAL_CHn+1)*ADC CHn Output Code. This register is a Don't Care if EN_GAINCAL=0 (Offset calibration disabled) but its value is not cleared by the EN_GAINCAL bit. (c) 2012 Microchip Technology Inc. DS22286A-page 61 MCP3911 7.9 VREFCAL Register - Internal Voltage Reference Temperature Coefficient Adjustment Register REGISTER 7-9: VREFCAL REGISTER Name Bits Address Cof VREFCAL 8 0x1A R/W This register is only for advanced users. This register should not be written unless the user wants to calibrate the temperature coefficient of the whole system or application. The default value of this register is set to 0x42. R/W-0 VREFCAL<7> R/W-1 R/W-0 R/W-0 R/W-0 VREFCAL<6> VREFCAL<5> VREFCAL<4> VREFCAL<3> R/W-0 VREFCAL<2> R/W-1 R/W-0 VREFCAL<1> VREFCAL<0> bit 7 bit 0 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as `0' -n = Value at POR `1' = Bit is set `0' = Bit is cleared bit 7:0 x = Bit is unknown Internal Voltage Temperature coefficient register value. (See Section 5.7.3 "Temperature compensation (VREFCAL register)" for complete description). DS22286A-page 62 (c) 2012 Microchip Technology Inc. MCP3911 8.0 PACKAGING INFORMATION 8.1 Package Marking Information 20-Lead QFN (4x4x0.9 mm) PIN 1 Example: PIN 1 20-Lead SSOP (SS) 3911A0 e3 E/ML^^ 122256 Example: 3911A0 e3 E/SS^^ 1122256 Legend: XX...X Y YY WW NNN e3 * Note: Customer-specific information Year code (last digit of calendar year) Year code (last 2 digits of calendar year) Week code (week of January 1 is week `01') Alphanumeric traceability code Pb-free JEDEC designator for Matte Tin (Sn) This package is Pb-free. The Pb-free JEDEC designator ( e3 ) can be found on the outer packaging for this package. In the event the full Microchip part number cannot be marked on one line, it will be carried over to the next line, thus limiting the number of available characters for customer-specific information. (c) 2012 Microchip Technology Inc. DS22286A-page 63 MCP3911 ) !!"# $$ % & '( 2 % & %! % *" ) ' % * $% %"% %% 133)))& &3 * D D2 EXPOSED PAD e E2 2 E b 2 1 1 K N N NOTE 1 TOP VIEW L BOTTOM VIEW A A1 A3 4% & 5&% 6!&( $ 55, , 6 6 67 8 % 7 9 % : %" $$ . 0 %% * ./0 + 7 ;"% , ,# , "";"% 7 5% ,# ""5% ,2 /0 < : /0 < : 0 %%;"% ( : . + 0 %%5% 5 + . = > > 0 %%% ,# "" ) !"#$%! & '(!%&! %( %")% % % " * ) !%" + & "% ,-. /01 / & %#%! ))% !%% ,21 $ & '! !)% !%% '$ $ &% ! DS22286A-page 64 ) 0</ (c) 2012 Microchip Technology Inc. MCP3911 ) 2 % & %! % *" ) ' % * $% %"% %% 133)))& &3 * (c) 2012 Microchip Technology Inc. DS22286A-page 65 MCP3911 ) *+,- *$ .- ** /"0 $$ % & '**. ( 2 % & %! % *" ) ' % * $% %"% %% 133)))& &3 * D N E E1 NOTE 1 1 2 e b c A2 A A1 L1 4% & 5&% 6!&( $ L 55, , 6 6 67 8 % 7 9 % > > <. . :. %" $$ . > > 7 ;"% , : : ""*;"% , . .+ .< 7 5% < . .. . . ""* * 2 %5% 5 2 % % 5 5" 2 * % 5";"% <./0 .,2 > ? ? . :? ( > +: ) !"#$%! & '(!%&! %( %")% % % " & "," %!"& "$ % ! "$ % ! %#"&& " + & "% ,-. /01 / & %#%! ))% !%% ,21 $ & '! !)% !%% '$ $ &% ! DS22286A-page 66 ) 0/ (c) 2012 Microchip Technology Inc. MCP3911 APPENDIX A: REVISION HISTORY Revision A (March 2012) * Original Release of this Document. (c) 2012 Microchip Technology Inc. DS22286A-page 67 MCP3911 NOTES: DS22286A-page 68 (c) 2012 Microchip Technology Inc. MCP3911 PRODUCT IDENTIFICATION SYSTEM To order or obtain information, e.g., on pricing or delivery, refer to the factory or the listed sales office. PART NO. XX X Device Address Options X Tape and Temperature Reel Range /XX Package Device: MCP3911A0: Two Channel Analog Font End Converter Address Options: XX A6 A5 A0* = 0 0 A1 = 0 1 A2 = 1 0 A3 = 1 1 * Default option. Contact Microchip factory for other address options Tape and Reel: T = Tape and Reel Temperature Range: E = -40C to +125C Package: ML = Plastic Quad Flat No Lead Package (QFN) Examples: a) MCP3911A0-E/ML: Extended Temperature, Two Channel Analog Front End Converter, 20LD QFN package. b) MCP3911A0T-E/ML:Tape and Reel, Extended Temperature, Two Channel Analog Front End Converter, 20LD QFN package. c) MCP3911A0-E/SS: Extended Temperature, Two Channel Analog Front End Converter, 20LD SSOP package. d) MCP3911A0T-E/SS:Tape and Reel, Extended Temperature, Two Channel Analog Front End Converter, 20LD SSOP package. SS = Small Shrink Output Package (SSOP-20) (c) 2012 Microchip Technology Inc. DS22286A-page 69 MCP3911 NOTES: DS22286A-page 70 (c) 2012 Microchip Technology Inc. Note the following details of the code protection feature on Microchip devices: * Microchip products meet the specification contained in their particular Microchip Data Sheet. * Microchip believes that its family of products is one of the most secure families of its kind on the market today, when used in the intended manner and under normal conditions. * There are dishonest and possibly illegal methods used to breach the code protection feature. All of these methods, to our knowledge, require using the Microchip products in a manner outside the operating specifications contained in Microchip's Data Sheets. Most likely, the person doing so is engaged in theft of intellectual property. * Microchip is willing to work with the customer who is concerned about the integrity of their code. * Neither Microchip nor any other semiconductor manufacturer can guarantee the security of their code. Code protection does not mean that we are guaranteeing the product as "unbreakable." Code protection is constantly evolving. We at Microchip are committed to continuously improving the code protection features of our products. Attempts to break Microchip's code protection feature may be a violation of the Digital Millennium Copyright Act. If such acts allow unauthorized access to your software or other copyrighted work, you may have a right to sue for relief under that Act. Information contained in this publication regarding device applications and the like is provided only for your convenience and may be superseded by updates. It is your responsibility to ensure that your application meets with your specifications. MICROCHIP MAKES NO REPRESENTATIONS OR WARRANTIES OF ANY KIND WHETHER EXPRESS OR IMPLIED, WRITTEN OR ORAL, STATUTORY OR OTHERWISE, RELATED TO THE INFORMATION, INCLUDING BUT NOT LIMITED TO ITS CONDITION, QUALITY, PERFORMANCE, MERCHANTABILITY OR FITNESS FOR PURPOSE. Microchip disclaims all liability arising from this information and its use. Use of Microchip devices in life support and/or safety applications is entirely at the buyer's risk, and the buyer agrees to defend, indemnify and hold harmless Microchip from any and all damages, claims, suits, or expenses resulting from such use. No licenses are conveyed, implicitly or otherwise, under any Microchip intellectual property rights. Trademarks The Microchip name and logo, the Microchip logo, dsPIC, KEELOQ, KEELOQ logo, MPLAB, PIC, PICmicro, PICSTART, PIC32 logo, rfPIC and UNI/O are registered trademarks of Microchip Technology Incorporated in the U.S.A. and other countries. FilterLab, Hampshire, HI-TECH C, Linear Active Thermistor, MXDEV, MXLAB, SEEVAL and The Embedded Control Solutions Company are registered trademarks of Microchip Technology Incorporated in the U.S.A. Analog-for-the-Digital Age, Application Maestro, chipKIT, chipKIT logo, CodeGuard, dsPICDEM, dsPICDEM.net, dsPICworks, dsSPEAK, ECAN, ECONOMONITOR, FanSense, HI-TIDE, In-Circuit Serial Programming, ICSP, Mindi, MiWi, MPASM, MPLAB Certified logo, MPLIB, MPLINK, mTouch, Omniscient Code Generation, PICC, PICC-18, PICDEM, PICDEM.net, PICkit, PICtail, REAL ICE, rfLAB, Select Mode, Total Endurance, TSHARC, UniWinDriver, WiperLock and ZENA are trademarks of Microchip Technology Incorporated in the U.S.A. and other countries. SQTP is a service mark of Microchip Technology Incorporated in the U.S.A. All other trademarks mentioned herein are property of their respective companies. (c) 2012, Microchip Technology Incorporated, Printed in the U.S.A., All Rights Reserved. Printed on recycled paper. ISBN: 978-1-62076-094-9 Microchip received ISO/TS-16949:2009 certification for its worldwide headquarters, design and wafer fabrication facilities in Chandler and Tempe, Arizona; Gresham, Oregon and design centers in California and India. The Company's quality system processes and procedures are for its PIC(R) MCUs and dsPIC(R) DSCs, KEELOQ(R) code hopping devices, Serial EEPROMs, microperipherals, nonvolatile memory and analog products. In addition, Microchip's quality system for the design and manufacture of development systems is ISO 9001:2000 certified. (c) 2012 Microchip Technology Inc. DS22286A-page 71 Worldwide Sales and Service AMERICAS ASIA/PACIFIC ASIA/PACIFIC EUROPE Corporate Office 2355 West Chandler Blvd. Chandler, AZ 85224-6199 Tel: 480-792-7200 Fax: 480-792-7277 Technical Support: http://www.microchip.com/ support Web Address: www.microchip.com Asia Pacific Office Suites 3707-14, 37th Floor Tower 6, The Gateway Harbour City, Kowloon Hong Kong Tel: 852-2401-1200 Fax: 852-2401-3431 India - Bangalore Tel: 91-80-3090-4444 Fax: 91-80-3090-4123 India - New Delhi Tel: 91-11-4160-8631 Fax: 91-11-4160-8632 Austria - Wels Tel: 43-7242-2244-39 Fax: 43-7242-2244-393 Denmark - Copenhagen Tel: 45-4450-2828 Fax: 45-4485-2829 India - Pune Tel: 91-20-2566-1512 Fax: 91-20-2566-1513 France - Paris Tel: 33-1-69-53-63-20 Fax: 33-1-69-30-90-79 Japan - Osaka Tel: 81-66-152-7160 Fax: 81-66-152-9310 Germany - Munich Tel: 49-89-627-144-0 Fax: 49-89-627-144-44 Atlanta Duluth, GA Tel: 678-957-9614 Fax: 678-957-1455 Boston Westborough, MA Tel: 774-760-0087 Fax: 774-760-0088 Chicago Itasca, IL Tel: 630-285-0071 Fax: 630-285-0075 Cleveland Independence, OH Tel: 216-447-0464 Fax: 216-447-0643 Dallas Addison, TX Tel: 972-818-7423 Fax: 972-818-2924 Detroit Farmington Hills, MI Tel: 248-538-2250 Fax: 248-538-2260 Indianapolis Noblesville, IN Tel: 317-773-8323 Fax: 317-773-5453 Los Angeles Mission Viejo, CA Tel: 949-462-9523 Fax: 949-462-9608 Santa Clara Santa Clara, CA Tel: 408-961-6444 Fax: 408-961-6445 Toronto Mississauga, Ontario, Canada Tel: 905-673-0699 Fax: 905-673-6509 Australia - Sydney Tel: 61-2-9868-6733 Fax: 61-2-9868-6755 China - Beijing Tel: 86-10-8569-7000 Fax: 86-10-8528-2104 China - Chengdu Tel: 86-28-8665-5511 Fax: 86-28-8665-7889 China - Chongqing Tel: 86-23-8980-9588 Fax: 86-23-8980-9500 Korea - Daegu Tel: 82-53-744-4301 Fax: 82-53-744-4302 China - Hangzhou Tel: 86-571-2819-3187 Fax: 86-571-2819-3189 Korea - Seoul Tel: 82-2-554-7200 Fax: 82-2-558-5932 or 82-2-558-5934 China - Hong Kong SAR Tel: 852-2401-1200 Fax: 852-2401-3431 Malaysia - Kuala Lumpur Tel: 60-3-6201-9857 Fax: 60-3-6201-9859 China - Nanjing Tel: 86-25-8473-2460 Fax: 86-25-8473-2470 Malaysia - Penang Tel: 60-4-227-8870 Fax: 60-4-227-4068 China - Qingdao Tel: 86-532-8502-7355 Fax: 86-532-8502-7205 Philippines - Manila Tel: 63-2-634-9065 Fax: 63-2-634-9069 China - Shanghai Tel: 86-21-5407-5533 Fax: 86-21-5407-5066 Singapore Tel: 65-6334-8870 Fax: 65-6334-8850 China - Shenyang Tel: 86-24-2334-2829 Fax: 86-24-2334-2393 Taiwan - Hsin Chu Tel: 886-3-5778-366 Fax: 886-3-5770-955 China - Shenzhen Tel: 86-755-8203-2660 Fax: 86-755-8203-1760 Taiwan - Kaohsiung Tel: 886-7-536-4818 Fax: 886-7-330-9305 China - Wuhan Tel: 86-27-5980-5300 Fax: 86-27-5980-5118 Taiwan - Taipei Tel: 886-2-2500-6610 Fax: 886-2-2508-0102 China - Xian Tel: 86-29-8833-7252 Fax: 86-29-8833-7256 Thailand - Bangkok Tel: 66-2-694-1351 Fax: 66-2-694-1350 Italy - Milan Tel: 39-0331-742611 Fax: 39-0331-466781 Netherlands - Drunen Tel: 31-416-690399 Fax: 31-416-690340 Spain - Madrid Tel: 34-91-708-08-90 Fax: 34-91-708-08-91 UK - Wokingham Tel: 44-118-921-5869 Fax: 44-118-921-5820 China - Xiamen Tel: 86-592-2388138 Fax: 86-592-2388130 China - Zhuhai Tel: 86-756-3210040 Fax: 86-756-3210049 DS22286A-page 72 Japan - Yokohama Tel: 81-45-471- 6166 Fax: 81-45-471-6122 11/29/11 (c) 2012 Microchip Technology Inc.