F Semiconductor Thermally Protected High Voltage Linear Regulator The HIP5600 is an adjustable 3-terminal positive linear voltage regulator capable of operating up to either 400Vpc or 280Vpms. The output voltage is adjustable from 1.2Vp to within 50V of the peak input voltage with two external resistors. This high voltage linear regulator is capable of sourcing 1mA to 30mA with proper heat sinking. The HIP5600 can also provide 40mA peak (typical) for short periods of time. Protection is provided by the on chip thermal shutdown and output current limiting circuitry. The HIP5600 has a unique advantage over other high voltage linear regulators due to its ability to withstand input to output voltages as high as 400V (peak), a condition that could exist under output short circuit conditions. Common linear regulator configurations can be implemented as well as AC/DC conversion and start-up circuits for switch mode power supplies. The HIP5600 requires a minimum output capacitor of 10uF for stability of the output and may require a 0.02uF input decoupling capacitor depending on the source impedance. It also requires a minimum load current of 1mA to maintain output voltage regulation. All protection circuitry remains fully functional even if the adjustment terminal is disconnected. However, if this happens the output voltage will approach the input voltage. HIP5600 September 1998 File Number 3270.7 Features * Operates from 50Vpc to 400Vpc * Operates from 50Vpys to 280V Ais Line UL Recognized * Variable DC Output Voltage 1.2Vpc to Vix - 50V * Internal Thermal Shutdown Protection * Internal Over Current Protection * Up to 40mA Peak Output Current * Surge Rated to +650V; Meets IEEE/ANSI C62.41.1980 with Additional MOV CAUTION: This product does not provide isolation from AC line. Applications * Switch Mode Power Supply Start-Up * Electronically Gommutated Motor Housekeeping Supply Power Supply for Simple Industrial/Commercial/Consumer Equipment Controls * Off-Line (Buck) Switch Mode Power Supply Ordering Information PART NUMBER TEMP. RANGE PACKAGE HIP5600IS -40C to +100C | 3 Lead Plastic SIP HIP56001S2 -40C to +100C 3 Lead Gullwing Plastic SIP Pinouts HIP5600 (TO-220) TOP VIEW TAB ELECTRICALLY CONNECTED TO Vout O Vout HIP5600 ADJ Vout VIN HIP5600 (MO-169) TOP VIEW a O ADJ T_] Vw Vi CAUTION: These devices are sensitive to electrostatic discharge; follow proper IC Handling Procedures. Copyright Harris Corporation 1998HIP5600 Functional Block Diagram VIN C1 RECTIFIER FOR AC OPERATION THERMAL SHUTDOWN HIP5600 PASS TRANSISTOR PROTECTION BIAS NETWORK FEEDBACK OR CONTROL AMPLIFIER VOLTAGE REFERENCE ADJ SHORT-CIRCUIT Schematic Diagram VIN > >| > * Di D2 Ri D4 R2= LE 4 ha > R4 < AAA VVV au ou -__Kas Q12 Q Q13 An wv VvVY AA vVVvY Q14 R14 R15 Rg ADJ <AAA_1 a7k, as mA FIGURE 1. > VouT 2 | HARRISHIP5600 Absolute Maximum Ratings Thermal Information (Typical) Input to Output Voltage, Continuous............. +480V to -550V Thermal Resistance OIA 9Jc Input to Output Voltage, Peak (Non Repetitive, 2ms)........ +650V Plastic SIP Package .............. 60C/W 4C/wW Junction Temperature... .. 6... .0..0. 0.0.00. .000 0000 +150C ADJ to Output, Voltage to ADJ... eee ee +5V Storage Temperature Range ................. -65C to +150C Lead Temperature (Soldering 10s).................... +265C CAUTION: Stresses above those listed in Absolute Maximum Ratings may cause permanent damage to the device. This is a stress only rating and operation of the device at these or any other conditions above those indicated in the operational sections of this specification is not implied. Operating Conditions Operating Voltage Range.............. 80VRmsto280VAMmsor Operating Temperature Range................ -40C to +100C 50Vpc to 400Vpc Electrical Specifications Conditions Vij = 400VDC, I, = 1mA, C, = 10UF Vapy = 3.79V, Vout = 5V (Unless Otherwise Specified) Tem- perature = Case Temperature. PARAMETER CONDITION TEMP MIN TYP MAX UNITS INPUT Input Voltage DC Full 50 - 400 v Max Peak Input Voltage Non-Repetitive (2ms) Full - - +650 Vv Input Frequency (Note 1) Full DC - 1000 Hz Bias Current (IBjas Note 2) Full 0.4 0.5 0.6 mA REFERENCE lADJ 425C 50 65 80 HA laDJTc (Note 1) IL=1mA Full - +0.15 - LAC IADJ LOAD REG (Note 1) IL =1mA to 10mA 425C - -215 - nA/mA Vrer (Note 3) +25C 1.07 1.18 1.30 V Vrer Tc (Note 1) IL=1mA Full - -460 - uVPC Line Regulation 5SOVDC to 400VDC +25C - 9 145 yV/V VREF LINE REG Full - 9 29 yv/V Load Regulation lout = 1mA to 10mA 425C - 3 5 mV/mA VREF LOAD REG Full - 3 6 mV/mA PROTECTION CIRCUITS Output Short Circuit Current Limit VIN = 50V +25C 35 - 45 mA Thermal Shutdown TTs VIN = 400V - 127 134 142 C (IC surface, not case temperature. Note 1) Thermal Shutdown Hysteresis (Note 1) VIN = 400V - - 34 - C NOTES: 1. Characterized not tested 2. Bias current = input current with output pin floating. 3. VReF= Vout VabJ 3 | BARRISHIP5600 Application information Introduction In many electronic systems the components operate at 3V to 15V but the system obtains power from a high voltage source (AC or DC). When the current requirements are small, less than 10mA, a linear regulator may be the best supply provided that it is easy to design in, reliable, low cost and compact. The HIP5600 is similar to other 3 terminal reg- ulators but operates from much higher voltages. It protects its load from surges +250V above its 400V operating input voltage and has short circuit current limiting and thermal shutdown self protection features. Ouiput Voltage The HIP5600 provides a temperature independent 1.18V reference, Vref, between the output and the adjustment terminal (VREF = Vout - Vapg). This constant reference voltage is impressed across RF1 (see Figure 2) and results in a constant current (l,) that flows through RF2 to ground. The voltage across RF2 is the product of its resistance and the sum of ly and lapy, The output voltage is given in Equa- tions 1(A, B). RF1+RF2 Yout = rer Req *!apy(RFA) (FQ. 1A) RF1+RF2 Vout = (1.18) x = + 65H A(RF2) (EQ. 1B) Error Budget _ awt RF1+RF2 T ARF2 AVout = AV per gee +Al ADJRF2+ apy RF2 RF2 RF2\/ARF2 ARF1 v.__(BE2\(ARF2 ARF1 EQ. 2A * rer(aea) RF2 a) ( ) Where; T _ Veer = Veer + YREF oaprea our t VrertCCATemp) Var C(O ga) Al gut Yin) + Vace NEREG (EQ. 2B) T= Al ADJ =Alypy + 'ADJLOADREG lout? + IapytClATemp) than jTC(On, ACI Vin) ADJ sAVouT IN EQ. 2C Note: ( ARFx = % tolerance of resistor x RFx Equations 2(A,B,C) are provided to determine the worst case output voltage in relation to; manufacturing tolerances (AVReF and Alper),% tolerance in external resistors (ARF1/RF1, ARF2/RF2), load regulation (VREF LOAD REG: [ADJ LOAD REG): line regulation (VREF LINE REG) and the effects of temperature (VpeFIC, IpeFTC), which includes self heating (Osa). VouT(NOMINAL) | RF1 | RF2 HIP5600 3.3V 3.6k | 5.6k AC/DC 4.9V 2.7k | 7.5k Y 12.0V 1.8k 15k 14.8V 1.1k 12k eh yf > RFA OUT I ADJ 2 RF2 | t Ac/DC FIGURE 2. Example: Given: Vij = 200Vpc, Vout = 15V, louT = 2mA to 12mA, Osa = 10C/W, RF1 = 1.1kQ 5% low, RF2 = 12kQ 5% high, Aloyt equals 10mA and ATemp equals +60C (ambient temperature +25C to +85C). The worst case AVoyt for the given conditions is -1.13V. The shift in VouT is attributed to the following: -1.55V manufacturing tol- erances, +1.33V external resistors, -0.62V load regulation and -0.29V temperature effects. Regulator With Zener Vout = 1.18 + Vz Mer VouT Vz 3.7V 2.5V 5.1V 3.9V 10.3V 9.1V 12.2V 11V T | { > RFA 16.2V 15V OUT laDJ Ln Vz | RF1 = 10k Ac/DC FIGURE 3. The output voltage can be set by using a zener diode (Figure 3) instead of the resistor divider shown in Figure 2. The zener diode improves the ripple rejection ratio and reduces the value of the worst case output voltage, as illustrated in the example to follow. The bias current of the zener diode is set by the value of RF1 and lapy. The regulator / zener diode becomes an attractive solution if ripple rejection or the worst case tolerance of the output volt- age is critical (i.e. one zener diode cost less than one 10uF capacitor (C3) and one 1/4W resistor RF2). Minimum power dissipation is possible by reducing |; current, with little effect on the output voltage regulation. The output voltage is given in Equation 3. Equations 4(A,B,C) are provided to determine the worst case output voltage in relation to; manufacturing tolerances 4 | BARRISHIP5600 Vout = Yrer*Yz (EQ. 3) Error Budget AVoyz = AV REF + AV'2 (EQ. 4A) AV pep =AVper + VREFLoapREG Sour) + VrerTO(ATemp) +VpeeTClOga) Alloys: Vin) + VRE ELINEREG (EQ. 4B) Avls = Vztolerance(V>) + VzTC(ATem p) (EQ. 4C) of HIP5600 and the zener diode (AVp_r and AV,), load reg- ulation of the HIP5600 (VREF LOAD REG), and the effects of temperature on the HIP5600 and the zener diode (VpEFTC, VzTC). Example: Given: Viy = 200V, VouT = 14.18V (VREF = 1.18V, Vz = 13V), AVz = 5%, V7TC = +0.079%/C (assumes 1N5243BPH), Algyt equal 10mA and ATemp equal +60C. The worst case AVoytT is 0.4956V. The shift in Vout is attributed to the following: -0.2 (HIP5600) and 0.69 (zener diode). The regulator/zener diode configuration gives a 3.5% (0.49/14.18) worst case output voltage error where, for the same conditions, the regulator/resistor configuration results in an 7.5% (1.129/15) worst case output voltage error. External Capacitors A minimum10uF output capacitor (C2) is required for stability of the output stage. Any increase of the load capacitance greater than 10uF will merely improve the loop stability and output impedance. A 0.02uUF input decoupling capacitor (C1) between Vj, and ground may be required if the power source impedance is not sufficiently low for the 1MHz - 10MHz band. Without this capacitor, the HIP5600 can oscillate at 2.5MHz when driven by a power source with a high impedance for the 1MHz - 10MHz band. An optional bypass capacitor (C3) from Vapy to ground improves the ripple rejection by preventing the ripple at the Adjust pin from being amplified. Bypass capacitors larger than 10uF do not appreciably improve the ripple rejection of the part (see Figure 20 through Figure 25). Load Regulation For improved load regulation, resistor RF1 (connected between the adjustment terminal and Voyt) should be tied directly to the output of the regulator (Figure 4A) rather than near the load Figure 4B. This eliminates line drops (Rg) from appearing effectively in series with RF1 and degrading regu- lation. For example, a 15V regulator with a 0.05 resistance between the regulator and the load will have a load regula- tion due to line resistance of 0.05 x Al,. If RF1 is con- nected near the load the effective load regulation will be 11.9 times worse (1+R2/R1, where R2 = 12k, R1 = 1.1k). HIP5600 HIP5600 AC/DC AC/DC = = / a a < < Rs ! ry { s { > RFA > Vout Vout l l ADJ Sapo | ADS Spero | AC/DC AC/DC B 4) FIGURE 4. () Protection Diodes The HIP5600, unlike other voltage regulators, is internally protected by input diodes in the event the input becomes shorted to ground. Therefore, no external protection diode is required between the input pin and the output pin to protect against the output capacitor (C2) discharging through the input to ground. If the output is shorted in the absence of D1 (Figure 5), the bypass capacitor voltage (C3) could exceed the absolute maximum voltage rating of +5V between Voyt and Vjy. Note; No protection diode (D1) is needed for output voltages less than 6V or if C3 is not used. HIP5600 VIN C1 DISCHARGING WHEN THE OUTPUT IS SHORTED. 0.02uF Di PROTECTS AGAINST C3 + Vout FIGURE 5. REGULATOR WITH PROTECTION DIODE Selecting the Right Heat Sink Linear power supplies can dissipate a lot of power. This power or heat must be safely dissipated to permit continuous operation. This section will discuss thermal resistance and show how to calculate heat sink requirements. Electronic heat sinks are generally rated by their thermal resistance. Thermal resistance is defined as the temperature rise per unit of heat transfer or power dissipated, and is expressed in units of degrees centigrade per watt. For a par- ticular application determine the thermal resistance (@g,) which the heat sink must have in order to maintain a junction temperature below the thermal shut down limit (TT3). 5 | BARRISHIP5600 A thermal network that describes the heat flow from the inte- grated circuit to the ambient air is shown in Figure 6. The basic relation for thermal resistance from the IC surface, his- torically called junction, to ambient (8a) is given in Equa- tion 5. The thermal resistance of the heat sink (@s,) to maintain a desired junction temperature is calculated using Equation 6. Ty = JUNCTION < + oD c Qo Te = CASE < fan) 9 a AA AAA V" YYY Ts = HEAT SINK # > S9sq HEAT SINK Ta = AMBIENT AIR _ FIGURE 6. 9. - tA (C JA=p [yw (EQ. 5) Where: 9a = %9c*8%es*8sa and Ty=TTs Tre_T ts la Where: 6 Ja = (Junction to Ambient Thermal Resistance) The sum of the thermal resistances of the heat flow path. 8JA = 8Jc + OCs + OSA Ty = (Junction Temperature) The desired maximum junc- tion temperature of the part. Ty = TTs Tts = (Thermal Shutdown Temperature) The maximum junction temperature that is set by the thermal pro- tection circuitry of the HIP5600 (min = +127C, typ = +134C and max = +142C). 8jc = (Junction to Case Thermal Resistance) Describes the thermal resistance from the IC surface to its case. 8Ic= 4.8C/W 8cs = (Case to Mounting Surface Thermal Resistance) The resistance of the mounting interface between the transistor case and the heat sink. For example, mica washer. 8sa = (Mounting Surface to Ambient Thermal Resistance) The resistance of the heat sink to the ambient air. Varies with air flow. Ta = Ambient Temperature P = The power dissipated by the HIP5600 in watts. P = (Vin- VouTtMlout) Worst case Oe, is calculated using the minimum Trs of +127C in Equation 6. Example, Given: Vin =400Vpc Vout = 15V 8c =4.8CWW Trg=4+127C laps = 800A Ta = +50C RF1 = 1.1k VReF= 1.18V P= 6.2W = (Vin - VouT)(in) ILOAD = 15mA al VREF IN='ADJ* RET ~ LOAD Find: Proper heat sink to keep the junction temperature of the HIP5600 from exceeding TT (+127C). Solution: Use Equation 6, 9. - TS 'A 4 SA>~p JC (EQ. 7) 127C 50C C 8ga = 35 -48 C= 7.6207 (EQ. 8) The selection of a heat sink with Og, less than +7.62C/W would ensure that the junction temperature would not exceed the thermal shut down temperature (TT) of +127C. A Thermalloy P/N7023 at 6.2W power dissipation would meet this requirement with a Og, of +5.7C/W. Operation Without A Heatsink The package has a 6a of +60C/W. This allows 0.7W power dissipation at +85C in still air. Mounting the HIP5600 to a printed circuit board (see Figure 39 through Figure 41) decreases the thermal impedance sufficiently to allow about 1.6W of power dissipation at +85C in still air. Thermal Transient Operation For applications such as start-up, the HIP5600 in the TO-220 package can operate at several watts -without a heat sink- for a period of time before going into thermal shutdown. om Pp = lin (Vin - Vout) q Ty = JUNCTION @ | > 0.66jc Cp | DIE/PACKAGE INTERFACE Ts = HEAT SINK OR CASE CS +0.5Cp T, = AMBIENT AIR FIGURE 7. THERMAL CAPACITANCE MODEL OF HIP5600 Figure 7 shows the thermal capacitances of the TO-220 package, the integrated circuit and the heat sink, if used. When power is initially applied, the mass of the package absorbs heat which limits the rate of temperature rise of the 6 | BARESHIP5600 junction. With no heat sink Cs equals zero and @s,a equals the difference between ja and @jc. The following equations pre- dict the transient junction temperature and the time to thermal shutdown for ambient temperatures up to +85C and power levels up to 8W. The output current limit temperature coeffi- cient (Figure 39) precludes continuous operation above 8W. -t T(t) = Tr#P Qo *PO5,| 1-6) (EQ. 9) Where: T=Ooq(Cp + Cg) P(O)n4+0ceq)+T, -T. t = od (EQ. 10) POca For the TO-220, Cp is 0.9Ws to 1.1Ws per degree compared to about 2.6mWs per degree for the integrated circuit and Cs is 0.9Ws per degree per gram for aluminum heat sinks. Figure 8 shows the time to thermal shutdown versus power dissipation for a part in +22C still air and at various elevated ambient temperatures with a 8g, of +27C/W from forced air flow. For the shorter shutdown times, the Oga value is not impor- tant but the thermal capacitances are. A more accurate equation for the transient silicon surface temperature can be derived from the model shown in Figure 7. Due to the distrib- uted nature of the package thermal capacitance, the second time constant is 1.7 times larger than expected. 102 TIME TO THERMAL SHUTDOWN (s) 3 3 2%, >, = oc 4 +115C +120 C 10-2 0.0 2.0 4.0 6.0 8.0 10 POWER DISSIPATION (W) FIGURE 8. TIME TO THERMAL SHUTDOWN vs POWER DISSIPATION Ty) = Ty +Ty+To+T3 (EQ. 11A) -t - a1 T, Po 1 Where: (EQ. 11B) T1 =O, (Cp t+ Cg) +t - 72 Ty= 04P yg -e (EQ. 11C) Where: 2076 (* + 3?) Jc Cp + Cg at Ts -08P Qc 8 (EQ. 11D) Where: T= 0.69 Sp Thermal Shutdown Hysteresis Figure 9 shows the HIP5600 thermal hysteresis curve with Vin = 100Vpc, Vout = 5V and Ioyt = 10mA. Hysteresis is added to the thermal shutdown circuit to prevent oscillations as the junction temperature approaches the thermal shut- down limit. The thermal shutdown is reset when the input voltage is removed, goes negative (i.e. AC operation) or when the part cools down. 10 1 1 tos HEATING 8.0 = 6.0 \ SHUTDOWN E \ REGION ke 2 o = 40 \ COOLING | 2.0 ~K OOF peepee tee puede 98.0 105.0 113.0 120 127 135 142 CASE TEMPERATURE (C) FIGURE 9. THERMAL HYSTERESIS CURVE AC to DC Operation Since the HIP5600 has internal high voltage diodes in series with its input, it can be connected directly to an AC power line. This is an improvement over typical low current supplies constructed from a high voltage diode and voltage dropping resistor to bias a low voltage zener. The HIP5600 provides better line and load regulation, better efficiency and heat 7 | BARESHIP5600 transfer. The latter because the TO-220 package permits easy heat sinking. The efficiency of either supply is approximately the DC output voltage divided by the RMS input voltage. The resistor value, in the typical low current supply, is chosen such that for maximum load at minimum line voltage there is some current flowing into the zener. This resistor value results in excess power dissipation for lighter loads or higher line voltages. Using the circuit in Figure 3 with a 1000uF output capacitor the HIP5600 only takes as much current from the power line as the load requires. For light loads, the HIP5600 is even more efficient due to its interaction with the output capacitor. Immediately after the AC line goes positive, the HIP5600 tries to replace all the charge drained by the load during the negative half cycle at a rate limited by the short circuit cur- rent limit (see A1 and B1 Figure 10). Since most of this charge is replaced before the input voltage reaches its RMS value, the power dissipation for this charge is lower than it would be if the charge were transferred at a uniform rate dur- ing the cycle. When the product of the input voltage and cur- rent is averaged over a cycle, the average power is less than if the input current were constant. Figure 11 shows the HIP5600 efficiency as a function of load current for 80Vanys and 132Vpms inputs for a 15.6V output. 120VRms; 60Hz A IN 20mA/DIV. Vout A2 | 100mV/DIV. 2ms/DIV. FIGURE 10. AC OPERATION 25 aN b VIN = 80VRMsS 23 Ne 21 $19 ae > 9 18 ww 3 Vin = 132VRMs iL 16 Le WW 14 12 _ Vout = 15.6Vpc WOR ep ppp raays teed piss ened 0.0 5.0 10.0 15.0 LOAD CURRENT (mA) FIGURE 11. EFFICIENCY AS A FUNCTION OF LOAD CURRENT Referring again to Figure 10, Curve A1 shows the input current for a 10mA output load and curve B1 with a 3mA output load. The input current spike just before the negative going zero crossing occurs while the input voltage is less than the minimum operating voltage but is so short it has no detrimental effect. The input current also includes the charg- ing current for the 0.02uF input decoupling capacitor C1. The maximum load current cannot be greater than 1/2 of the short circuit current because the HIP5600 only conducts over 1/2 of the line cycle. The short circuit current limit (Figure 38) depends on the case temperature, which is a function of the power dissipation. Figure 38 for a case temperature of +100C (i.e. no heat sink) indicates for AC operation the maximum available output current is 10mA (1/2 x 20mA). Operation from full wave rectified input will increase the maximum output current to 20mA for the same +100C case temperature. As a reminder, since the HIP5600 is off during the negative half cycle, the output capacitor must be large enough to sup- ply the maximum load current during this time with some acceptable level of droop. Figure 10 also shows the output ripple voltage, for both a 10mA and 3mA output loads A2 and B2, respectively. Dos And Donts DC Operation 1. Do not exceed the absolute maximum ratings. 2. The HIP5600 requires a minimum output current of 1mA. Minimum output current includes current through RF1. Warning: If there is less than 1mA load current, the out- put voltage will rise. If the possibility of no load exists, RF1 should be sized to sink 1mA under these conditions. VREF _ 1.07V RFIMIN = ma = tma 7 K2 3. Do not HOT switch the input voltage without protecting the input voltage from exceeding +650V. Note: induc- tance from supplies and wires along with the 0.02uUF decoupling capacitor can form an under damped tank cir- cuit that could result in voltages which exceed the maxi- mum +650V input voltage rating. Switch arcing can further aggravate the effects of the source inductance creating an over voltage condition. Recommendation: Adequate protection means (such as MOV, avalanche diode, surgector, etc.) may be needed to clamp transients to within the +650V input limit of the HIP5600. 4. Do not operate the part with the input voltage below the minimum 50Vpe recommended. Low voltage opera- tion: For input voltages between OVpc and +5Vpc noth- ing happens (IgyT=90), for input voltages between +5Vpc and +35Vpc there is not enough voltage for the pass transistor to operate properly and therefore a high frequency (2MHz) oscillation occurs. For input voltages +35Vpc to +50Vpc proper operation can occur with some parts. 8 | BARRISHIP5600 5. Warning: the output voltage will approach the input volt- age if the adjust pin is disconnected, resulting in perma- nent damage to the low voltage output capacitor. AC Operation 1. Do not exceed the absolute maximum ratings. 2. The HIP5600 requires a minimum output current of 0.5mA. Minimum output current includes current through RF1. Warning: If there is less than 0.5mA output current, the output voltage will rise. If the possibility of no load exists, RF1 should be sized to sink 0.5mA under these conditions. Vv _ REF 1.07V _ RFIMIN = o5mA ~ 0.5mA = 2K 3. If using a laboratory AC source (such as VARIACs or step-up transformers, etc.) be aware that they contain large inductances that can generate damaging high volt- age transients when they are switched on or off. Recommendations (1) Preset VARIAC output voltage before applying power to part. (2) Adequate protection means (such as MOV, avalanche diode, surgector, etc.) may be needed to clamp tran- sients to within the +650V input limit of the HIP5600. 4. Do not operate the part with the input voltage below the minimum 50VRys recommended. Low voltage opera- tion similar to DC operation (reference step 4 under DC operation). 5. Warning: the output voltage will approach the input volt- age if the adjust pin is disconnected, resulting in perma- nent damage to the low voltage output capacitor. General Precautions Instrumentation Effects Background: Input to output parasitic impedances exist in most test equipment power supplies. The inter-winding capacitance of the transformer may result in substantial cur- rent flow (mA) from the equipment power lines to the DC ground of the HIP5600. This ground loop current can result in erroneous measurements of the circuits performance and in some cases lead to overstress of the HIP5600. Recommendations for Evaluation of the HIP5600 in the Lab a) The use of battery powered DVMs and scopes will elimi- nate ground loops. b) When connecting test equipment, locate grounds as close to circuit ground as possible. c) Input current measurements should be made with a non- contact current probe. If AC powered test equipment is used, then the use of an isolated plug is recommended. The isolated plug eliminates any voltage difference between earth ground and AC ground. However, even though the earth ground is discon- nected, ground loop currents can still flow through trans- former of the test equipment. Ground loops can be minimized by connecting the test equipment ground as close to the circuit ground as possible. GAUTION: Dangerous voltages may appear on exposed metal surfaces of AC powered test equipment. Application Circuits HIP5600 + 50VDC TO 400VDC BUS FIGURE 12. DC/DC CONVERTER The HIP5600 can be configured in most common DC linear regulator applications circuits with an input voltage between 50Vpc to 400Vpc (above the output voltage) see Figure 12. A 10uF capacitor (C2) provides stabilization of the output stage. Heat sinking may be required depending upon the power dissipation. Normally, choose RF1 << Vrer/lapy- HIP5600 flow ~---- 4 \ (NOTE 1) J 1kQ J ct 0.02uF s s SURGE 4 , + Vout | PROTECTION } < RF1 NOTE 1. 200Vams - 280VaMs c2 Operation Only 10uF C3 >RF2 10uF > FIGURE 13. AC/DC CONVERTER The HIP5600 can operate from an AC voltage between 50Vams to 280Vpmys, see Figure 13. The combination of a 1kQ (2W) input resistor and a V275LA10B MOV provides input surge protection up to 6kV 1.2 x 50us oscillating and pulse waveforms as defined in IEEE/ANSI C62.41.1980. When operating from 120Vac, a V130LA10B MOV provides protection without the 1kQ resistor. The output capacitor is larger for operation from AC than DC because the HIP5600 only conducts current during the posi- tive half cycle of the AC line. The efficiency is approximately equal to Vout /Vin (RMS), see Figure 11. 9 | BARRISHIP5600 The HIP5600 provides an efficient and economical solution as a start-up supply for applications operating from either AC (50Vpms to 280Vpys) or DC (50Vpc to 400Vpc). _O _| N\ ey + 50Vpc TO 400Vpc BUS Vout FIGURE 14. START UP CIRCUIT The HIP5600 has on chip thermal protection and output cur- rent limiting circuitry. These features eliminate the need for an in-line fuse and a large heat sink. The HIP5600 can provide up to 40mA for short periods of time to enable start up of a switch mode power supplys control cir- cuit. The length of time that the HIP5600 will be on, prior to thermal shutdown, is a function of the power dissipation in the HIP5600 +20Vpc TO +400Vpc NOTES: LOAD 1. Vout Floating T 2. Fixed 500A Current Source FIGURE 15. CONSTANT 450A CURRENT SOURCE part, the amount of heat sinking (if any) and the ambient tem- perature. For example; at 400Vpc with no heat sink, it will pro- vide 20mA for about 8s, see Figure 8. Power supply efficiency is improved by turning off the HIP5600 when the SMPS is up and running. In this applica- tion the output of the HIP5600 would be set via RF1 and RF2 to be about 9V. The tickler winding would be adjusted to about 12V to insure that the HIP5600 is kept off during normal oper- ating conditions.The input current under these conditions is approximately equal to IBjas. (See Figure 27). The HIP5600 can supply a 450A (420%) constant current. (See Figure 15). It makes use of the internal bias network. See Figure 27 for bias current versus input voltage. With the addition of a potentiometer and a 10uF capacitor the HIP5600 will provide a constant current source. Igy is given by Equation 13 in Figure 16. The HIP5600 can control a P-channel MOSFET or IGPT ina self-oscillating buck regulator. The circuit shown (Figure 17) shows the self-oscillating concept with a P-IGBT driving a dedicated fan load. The output voltage is set by the resistor combination of RF1, RF2, and RF3. Components C3 and RF3 impresses the output ripple voltage across RF1 causing the HIP5600 to oscillate and control the conduction of the P-IGBT. The start-up protection components limit the initial surge current in the P-IGBT by forcing this device into its active region. The snubber circuit is recommended to reduce the power dissipation of the P-IGBT. la llegel ei] 8) +50Vpc TO +400Vpc 0.02uF >? lve a e2t out OUT =3 (EQ. 13) FIGURE 16. ADJUSTABLE CURRENT SOURCE 10 | BARESHIP5600 HIP5600 ADJ es] oo AA v + - ~ pc ~~ FAN FIGURE 17. HIGH CURRENT BUCK REGULATOR CONCEPT Typical Performance Curves OUTPUT VOLTAGE DEVIATION (%) RIPPLE REJECTION (dB) -0.4 1mA TO 10mA -1.0 1mA TO 20mA 1mA TO 30mA Vin = 50Vpc -40 -20 0 25 40 60 80 100 CASE TEMPERATURE (C) FIGURE 18. LOAD REGULATION vs TEMPERATURE 85 80 Vin = 170Vpe, IL = 10mA, f = 120Hz, Tc = +25C 75 70 1u,.F BYPASS CAPACITOR 65 10uF BYPASS CAPACITOR 60 55 50 - NO BYPASS CAPACITOR 45 0 10 20 30 40 50 60 70 80 90 100 110 OUTPUT VOLTAGE (V) FIGURE 20. RIPPLE REJECTION RATIO (OUTPUT VOLTAGE) | 2 <3 1mA TO 10mA 4 5 6 1mA TO 20mA 7 -8 TT 1mA TO 320mA -9 Vin = 400Vpc OUTPUT VOLTAGE DEVIATION (%) -10 -40 -20 0 25 40 60 80 CASE TEMPERATURE (C) FIGURE 19. LOAD REGULATION VS. TEMPERATURE 90 T T T T T T Vin = 400Vpc,; IL = 10mA, f = 120Hz, To = +25C RK * 70 \ | \ 1uF BYPASS CAPACITOR 60 |S 10uF BYPASS CAPACITOR 50 > petteneetesee! ee 40 NO BYPASS CAPACITOR 80 RIPPLE REJECTION (dB) 30 0 50 100 150 200 250 300 350 OUTPUT VOLTAGE (V) FIGURE 21. RIPPLE REJECTION RATIO (OUTPUT VOLTAGE) 11 | BARESHIP5600 Typical Performance Curves (continued) 85 Vin = 170Vpc, IL = 10mA, VoytT = 15V, Tc = +25C 80 | 10.F BYPASS ao CAPACITOR ZS 75 6 = 70 i > 65 Ww o w 60 a = 55 1u.F BYPASS CAPACITOR 50 NO BYPASS CAPACITOR 45 1 10 100 1k 10k 100k 1M 10M INPUT FREQUENCY (Hz) FIGURE 22. RIPPLE REJECTION RATIO (INPUT FREQUENCY) RIPPLE REJECTION (dB) 85 7 7 7 7 7 7 VIN = 170Vpc, Vout = 10mA, f = 120Hz, Te = +25C 80 (REFERENCE FIGURE 3) 7 joeeteneeseced 75 jee! ee N 70 1uF BYPASS CAPACITOR 10uF BYPASS CAPACITOR I 65 60 55 NO BYPASS CAPACITOR wl | | | 0 5 10 15 20 25 30 35 OUTPUT CURRENT (mA) FIGURE 24. RIPPLE REJECTION RATIO (OUTPUT CURRENT) OUTPUT IMPEDANCE () 100 _ C2 = 0.01 uF, C3 = OuF 10.0 LL _ C2= 10uF, C3 = OuF XN S| 1.0 C2 = 10uF, C3 = 10uF KK 0.1 Le Le | | Le l 10 100 1K 10K 100K 1M FREQUENCY (Hz) FIGURE 26. OUTPUT IMPEDANCE RIPPLE REJECTION (dB) Vin = 400Vpg, IL = 10MA, VoyT = 15V, Tc = +25C 10uF BYPASS 5 CAPACITOR 1uF BYPASS CAPACITOR NO BYPASS CAPACITOR 1 10 100 1k 10k 100k INPUT FREQUENCY (Hz) 1M 10M FIGURE 23. RIPPLE REJECTION RATIO (INPUT FREQUENCY) RIPPLE REJECTION (dB) 85 80 75 70 65 60 55 50 Vin = 400Vpc, Vout = 10mA, f = 120Hz, Tg = +25C (REFERENCE FIGURE 3) 7] ~ | oS} aN x : 1y.F BYPASS CAPACITOR 10uF BYPASS CAPACITOR NO BYPASS CAPACITOR pe 0 5 10 15 20 25 30 35 OUTPUT CURRENT (mA) FIGURE 25. RIPPLE REJECTION RATIO (OUTPUT CURRENT) IBias (HA) 520 510 500 490 480 470 460 450 440 430 420 . lout = 0 Tce =+1 00C a Tce = +25C 50 100 200 INPUT VOLTAGE (Vpc) 300 400 FIGURE 27. Ipjas vs INPUT VOLTAGE 12 | BARRISHIP5600 Typical Performance Curves (continued) | | + 100mv/DIV C3 =10uF =p f Vout H + 15V a C3 = OuF + Vv pre 4ooy HEH tetera HHH INPUT - 1OOV/DIV | VOLTAGE oe Vout = 15VpcE Ty=+25C oF T= 100ms/DIV ov | l L 1 1 1 REFERENCE VOLTAGE (V) REFERENCE VOLTAGE (V) FIGURE 28. LINE TRANSIENT RESPONSE 1.21 1.20 1.19 1.18 1.17 1.16 1.15 1.14 1.13 1.12 1.11 1.10 Vin = 50Vpc -20 0 25 40 60 CASE TEMPERATURE (C) 80 FIGURE 30. REFERENCE VOLTAGE vs TEMPERATURE 1.20 1.19 1.18 1.17 1.16 1.15 1.14 1.13 1.12 1.11 1.10 1.09 1.08 louT =10mA To = -40C To = +25C Te = +100C 0 100 200 INPUT VOLTAGE (Vpc) 300 400 FIGURE 32. REFERENCE VOLTAGE vs INPUT VOLTAGE + \ 20mvV/DIV C3 = 10uF rr b | + ~~ 6 15V v > HEE HEPAT HHS HAH HEE HH HHH - ie C3 = OuF i | x 40mA ' : 5mA/DIV 3 VIN = 400V pc = | | 5 5mA VouT=15V - , , a Ty=4+25C = T= 100ms/DIV 5 omA 1 1 1 1 1 1 FIGURE 29. LOAD TRANSIENT RESPONSE 1.25 T T Vin = 400Vpc 1imA > 1.20 ~ feettoteenensncenns / 5mA 1.15 -- z i | [i cr yA 20mA an, 4.05 4 o 30mA 1.00 -40 -20 0 25 40 60 80 REFERENCE VOLTAGE (V) CASE TEMPERATURE (C) FIGURE 31. REFERENCE VOLTAGE vs TEMPERATURE 1.08 1.06 1.04 0 100 200 INPUT VOLTAGE (Vpc) 300 400 FIGURE 33. REFERENCE VOLTAGE vs Vin; CASE TEMPERA- TURE OF +25C 13 | BARESHIP5600 Typical Performance Curves (continued) 80 1 1 80 Vin = 50Vpc Vin = 400Vpc 75 -t- 7H 1ImA A ~_ A ~~ = 7 \ a = 70 5mA 10mA E E \ Ss oc / & imA \A \ x 2 60 \ 3 60 7 0 N , 5 20mA a 30mA a qt 55-4 55 XN] 30mA 50 50 | 45 B10 20 0 25 40 60 80 -40 -20 0 25 40 60 80 100 - : CASE TEMPERATURE (C) CASE TEMPERATURE (C) FIGURE 34. lapy vs TEMPERATURE FIGURE 35. lapy vs TEMPERATURE 775 2000 Vin = 100Vpc To = 25C 770 = Tg = +25C 1500 = 765 =< MINIMUM LOAD Zz = | CURRENT a 5 4 ge 760r Fa 1000 BIAS CURRENT _| Oo a, _ 0, oc Q 755 To = +100C 3 a tn o aa, 4 500 louT 750 | laDu 745 0 ! 50 100 200 300 400 1 2 3 4 5 INPUT VOLTAGE (Vpc) Vout - Vabs (Vpc) FIGURE 36. MINIMUM LOAD CURRENT vs Vin FIGURE 37. TERMINAL CURRENTS vs FORCED Vper 55 50 45 40 35 30 OUTPUT CURRENT (mA) 25 To = +100C 20 50 100 150 200 250 300 350 INPUT-OUTPUT (Vpc) FIGURE 38. CURRENT LIMIT vs TEMPERATURE 400 14 | BARRISHIP5600 Evaluation Boards : Osa = 22C/W HEAT SINK O eS a 3 ooo &) : r @ i+ C2 e |. C1 Vin MO RF2 C3 Vout HIP5600 EVALUATION BOARD ___ 5 ~ 3.25". _+ 3.25 FIGURE 39. EVALUATION BOARD (TOP) FIGURE 40. EVALUATION BOARD METAL MASK (BOTTOM) 3.25 e e e e a e + eo @ee e e |. VIN Vout HIP5600 EVALUATION BOARD 3.25 FIGURE 41. EVALUATION BOARD METAL MASK (TOP) 15 | BARRISHIP5600 Single-In-Line Plastic Packages (SIP) | A he No oe OF Hl Y < --)_s\__ 0 c1 NOTES: 1. Lead dimension and finish uncontrolled in zone L1. 2. Position of lead to be measured 0.250 inches (6.35mm) from bot- tom of dimension D. 3. Position of lead to be measured 0.100 inches (2.54mm) from bot- tom of dimension D. 4. Controlling dimension: INCH. Z3.1B 3 LEAD PLASTIC SINGLE-IN-LINE PACKAGE INCHES MILLIMETERS SYMBOL MIN MAX MIN MAX NOTES A 0.140 0.190 3.56 4.82 - b 0.015 0.040 0.38 1.02 - b1 0.045 0.070 1.14 1.77 1 cl 0.014 0.022 0.36 0.56 1 0.560 0.650 14.23 16.51 - 0.380 0.420 9.66 10.66 - e 0.090 0.110 2.29 2.79 2 e1 0.190 0.210 4.83 5.33 F 0.020 0.055 0.51 1.39 - H1 0.230 0.270 5.85 6.85 - J 0.080 0.115 2.04 2.92 3 L 0.500 0.580 12.70 14.73 - L1 - 0.250 - 6.35 1 @P 0.139 0.161 3.53 4.08 - Q 0.100 0.135 2.54 3.43 - Rev. 1 2/95 16 | BARRES