MP1495
High Efficiency 3A, 16V, 500kHz
Synchronous Step Down Converter
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© 2012 MPS. All Rights Reserved.
The Future of Analog IC Technology
DESCRIPTION
The MP1495 is a high-frequency, synchronous,
rectified, step-down, switch-mode converter
with built-in power MOSFETs. It offers a very
compact solution to achieve a 3A continuous
output current with excellent load and line
regulation over a wide input supply range. The
MP1495 has synchronous mode operation for
higher efficiency over the output current load
range.
Current-mode operation provides fast transient
response and eases loop stabilization.
Full protection features include over-current
protection and thermal shut down.
The MP1495 requires a minimal number of
readily-available standard external components,
and is available in a space-saving 8-pin
TSOT23 package.
FEATURES
• Wide 4.5V-to-16V Operating Input Range
• 80m/30m Low RDS(ON) Internal Power
MOSFETs
• High-Efficiency Synchronous Mode
Operation
• Fixed 500kHz Switching Frequency
• Synchronizes to a 200kHz to 2MHz External
Clock
• AAM Power-Save Mode
• Internal Soft-Start
• OCP Protection and Hiccup
• Thermal Shutdown
• Output Adjustable from 0.8V
• Available in an 8-pin TSOT-23 package
APPLICATIONS
• Notebook Systems and I/O Power
• Digital Set-Top Boxes
• Flat-Panel Television and Monitors
• Distributed Power Systems
All MPS parts are lead-free and adhere to the RoHS directive. For MPS green
status, please visit MPS website under Quality Assurance. “MPS” and “Th
e
Future of Analog IC Technology” are Registered Trademarks of Monolithi
c
Power Systems, Inc.
TYPICAL APPLICATION
MP1495
IN
EN/SYNC
VCC
AAM GND
FB
SW
BSTVIN
EN/
SYNC
C3
0.1
R1
40.2k
R2
13k
R3
90.9k
R5
10k
L1
C2
47
C4
C1
4.5V-16V
3.3V/2A
22
2
6
7
1
5
R4
10
3
8
4
R9
33k
LOAD CURRENT(A)
Efficiency vs. Load Current
VIN=12V, VOUT=3.3V, AAM=0.5V
70
75
80
85
90
95
100
0.01 0.1 1 10
VIN=5V
VIN=12V
VIN=16V
MP1495 – SYNCHRONOUS STEP-DOWN CONVERTER
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ORDERING INFORMATION
Part Number* Package Top Marking
MP1495DJ TSOT-23-8 ACS
For Tape & Reel, add suffix –Z (e.g. MP1495DJ–Z);
For RoHS, compliant packaging, add suffix –LF (e.g. MP1495DJ–LF–Z).
PACKAGE REFERENCE
ABSOLUTE MAXIMUM RATINGS (1)
VIN ..................................................-0.3V to 17V
VSW ......................................................................
-0.3V (-5V for <10ns) to 17V (19V for <10ns)
VBS ......................................................... VSW+6V
All Other Pins................................ -0.3V to 6V (2)
Continuous Power Dissipation (TA = +25°C) (3)
........................................................... 1.25W
Junction Temperature...............................150°C
Lead Temperature ....................................260°C
Storage Temperature................. -65°C to 150°C
Recommended Operating Conditions (4)
Supply Voltage VIN ...........................4.5V to 16V
Output Voltage VOUT..................... 0.8V to VIN-3V
Operating Junction Temp. (TJ). -40°C to +125°C
Thermal Resistance (5) θJA θJC
TSOT-23-8............................. 100 ..... 55... °C/W
Notes:
1) Exceeding these ratings may damage the device.
2) About the details of EN pin’s ABS MAX rating, please refer to
Page 9, Enable/SYNC control section.
3) The maximum allowable power dissipation is a function of the
maximum junction temperature TJ (MAX), the junction-to-
ambient thermal resistance JA, and the ambient temperature
TA. The maximum allowable continuous power dissipation at
any ambient temperature is calculated by PD (MAX) = (TJ
(MAX)-TA)/JA. Exceeding the maximum allowable powe
r
dissipation will cause excessive die temperature, and the
regulator will go into thermal shutdown. Internal thermal
shutdown circuitry protects the device from permanent
damage.
4) The device is not guaranteed to function outside of its
operating conditions.
5) Measured on JESD51-7, 4-layer PCB.
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ELECTRICAL CHARACTERISTICS (6)
VIN = 12V, TA = 25°C, unless otherwise noted.
Parameter Symbol Condition Min Typ Max Units
Supply Current (Shutdown) IIN V
EN = 0V 1 A
Supply Current (Quiescent) Iq V
EN = 2V, VFB = 1V, AAM=0.5V 0.5 1 mA
HS Switch-ON Resistance HSRDS-ON V
BST-SW=5V 80 m
LS Switch-ON Resistance LSRDS-ON V
CC =5V 30 m
Switch Leakage SWLKG V
EN = 0V, VSW =12V 1 A
Current Limit (6) I
LIMIT Under 40% Duty Cycle 4.2 5 A
Oscillator Frequency fSW V
FB=0.75V 440 500 580 kHz
Fold-Back Frequency fFB V
FB<400mV 0.25 fSW
Maximum Duty Cycle DMAX V
FB=700mV 90 95 %
Minimum ON Time(6) t
ON_MIN 60 ns
Sync Frequency Range fSYNC 0.2 2 MHz
TA =25°C 791 807 823
Feedback Voltage VFB -40°C<TA<85°C (7) 787 807 827 mV
Feedback Current IFB V
FB=820mV 10 50 nA
EN Rising Threshold VEN_RISING 1.2 1.4 1.6 V
EN Falling Threshold VEN_FALLING 1.1 1.25 1.4 V
VEN=2V 2 A
EN Input Current IEN
VEN=0 0 A
EN Turn-Off Delay ENtd-off 8 s
VIN Under-Voltage Lockout
Threshold-Rising INUVVth 3.7 3.9 4.1 V
VIN Under-Voltage Lockout
Threshold-Hysteresis INUVHYS 650 mV
VCC Regulator VCC 5 V
VCC Load Regulation ICC=5mA 3 %
Soft-Start Period tSS 1.5 ms
Thermal Shutdown (6) 150 °C
Thermal Hysteresis (6) 20 °C
Notes:
6) Guaranteed by design.
7) Not tested in production and guaranteed by over temperature correlation.
MP1495 – SYNCHRONOUS STEP-DOWN CONVERTER
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TYPICAL PERFORMANCE CHARACTERISTICS
Performance waveforms are tested on the evaluation board of the Design Example section.
VIN = 12V, VOUT = 3.3V, AAM=0.5V, TA = 25°C, unless otherwise noted.
PEAK CURRENT(A)
INPUT VOLTAGE(V)
LOAD CURRENT(A)
Load Regulation
V
IN
=4.5V-16V, I
OUT
=0-2A
Peak Current vs. Duty
Cycle
Disabled Supply Current
vs. Input Voltage
V
IN
=6-16V, I
OUT
=0A
Line Regulation
V
IN
=5-16V
Case Temperature Rise
vs. Output Current
I
OUT
=0-3A
Enabled Supply Current
vs. Input Voltage
V
IN
=6-16V, I
OUT
=0A
OUTPUT CURRENT(A)
INPUT VOLTAGE(V)
OUTPUT CURRENT(A)INPUT VOLTAGE(V)
LOAD CURRENT(A)
INPUT CURRENT(nA)
70
75
80
85
90
95
100
0 0.5 1 1.5 2 2.5 3 70
75
80
85
90
95
100
0 0.5 1 1.5 2 2.5 3
V
IN
=5V
V
IN
=12V
V
IN
=16V
V
IN
=5V
V
IN
=16V
V
IN
=12V
-0.20
-0.15
-0.10
-0.05
0.00
0.05
0.10
0.15
0.20
0 0.5 1 1.5 2 2.5 3
V
IN
=4.5V
V
IN
=12V
V
IN
=16V
3.5
3.9
4.3
4.7
5.1
5.5
5.9
10 20 30 40 50 60 70
-1.0
-0.8
-0.6
-0.4
-0.2
0.0
0.2
0.4
0.6
0.8
1.0
46 810121416
I
OUT
=0A
I
OUT
=1.5A
I
OUT
=3A
-30
-20
-10
0
10
20
30
40
50
46 81012141618
500
505
510
515
520
525
530
535
540
4 6 8 1012141618 0
5
10
15
20
25
30
0 0.5 1 1.5 2 2.5 3
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TYPICAL PERFORMANCE CHARACTERISTICS (continued)
Performance waveforms are tested on the evaluation board of the Design Example section.
VIN = 12V, VOUT = 3.3V, AAM=0.5V, TA = 25°C, unless otherwise noted.
V
OUT
/AC
100mV/div.
I
OUT
1A/div.
V
SW
5V/div.
V
EN
5V/div.
V
OUT
2V/div.
I
-inductor
2A/div.
Start up through Input
Voltage
I
OUT
=0A
Shutdown through Input
Voltage
I
OUT
=0A
Start up through Input
Voltage
I
OUT
=3A
Shutdown through Input
Voltage
I
OUT
=3A
Startup through Enable
I
OUT
=0A
Startup through Enable
I
OUT
=3A
Shutdown through Enable
I
OUT
=3A
V
SW
5V/div.
V
EN
5V/div.
V
OUT
2V/div.
I
-inductor
2A/div.
V
SW
5V/div.
V
EN
5V/div.
V
OUT
2V/div.
I
-inductor
2A/div.
V
SW
5V/div.
V
EN
5V/div.
V
OUT
2V/div.
I
-inductor
2A/div.
V
SW
5V/div.
V
EN
5V/div.
V
OUT
2V/div.
I
-inductor
2A/div.
Shuthdown through Enable
I
OUT
=0A
V
SW
5V/div.
V
EN
5V/div.
V
OUT
2V/div.
I
-inductor
2A/div.
V
SW
5V/div.
V
EN
5V/div.
V
OUT
2V/div.
I
-inductor
2A/div.
V
SW
5V/div.
V
EN
5V/div.
V
OUT
2V/div.
I
-inductor
2A/div.
MP1495 – SYNCHRONOUS STEP-DOWN CONVERTER
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TYPICAL PERFORMANCE CHARACTERISTICS (continued)
Performance waveforms are tested on the evaluation board of the Design Example section.
VIN = 12V, VOUT = 3.3V, AAM=0.5V, TA = 25°C, unless otherwise noted.
V
IN
/AC
200mV/div.
V
OUT
/AC
20mV/div.
V
SW
10V/div.
I
-inductor
2A/div.
I
-inductor
5A/div.
Input / Output Ripple
IOUT=3A
V
SW
5V/div.
V
OUT
2V/div.
Short Circuit Entry
IOUT=0A
Short Circuit Recovery
IOUT=0A
I
-inductor
5A/div.
V
SW
5V/div.
V
OUT
2V/div.
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PIN FUNCTIONS
Package
Pin # Name Description
1 AAM
Advanced Asynchronous Modulation. Connect the tap of 2 resistor dividers to force the
MP1495 into non-synchronous mode under light loads. Drive AAM pin high (VCC) to
force the MP1495 into CCM.
2 IN
Supply Voltage. The MP1495 operates from a 4.5V to 16V input rail. Requires C1 to
decouple the input rail. Connect using a wide PCB trace.
3 SW Switch Output. Connect using a wide PCB trace.
4 GND
System Ground. This pin is the reference ground of the regulated output voltage, and
PCB layout requires special care. For best results, connect to GND with copper traces
and vias.
5 BST
Bootstrap. Requires a capacitor connected between SW and BST pins to form a floating
supply across the high-side switch driver. A 10resistor placed between SW and BST
cap is strongly recommended to reduce SW spike voltage.
6 EN/SYNC
Enable/Synchronize. EN high to enable the MP1495. Apply an external clock to the EN
pin to change the switching frequency.
7 VCC
Bias Supply. Decouple with 0.1F-to-0.22F capacitor. Select a capacitor that does not
exceed 0.22F. VCC capacitor should be put closely to VCC pin and GND pin.
8 FB
Feedback. Connect to the tap of an external resistor divider from the output to GND, to
set the output voltage. The frequency fold-back comparator lowers the oscillator
frequency when the FB voltage is below 400mV to prevent current limit runaway during a
short-circuit fault condition.
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BLOCK DIAGRAM
Figure 1: Functional Block Diagram
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OPERATION
The MP1495 is a high-frequency, synchronous,
rectified, step-down, switch-mode converter
with built-in power MOSFETs. It offers a very
compact solution to achieve 3A continuous
output current with excellent load and line
regulation over a wide input supply range.
The MP1495 operates in a fixed-frequency,
peak-current–control mode to regulate the
output voltage. An internal clock initiates a
PWM cycle. The integrated high-side power
MOSFET turns on and remains on until its
current reaches the value set by the COMP
voltage. When the power switch is off, it
remains off until the next clock cycle starts. If
the current in the power MOSFET does not
reach the current value set by COMP within
95% of one PWM period, the power MOSFET
will be forced to turn off.
Internal Regulator
The 5V internal regulator power most of the
internal circuitries. This regulator takes the VIN
input and operates in the full VIN range: When
VIN exceeds 5.0V, the output of the regulator is
in full regulation; when VIN falls below 5.0V, the
output decreases and requires a 0.1µF
decoupling ceramic capacitor.
Error Amplifier
The error amplifier compares the FB pin voltage
against the internal 0.8V reference (REF) and
outputs a COMP voltage—this COMP voltage
controls the power MOSFET current. The
optimized internal compensation network
minimizes the external component count and
simplifies the control loop design.
Enable/SYNC control
EN/Sync is a digital control pin that turns the
regulator on and off: Drive EN high to turn on
the regulator, drive it low to turn it off. An
internal 1M resistor from EN/Sync to GND
allows EN/Sync to be floated to shut down the
chip.
The EN pin is clamped internally using a 6.7V
series Zener diode, as shown in Figure 2.
Connect the EN input pin through a pullup
resistor to any voltage connected to the VIN
pin—the pullup resistor limits the EN input
current to less than 100µA.
For example, with 12V connected to VIN,
RPULLUP (12V – 6.5V) ÷ 100µA = 55k.
Connecting the EN pin is directly to a voltage
source without any pullup resistor requires
limiting voltage amplitude to ≤6V to prevent
damage to the Zener diode.
Figure 2: 6.5V-type Zener Diode
Connect an external clock with a range of
200kHz to 2MHz 2ms after output voltage is set
to synchronize the internal clock rising edge to
the external clock rising edge. The pulse width
of external clock signal should be less than
1.7s.
Under-Voltage Lockout
Under-voltage lockout (UVLO) protects the chip
from operating at an insufficient supply voltage.
The MP1495 UVLO comparator monitors the
output voltage of the internal regulator, VCC.
The UVLO rising threshold is about 3.9V while
its falling threshold is 3.25V.
Internal Soft-Start
The soft-start prevents the converter output
voltage from overshooting during startup. When
the chip starts, the internal circuitry generates a
soft-start voltage (SS) that ramps up from 0V to
1.2V. When SS is lower than REF, SS
overrides REF so the error amplifier uses SS as
the reference. When SS exceeds REF, the
error amplifier uses REF as the reference. The
SS time is internally set to 1.5ms.
Over-Current Protection and Hiccup
The MP1495 has cycle-by-cycle over current
limit for when the inductor current peak value
exceeds the set current limit threshold. If the
output voltage starts to drop until FB is below
the Under-Voltage (UV) threshold—typically
50% below the reference—the MP1495 enters
hiccup mode to periodically restart the part.
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This protection mode is especially useful when
the output is dead-shorted to ground. The
average short-circuit current is greatly reduced
to alleviate the thermal issue and to protect the
regulator. The MP1495 exits the hiccup mode
once the over-current condition is removed.
Thermal Shutdown
Thermal shutdown prevents the chip from
operating at exceedingly high temperatures.
When the silicon die temperature exceeds
150°C, it shuts down the whole chip. When the
temperature drops below its lower threshold
(typically 130°C) the chip is enabled again.
Floating Driver and Bootstrap Charging
An external bootstrap capacitor powers the
floating power MOSFET driver. This floating
driver has its own UVLO protection, with a
rising threshold of 2.2V and hysteresis of
150mV. The bootstrap capacitor voltage is
regulated internally by VIN through D1, M1, C4,
L1 and C2 (Figure 3). If (VIN-VSW) exceeds 5V,
U1 regulates M1 to maintain a 5V BST voltage
across C4. A 10 resistor placed between SW and
BST cap is strongly recommended to reduce SW
spike voltage.
Figure 3: Internal Bootstrap Charging Circuit,
Startup and Shutdown
If both VIN and EN exceed their appropriate
thresholds, the chip starts: The reference block
starts first, generating stable reference voltage
and currents, and then the internal regulator is
enabled. The regulator provides stable supply
for the remaining circuitries.
Three events can shut down the chip: EN low,
VIN low, and thermal shutdown. In the shutdown
procedure, the signaling path is first blocked to
avoid any fault triggering. The COMP voltage
and the internal supply rail are then pulled down.
The floating driver is not subject to this
shutdown command.
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APPLICATION INFORMATION
Setting the Output Voltage
The external resistor divider sets the output
voltage. The feedback resistor R1 also sets the
feedback loop bandwidth with the internal
compensation capacitor (see Typical Application
on page 1). Choose R1 around 40k, then R2 is:
OUT
R1
R2 V1
0.807V
=
−
Use the T-type network when VOUT is low, as
shown in Figure 4.
FB 8RT
R2
R1
VOUT
Figure 4: T-Type Network
Table 1 lists the recommended T-type resistor
value for common output voltages.
Table 1: Resistor Selection for Common Output
Voltages
VOUT (V) R1 (kΩ) R2 (kΩ) Rt (kΩ)
1.0 20.5(1%) 82(1%) 82(1%)
1.2 30.1(1%) 60.4(1%) 82(1%)
1.8 40.2(1%) 32.4(1%) 56(1%)
2.5 40.2(1%) 19.1(1%) 33(1%)
3.3 40.2(1%) 13(1%) 33(1%)
5 40.2(1%) 7.68(1%) 33(1%)
Selecting the Inductor
For most applications, use a 1µH-to-10µH
inductor with a DC current rating that is at least
25% percent higher than the maximum load
current. Select an inductor with a DC resistance
less than 15m for highest efficiency. For most
designs, the inductance value can be derived
from the following equation.
OUT IN OUT
1
IN L OSC
V(VV)
LVIf
×−
=×Δ ×
Where IL is the inductor ripple current.
Choose an inductor ripple current to be
approximately 30% of the maximum load current.
The maximum inductor peak current is:
2
I
II L
LOAD)MAX(L
Δ
+=
Use a larger inductor for light-load conditions
(below 100mA) for improved efficiency.
Setting the AAM Voltage
The AAM voltage sets the transition point from
AAM to CCM. Select a voltage that balances
efficiency, stability, ripple, and transient: A
relatively low AAM voltage improves stability and
ripple, but degrades transient and efficiency
during AAM mode; a relatively high AAM voltage
improves the transient and efficiency during AAM,
but degrades stability and ripple.
AAM voltage is set from the tap of a resistor
divider from the VCC (5V) pin, as shown in Figure
5.
R3
AAM
VCC(5V)
R4
Figure 5: AAM Network
Generally, choose R4 to be around 10k, then
R3 is:
⎟
⎠
⎞
⎜
⎝
⎛−= 1
AAM
VCC
R4R3
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AAM(V)
0.1
0.2
0.3
0.4
0.5
0.6
0.7
0.8
024681012
VOUT=1.05V
VOUT=1.8V
VOUT=2.5V
VOUT=5V
VOUT=3.3V
Figure 6: AAM Selection for Common Output
Voltages (VIN=4.5V to 16V)
Selecting the Input Capacitor
The input current to the step-down converter is
discontinuous and therefore requires a capacitor to
supply the AC current to the step-down converter
while maintaining the DC input voltage. Use low-ESR
capacitors for the best performance. For best results,
use ceramic capacitors with X5R or X7R
dielectrics because of their low ESR and small
temperature coefficients. Use a 22µF capacitor
for most applications.
C1 requires an adequate ripple current rating since it
absorbs the input switching current. Estimate the
RMS current in the input capacitor with:
⎟
⎟
⎠
⎞
⎜
⎜
⎝
⎛
×−×=
IN
OUT
IN
OUT
LOAD1C V
V
1
V
V
II
The worst case condition occurs at VIN = 2VOUT,
where:
2
I
ILOAD
1C =
For simplification, choose an input capacitor
whose RMS current rating greater than half of the
maximum load current.
The input capacitor can be electrolytic, tantalum
or ceramic. When using electrolytic or tantalum
capacitors, place a small, high-quality ceramic
capacitor (e.g. 0.1F) as close to the IC as
possible. When using ceramic capacitors, make
sure that they have enough capacitance to
provide sufficient charge to prevent excessive
voltage ripple at the input. The input voltage
ripple caused by capacitance can be estimated
by:
LOAD OUT OUT
IN IN
SIN
IV V
V1
fC1V V
⎛⎞
Δ= × ×−
⎜⎟
×⎝⎠
Selecting the Output Capacitor
The output capacitor (C2) maintains the DC
output voltage. Use ceramic, tantalum, or low-
ESR electrolytic capacitors. For best results, use
low-ESR capacitors to keep the output voltage
ripple low. The output voltage ripple can be
estimated by:
OUT OUT
OUT ESR
S1 IN S
VV 1
V1R
fL V 8fC2
⎛⎞
⎛⎞
Δ= ×− × +
⎜⎟
⎜⎟
×××
⎝⎠
⎝⎠
Where L1 is the inductor value and RESR is the
equivalent series resistance (ESR) value of the
output capacitor.
For ceramic capacitors, the capacitance
dominates the impedance at the switching
frequency, and thus causes the majority of the
output voltage ripple. For simplification, the
output voltage ripple can be estimated by:
OUT OUT
OUT 2
IN
S1
VV
V1
V
8f L C2
⎛⎞
=×−
⎜⎟
××× ⎝⎠
For tantalum or electrolytic capacitors, the ESR
dominates the impedance at the switching
frequency. For simplification, the output ripple
can be approximated to:
OUT OUT
OUT ESR
IN
S1
VV
V1R
fL V
⎛⎞
=×−×
⎜⎟
×⎝⎠
The characteristics of the output capacitor also
affect the stability of the regulation system. The
MP1495 can be optimized for a wide range of
capacitance and ESR values.
MP1495 – SYNCHRONOUS STEP-DOWN CONVERTER
MP1495 Rev. 1.04 www.MonolithicPower.com 13
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External Bootstrap Diode
An external bootstrap diode may enhance the
regulator efficiency under the following
conditions:
z VOUT is 5V or 3.3V; and
z Duty cycle is high: D=
IN
OUT
V
V>65%
Connect the BST diode from the VCC pin to the
BST pin, as shown in Figure 7.
SW
BST
MP1495 C
L
BST
COUT
External BST Diode
VCC
IN4148
Figure 7: Optional External Bootstrap Diode for
Enhanced Efficiency
The recommended external BST diode is
IN4148, and the BST capacitor is 0.1 µF to 1F.
PC Board Layout (8)
PCB layout is very important to achieve stable
operation especially for VCC capacitor and
input capacitor placement. For best results,
follow these guidelines:
1) Use large ground plane directly connect to
GND pin. Add vias near the GND pin if bottom
layer is ground plane.
2) Place the VCC capacitor to VCC pin and
GND pin as close as possible. Make the trace
length of VCC pin-VCC capacitor anode-VCC
capacitor cathode-chip GND pin as short as
possible.
3) Place the ceramic input capacitor close to IN
and GND pins. Keep the connection of input
capacitor and IN pin as short and wide as
possible.
4) Route SW, BST away from sensitive analog
areas such as FB. It’s not recommended to
route SW, BST trace under chip’s bottom side.
5) Place the T-type feedback resistor R9 close
to chip to ensure the trace which connects to
FB pin as short as possible
Notes:
8) The recommended layout is based on the Figure 8 Typical
Application circuit on the next page.
8
7
6
5
L1
C2
C2A
C1
C1A
R5R6
R7
R9
R8
R1
R2
R3
R4
C3
C4
C5
C6
1
2
3
4
Vin
GND
Vout
SW
GND
GND
SW
GND
EN/SYNC BST
VCC
MP1495 – SYNCHRONOUS STEP-DOWN CONVERTER
MP1495 Rev. 1.04 www.MonolithicPower.com 14
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TYPICAL APPLICATION CIRCUITS
MP1495
C1A
NS
IN
2
7
1
5
3
8
6
4
VCC
AAM
EN/SYNC
GND
FB
SW
BST
U1
R7
90.9k
R2
13k
R1
40.2k R3
0
C3
15pF
3.3V
R4
10
R9
33k
R5
28.7k
R6
11k
R8
10k
C5
1nF
Figure 8: 12VIN, 3.3V/3A
MP1495 – SYNCHRONOUS STEP-DOWN CONVERTER
NOTICE: The information in this document is subject to change without notice. Users should warrant and guarantee that third
party Intellectual Property rights are not infringed upon when integrating MPS products into any application. MPS will not
assume any legal responsibility for any said applications.
MP1495 Rev. 1.04 www.MonolithicPower.com 15
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© 2012 MPS. All Rights Reserved.
PACKAGE INFORMATION
TSOT23-8
