TPS61006DGSRG4 - Texas Instruments

TPS61000, TPS61001, TPS61002, TPS61003, TPS61004, TPS61005, TPS61006, TPS61007

SINGLE- AND DUAL-CELL BOOST CONVERTER WITH START-UP INTO FULL LOAD

SLVS279C – MARCH 2000 – REVISED APRIL 2003

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

DStart-Up Into a Full Load With Supply

Voltages as Low as 0.9 V Over Full

Temperature Range

DMinimum 100-mA Output Current From

0.8-V Supply Voltage, 250 mA From 1.8 V

DHigh Power Conversion Efficiency,

up to 90%

DPower-Save Mode for Improved Efficiency

at Low Output Currents

DDevice Quiescent Current Less Than 50 µA

DAdded System Security With Integrated

Low-Battery Comparator

DLow-EMI Converter (Integrated Antiringing

Switch Across Inductor)

DMicro-Size 10-Pin MSOP Package

DEvaluation Modules Available

(TPS6100xEVM–156)

DApplications Include:

– Single- and Dual-Cell Battery Operated

Products

– MP3-Players and Wireless Headsets

– Pagers and Cordless Phones

– Portable Medical Diagnostic Equipment

– Remote Controls

description

The TPS6100x devices are boost converters intended for systems that are typically operated from a single- or

dual-cell nickel-cadmium (NiCd), nickel-metal hydride (NiMH), or alkaline battery . The converter output voltage

can be adjusted from 1.5 V to a maximum of 3.3 V and provides a minimum output current of 100 mA from a

single battery cell and 250 mA from two battery cells. The converter starts up into a full load with a supply voltage

of 0.9 V and stays in operation with supply voltages as low as 0.8 V.

The converter is based on a fixed-frequency , current-mode pulse-width-modulation (PWM) controller that goes

into power-save mode at low load currents. The current through the switch is limited to a maximum of 1 100 mA,

depending on the output voltage. The current sense is integrated to further minimize external component count.

The converter can be disabled to minimize battery drain when the system is put into standby.

A low-EMI mode is implemented to reduce interference and radiated electromagnetic energy that is caused by

the ringing of the inductor when the inductor discharge-current decreases to zero. The device is packaged in

the space-saving 10-pin MSOP package.

TPS61006

VBAT

LBI

VOUT

LBO

COMP

GND

Low Battery

Warning

10 kΩ

OFF

10 µF

L1 D1 VO = 3.3 V

100 pF

33 nF

22 µF

33 µH

024681012

TPS61006

START-UP TIMING INTO 33-Ω LOAD

14 16 18 20

– Output Voltage – V

VOUT

IOUT 80

100

120

140

– Output Current – mAIO

Time – ms

TYPICAL APPLICATION CIRCUIT FOR FIXED

OUTPUT VOLTAGE OPTION

Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of

Texas Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet.

PRODUCTION DATA information is current as of publication date.

Products conform to specifications per the terms of Texas Instruments

standard warranty. Production processing does not necessarily include

testing of all parameters.

TPS61000, TPS61001, TPS61002, TPS61003, TPS61004, TPS61005, TPS61006, TPS61007

SINGLE- AND DUAL-CELL BOOST CONVERTER WITH START-UP INTO FULL LOAD

SLVS279C – MARCH 2000 – REVISED APRIL 2003

2POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

AVAILABLE OPTIONS

TAPACKAGE OUTPUT VOLTAGE

(V) PART NUMBER†MARKING DGS

PACKAGE

Adj. from 1.5 V to 3.3 V TPS61000DGS ADA

1.5 TPS61001DGS ADB

1.8 TPS61002DGS ADC

40°Cto85°C

10 Pin MSOP DGS

2.5 TPS61003DGS ADD

–40°C to 85°C10-Pin MSOP DGS 2.8 TPS61004DGS ADE

3.0 TPS61005DGS ADF

3.3 TPS61006DGS ADG

Adj. from 1.5 V to 3.3 V TPS61007DGS ADH

†The DGS package is available taped and reeled. Add R suffix to device type (e.g. TPS61000DGSR) to order quantities of

2500 devices per reel.

Terminal Functions

TERMINAL

I/O

DESCRIPTION

NAME NO. I/O DESCRIPTION

COMP 2 Compensation of error amplifier. Connect R-C-C network to set frequency response of control loop. See the

Application section for more details.

EN 1 I Chip-enable input. The converter is switched on if EN is set high, and is switched off when EN is connected to

ground (shutdown mode).

FB 3 I Feedback input for adjustable output voltage (TPS61000 only). The output voltage is programmed depending on

the values of resistors R1 and R2. For the fixed output voltage versions (TPS61000, TPS61002, TPS61003,

TPS61004, TPS61005, TPS61006), leave the FB pin unconnected.

NC/FBGND 8 Not connected (TPS61000, TPS61002, TPS61003, TPS61004, TPS61005, TPS61006). A ground pin for the

feedback resistor divider for the TPS61007 only.

GND 4 Ground

LBI 9 I Low-battery detector input. A low-battery signal is generated at the LBO pin when the voltage on LBI drops below

the threshold of 500 mV . Connect LBI to GND or VBAT if the low-battery detector function is not used. Do not leave

this pin floating.

LBO 10 O Open-drain low-battery detector output. This pin is pulled low if the voltage on LBI drops below the threshold of

500 mV. A pullup resistor should be connected between LBO and VOUT.

SW 7 I Switch input pin. The node between inductor and anode of the rectifier diode is connected to this pin.

VBAT 6 I Supply pin

VOUT 5 O Output voltage. For the fixed output voltage versions, the integrated resistive divider is connected to this pin.

COMP

GND

VOUT

LBO

LBI

NC/FBGND‡

VBAT

DGS PACKAGE

(TOP VIEW)

‡TPS61007 only

TPS61000, TPS61001, TPS61002, TPS61003, TPS61004, TPS61005, TPS61006, TPS61007

SINGLE- AND DUAL-CELL BOOST CONVERTER WITH START-UP INTO FULL LOAD

SLVS279C – MARCH 2000 – REVISED APRIL 2003

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

functional block diagram

fixed output-voltage option

VREF

VBAT

Control Logic

Oscillator

Gate Drive

UVLO Current Sense

Current Limit

Slope Compensation

Bandgap

Reference

LBI

LBO

GND COMP

L1 D1

VOUT CO

CISW

Comparator

LBI/LBO

Comparator

Error

Amplifier

Antiringing

Comparator

and Switch

adjustable output-voltage option (TPS61000 only)

VREF

VBAT

Control Logic

Oscillator

Gate Drive

UVLO Current Sense

Current Limit

Slope Compensation

Bandgap

Reference

LBI

LBO

GND COMP

L1 D1

VOUT

CISW

Comparator

LBI/LBO

Comparator

Error

Amplifier

Antiringing

Comparator

and Switch

TPS61000, TPS61001, TPS61002, TPS61003, TPS61004, TPS61005, TPS61006, TPS61007

SINGLE- AND DUAL-CELL BOOST CONVERTER WITH START-UP INTO FULL LOAD

SLVS279C – MARCH 2000 – REVISED APRIL 2003

4POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

functional block diagram (continued)

adjustable output-voltage option (TPS61007 only)

VREF

VBAT

Control Logic

Oscillator

Gate Drive

UVLO Current Sense

Current Limit

Slope Compensation

Bandgap

Reference

LBI

LBO

GND COMP

L1 D1

VOUT

CISW

Comparator

LBI/LBO

Comparator

Error

Amplifier

Antiringing

Comparator

and Switch

FBGND

detailed description

controller circuit

The device is based on a current-mode control topology using a constant-frequency pulse-width modulator to

regulate the output voltage. It runs at an oscillator frequency of 500 kHz. The current sense is implemented by

measuring the voltage across the switch. The controller also limits the current through the power switch on a

pulse-by-pulse basis. Care must be taken that the inductor saturation current is higher than the current limit of

the TPS6100x. This prevents the inductor from going into saturation and therefore protects both device and

inductor. The current limit should not become active during normal operating conditions.

The TPS6100x is designed for high efficiency over a wide output current range. Even at light loads the efficiency

stays high because the controller enters a power-save mode, minimizing switching losses of the converter. In

this mode, the controller only switches if the output voltage trips below a set threshold voltage. It ramps up the

output voltage with one or several pulses, and again goes into the power-save mode once the output voltage

exceeds the threshold voltage. The controller enters the power-save mode when the output current drops to

levels that force the discontinuous current mode. It calculates a minimum duty cycle based on input and output

voltage and uses the calculation for the transition out of the power-save mode into continuous current mode.

The control loop must be externally compensated with an R/C/C network connected to the COMP pin. See the

application section for more details on the design of the compensation network.

device enable

The device is put into operation when EN is set high. During start-up of the converter the input current from the

battery is limited until the voltage on COMP reaches its operating point. The device is put into a shutdown mode

when EN is set to GND. In this mode, the regulator stops switching and all internal control circuitry including

the low-battery comparator is switched off. The output voltage drops to one diode drop below the input voltage

in shutdown.

TPS61000, TPS61001, TPS61002, TPS61003, TPS61004, TPS61005, TPS61006, TPS61007

SINGLE- AND DUAL-CELL BOOST CONVERTER WITH START-UP INTO FULL LOAD

SLVS279C – MARCH 2000 – REVISED APRIL 2003

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

detailed description (continued)

under-voltage lockout

An under-voltage lockout function prevents the device start-up if the supply voltage on VBAT is lower than

approximately 0.7 V. This undervoltage lockout function is implemented in order to prevent the malfunctioning

of the converter. When in operation and the battery is being discharged, the device automatically enters the

shutdown mode if the voltage on VBAT drops below approximately 0.7 V.

If the EN pin is hardwired to VBAT and if the voltage at VBAT drops temporarily below the UVLO threshold voltage,

the device switches off and does not start up again automatically, even if the supply voltage rises above 0.9 V.

The device starts up again only after a signal change from low to high on EN or if the battery voltage is completely

removed.

low Battery detector circuit (LBI and LBO)

The low-battery detector circuit is typically used to supervise the battery voltage and to generate an error flag

when the battery voltage drops below a user-set threshold voltage. The function is active only when the device

is enabled. When the device is disabled, the LBO pin is high impedance. The LBO pin goes active low when

the voltage on the LBI pin decreases below the set threshold voltage of 500 mV ±15 mV, which is equal to the

internal reference voltage. The battery voltage, at which the detection circuit switches, can be programmed with

a resistive divider connected to the LBI pin. The resistive divider scales down the battery voltage to a voltage

level of 500 mV, which is then compared to the LBI threshold voltage. The LBI pin has a built-in hysteresis of

10 mV. See the application section for more details about the programming of the LBI threshold.

If the low-battery detection circuit is not used, the LBI pin should be connected to GND (or to VBAT) and the LBO

pin can be left unconnected. Do not let the LBI pin float.

low-EMI switch

The device integrates a circuit which removes the ringing that typically appears on the SW-node when the con-

verter enters the discontinuous current mode. In this case, the current through the inductor ramps to zero and

the Schottky diode stops conducting. Due to remaining energy that is stored in parasitic components of the

diode, inductor, and switch, a ringing on the SW pin is induced. The integrated antiringing switch clamps this

voltage internally to VBAT and therefore dampens this ringing.

The antiringing switch is turned on by a comparator that monitors the voltage between SW and VOUT. This

voltage indicates when the diode is reverse biased. The ringing on the SW-node is damped to a large degree,

reducing the electromagnetic interference generated by the switching regulator to a very great extent.

adjustable output voltage (TPS61000 and TPS61007 only)

The accuracy of the internal voltage reference, the controller topology , and the accuracy of the external resistor

divider determine the accuracy of the adjustable output voltage versions. The reference voltage has an

accuracy of ±4% over line, load, and temperature. The controller switches between fixed frequency and

pulse-skip mode, depending on load current. This adds an offset to the output voltage that is equivalent to 1%

of VO. Using 1% accurate resistors for the feedback divider , a total accuracy of ±6% can be achieved over the

complete temperature and output current range. The TPS61007 is an improved adjustable output voltage

version. Ground shift in the feedback loop was eliminated by adding a separate ground pin for the feedback

resistor divider (FBGND).

TPS61000, TPS61001, TPS61002, TPS61003, TPS61004, TPS61005, TPS61006, TPS61007

SINGLE- AND DUAL-CELL BOOST CONVERTER WITH START-UP INTO FULL LOAD

SLVS279C – MARCH 2000 – REVISED APRIL 2003

6POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

absolute maximum ratings†

Input voltage range, VI (VBAT, VOUT, COMP, FB, LBO, EN, LBI) –0.3 V to 3.6 V. . . . . . . . . . . . . . . . . . . . . . . . .

Input voltage, VI (SW) –0.3 V to VOUT +0.7 V. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .

Peak current into SW 1300 mA. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .

Continuous total power dissipation See dissipation rating table. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .

Operating free-air temperature range, TA–40°C to 85°C. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .

Maximum junction temperature, TJ150°C. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .

Storage temperature range, Tstg –65°C to 150°C. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .

Lead temperature 260°C. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .

†Stresses beyond those listed under “absolute maximum ratings” may cause permanent damage to the device. These are stress ratings only , and

functional operation of the device at these or any other conditions beyond those indicated under “recommended operating conditions” is not

implied. Exposure to absolute-maximum-rated conditions for extended periods may af fect device reliability.

DISSIPATION RATING TABLE

PACKAGE TA ≤ 25_C

POWER RATING DERATING FACTOR

ABOVE TA = 25_CTA = 70_C

POWER RATING TA = 85_C

POWER RATING

DGS 424 mW 3.4 mW/_C271 mW 220 mW

recommended operating conditions

MIN NOM MAX UNIT

Supply voltage at VBAT 0.8 VOV

Output current

VBAT = 0.8 V 100

Output current VBAT = 1.8 V 250 mA

Inductor 10 33 µH

Input capacitor 10 µF

Output capacitor 22 µF

Operating junction temperature, TJ–40 125 °C

TPS61000, TPS61001, TPS61002, TPS61003, TPS61004, TPS61005, TPS61006, TPS61007

SINGLE- AND DUAL-CELL BOOST CONVERTER WITH START-UP INTO FULL LOAD

SLVS279C – MARCH 2000 – REVISED APRIL 2003

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

electrical characteristics over recommended operating free-air temperature range, VBAT = 1.2 V, EN

= VBAT (unless otherwise noted)

PARAMETER TEST CONDITIONS MIN TYP MAX UNIT

Input voltage for start up

RL = 33 Ω0.9

VIInput voltage for start-up RL = 3 kΩ,TA = 25°C 0.8 V

VIInput voltage once started IO = 100 mA 0.8 V

VOProgrammable output voltage TPS61000,

TPS61007 IO = 100 mA 1.5 3.3 V

TPS61001

1.2 V, IO = 1 mA 1.44 1.5 1.55

TPS61001 0.8 V < VI < VO, IO = 100 mA 1.45 1.5 1.55

TPS61002

1.2 V, IO = 1 mA 1.72 1.8 1.86

TPS61002 0.8 V < VI < VO, IO = 100 mA 1.74 1.8 1.86

1.2 V, IO = 1 mA 2.40 2.5 2.58

TPS61003 0.8 V < VI < VO, IO = 100 mA 2.42 2.5 2.58

TPS61003

1.6 V < VI < VO, IO = 200 mA 2.42 2.5 2.58

Output voltage

1.2 V, IO = 1 mA 2.68 2.8 2.89

VOOutput voltage TPS61004 0.8 V < VI < VO, IO = 100 mA 2.72 2.8 2.89 V

TPS61004

1.6 V < VI < VO, IO = 200 mA 2.72 2.8 2.89

1.2 V, IO = 1 mA 2.88 3.0 3.1

TPS61005 0.8 V < VI < VO, IO = 100 mA 2.9 3.0 3.1

TPS61005

1.6 V < VI < VO, IO = 200 mA 2.9 3.0 3.1

1.2 V, IO = 1 mA 3.16 3.3 3.4

TPS61006 0.8 V < VI < VO, IO = 100 mA 3.2 3.3 3.4

TPS61006

1.6 V < VI < VO, IO = 200 mA 3.2 3.3 3.4

Maximum continuous output current

VI = 0.8 V 100

IOMaximum continuous output current VI = 1.8 V 250 mA

TPS61001 0.5

TPS61002 0.65

Switch current limit

TPS61003

08V V V

0.9

ILIM Switch current limit TPS61004 0.8 V < VI < VO0.95 A

TPS61005 1

TPS61006 1.1

VFB Feedback voltage TPS61000,

TPS61007 468 500 515 mV

fOscillator frequency 360 500 840 kHz

DMAX Maximum duty cycle 85%

rDS(on) Switch-on resistance VO = 3.3 V 0.18 0.27 Ω

Line regulation (see Note 1) VI = 0.8 V to 1.25 V, IO = 50 mA 0.3 %/V

Load regulation fixed output voltage versions

(see Note 1) VI = 1.2 V, IO = 10 mA to 90 mA 0.25%

NOTE 1: Line and load regulation is measured as a percentage deviation from the nominal value (i.e., as percentage deviation from the nominal

output voltage). For line regulation, x %/V stands for ±x% change of the nominal output voltage per 1-V change on the input/supply

voltage. For load regulation, y% stands for ±y% change of the nominal output voltage per the specified current change.

TPS61000, TPS61001, TPS61002, TPS61003, TPS61004, TPS61005, TPS61006, TPS61007

SINGLE- AND DUAL-CELL BOOST CONVERTER WITH START-UP INTO FULL LOAD

SLVS279C – MARCH 2000 – REVISED APRIL 2003

8POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

electrical characteristics over recommended operating free-air temperature range, VBAT = 1.2 V, EN

= VBAT (unless otherwise noted) (continued)

PARAMETER TEST CONDITIONS MIN TYP MAX UNIT

Quiescent current drawn from power source IO = 0 mA, VEN = VI

VBAT 44

Quiescent

current

drawn

from

ower

source

(current into VBAT and into VOUT)

mA,

VEN

VO = 3.4 V VOUT 6µA

ISD Shutdown current from power source

(current into VBAT and into VOUT)VEN = 0 V 0.2 5 µA

VIL EN low-level input voltage 0.2 ×

VBAT V

VIH EN high-level input voltage 0.8 ×

VBAT V

EN input current EN = GND or VBAT 0.1 1 µA

VIL LBI low-level input voltage threshold VLBI voltage decreasing 470 500 530 mV

LBI input hysteresis 10 mV

IILBI input current 0.01 0.1 µA

VOL LBO low-level output voltage VLBI = 0 V, VO = 3.3 V, IOL = 50 µA 0.04 0.2 V

LBO output leakage current VLBI = 650 mV, VLBO = 3.3 V 0.01 1 µA

IFB FB input bias current (TPS61000, TPS61007 only) VFB = 500 mV 0.01 0.1 µA

PARAMETER MEASUREMENT INFORMATION

List of Components:

IC1: Only fixed output versions

(unless otherwise noted)

L1: Coilcraft DO3308P–333

D1: Motorola Schottky Diode

MBRM120LT3

CI: Ceramic

CO:Ceramic

TPS6100x

VBAT

LBI

NC/FBGND

VOUT

LBO

COMP

GND

Low Battery

Warning

10 kΩ

OFF

10 µF

L1 D1

100 pF C2

33 nF

22 µF

33 µH

Figure 1. Circuit Used for Typical Characteristics Measurements

TPS61000, TPS61001, TPS61002, TPS61003, TPS61004, TPS61005, TPS61006, TPS61007

SINGLE- AND DUAL-CELL BOOST CONVERTER WITH START-UP INTO FULL LOAD

SLVS279C – MARCH 2000 – REVISED APRIL 2003

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

TYPICAL CHARACTERISTICS

Table of Graphs

FIGURE

vs Output Current 2, 3

ηEfficiency vs Inductor Type 4

Efficiency

vs Input Voltage 5

IOMaximum Output Current vs Input Voltage 6

VOOutput Voltage vs Output Current 7

VOTPS61007 Output Voltage vs Output Current 8

IQNo-Load Supply Current vs Input Voltage 9

ISD Shutdown Current vs Input V oltage 10

VIMinimum Start-Up Input Voltage vs Load Current 11

ILIM Switch Current Limit vs Output Voltage 12

Output V oltage Ripple Amplitude 13

Output V oltage Ripple Amplitude 14

Load T ransient Response 15

Line T ransient Response 16

Start-Up T iming 17

Figure 2

0110

Efficiency – %

EFFICIENCY

OUTPUT CURRENT

100

VO = 3.3 V VO = 1.5 V

VI = 1.2 V

IO – Output Current – mA 1000

Figure 3

100

1 10 100 1000

VO = 3.3 V

VO = 2.8 V

VI = 2.4 V

Efficiency – %

EFFICIENCY

OUTPUT CURRENT

IO – Output Current – mA

TPS61000, TPS61001, TPS61002, TPS61003, TPS61004, TPS61005, TPS61006, TPS61007

SINGLE- AND DUAL-CELL BOOST CONVERTER WITH START-UP INTO FULL LOAD

SLVS279C – MARCH 2000 – REVISED APRIL 2003

10 POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

TYPICAL CHARACTERISTICS

100

Coilcraft

DO1608C Coilcraft

DS1608C Coiltronics

UP1B Coiltronics

UP2B Sumida

CD43 Sumida

CD54

Efficiency – %

EFFICIENCY

INDUCTOR TYPE

Inductor Type

VI = 1.2 V

VO = 3.3 V

IO = 100 mA

Figure 4

0.80 1.30 1.80 2.30 2.80 3.30

Efficiency – %

EFFICIENCY

INPUT VOLTAGE

VI – Input Voltage – V

IO = 50 mA

IO = 100 mA

Figure 5

0.10

0.20

0.30

0.40

0.50

0.60

0.70

0.80

0.90

0.8 1 1.2 1.4 1.6 1.8 2 2.2 2.4 2.6 2.8 3

– Maximum Output Current –

MAXIMUM OUTPUT CURRENT

INPUT VOLTAGE

VI – Input Voltage – V

VO = 1.45 V

VO = 1.75 V

Figure 6

VO = 2.42 V

VO = 3.2 V

TPS61000, TPS61001, TPS61002, TPS61003, TPS61004, TPS61005, TPS61006, TPS61007

SINGLE- AND DUAL-CELL BOOST CONVERTER WITH START-UP INTO FULL LOAD

SLVS279C – MARCH 2000 – REVISED APRIL 2003

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

TYPICAL CHARACTERISTICS

1.60

1.80

2.00

2.40

2.60

2.80

3.20

3.40

3.60

1 10 100 1000

VI = 1.2 V

3.3 V

2.5 V

1.8 V

– Output Voltage – V

TPS61002/3/6

OUTPUT VOLTAGE

OUTPUT CURRENT

IO – Output Current – mA

Figure 7 Figure 8

1.60

1.80

2.20

2.40

2.60

2.80

3.20

3.40

3.60

0.1 1 10 100 1000

VO = 3.3 V

– Output Voltage – V

TPS61007

OUTPUT VOLTAGE

OUTPUT CURRENT

IO – Output Current – mA

VO = 2.5 V

VO = 1.8 V

VI = 1.2 V

Figure 9

0.80 1.30 1.80 2.30 2.80 3.30 3.80

TA = 85°C

TA = 25°C

TA = –40°C

– No-Load Supply Current –

NO-LOAD SUPPLY CURRENT

INPUT VOLTAGE

Aµ

VI – Input Voltage – V

Figure 10

200

400

600

800

1000

1200

1400

1600

1800

0.80 1.30 1.80 2.30 2.80 3.30 3.80

– Shutdown Current – nA

SHUTDOWN CURRENT

INPUT VOLTAGE

VI – Input Voltage – V

TA = 85°C

TA = 25°C

TA = –40°C

ISD

TPS61000, TPS61001, TPS61002, TPS61003, TPS61004, TPS61005, TPS61006, TPS61007

SINGLE- AND DUAL-CELL BOOST CONVERTER WITH START-UP INTO FULL LOAD

SLVS279C – MARCH 2000 – REVISED APRIL 2003

12 POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

TYPICAL CHARACTERISTICS

Figure 11

0.60

0.65

0.70

0.75

0.80

0.85

0.90

01020 100

VO = min 3.2 V

– Minimum Start-Up Input Voltage – V

MINIMUM START-UP INPUT VOLTAGE

LOAD CURRENT

IO – Load Current – mA

30 40 50 60 70 80 90

Figure 12

0.5

1.5

1.5 1.7 1.9 2.1 2.3 2.5 2.7 2.9 3.1 3.3 3.5

VI = 1.2 V

– Switch Current Limit – A

TPS61000, TPS61007

SWITCH CURRENT LIMIT

OUTPUT VOLTAGE

VO – Output Voltage – V

ILIM

Figure 13

3.28

3.26

3.22

3.18

3.30

3.32

TPS61006

OUTPUT VOLTAGE RIPPLE AMPLITUDE

3.34

3.24

3.20

IO = 2 mA

Time – ms

– Output Voltage – VVO

01 5432

Figure 14

3.30

0123

3.32

3.34

3.36

TPS61006

OUTPUT VOLTAGE RIPPLE AMPLITUDE

Time – µs

VI = 1.2 V

– Output Voltage – V

VSW

VOUT

VSW

TPS61000, TPS61001, TPS61002, TPS61003, TPS61004, TPS61005, TPS61006, TPS61007

SINGLE- AND DUAL-CELL BOOST CONVERTER WITH START-UP INTO FULL LOAD

SLVS279C – MARCH 2000 – REVISED APRIL 2003

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

TYPICAL CHARACTERISTICS

Figure 15

3.2

00123456

3.3

3.4

TPS61006

LOAD TRANSIENT RESPONSE

78910

– Output Voltage – V

VI = 1.2 V

RC = 33 kΩ

50 mA

5 mA

– Output Current – mA

Time – ms

Figure 16

3.25

1.2

0123456

3.35

3.45

TPS61006

LINE TRANSIENT RESPONSE

3.55

78910

0.8

– Output Voltage – V

– Input Voltage – V

VOUT

VBAT

Time – ms

IO = 50 mA

RC = 33 kΩ

024681012

TPS61006

START-UP TIMING INTO 33-Ω LOAD

14 16 18 20

– Output Voltage – V

VOUT

IOUT 80

100

120

140

– Output Current – mA

Time – ms

Figure 17

TPS61000, TPS61001, TPS61002, TPS61003, TPS61004, TPS61005, TPS61006, TPS61007

SINGLE- AND DUAL-CELL BOOST CONVERTER WITH START-UP INTO FULL LOAD

SLVS279C – MARCH 2000 – REVISED APRIL 2003

14 POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

APPLICATION INFORMATION

The TPS6100x boost converter family is intended for systems that are powered by a single-cell NiCd or NiMH

battery with a typical terminal voltage between 0.9 V to 1.6 V. It can also be used in systems that are powered

by two-cell NiCd or NiMH batteries with a typical stack voltage between 1.8 V and 3.2 V. Additionally, single-

or dual-cell, primary and secondary alkaline battery cells can be the power source in systems where the

TPS6100x is used.

programming the TPS61000 and TPS61007 adjustable output voltage devices

The output voltage of the TPS61000 and TPS61007 can be adjusted with an external resistor divider. The typical

value of the voltage on the FB pin is 500 mV in fixed frequency operation and 485 mV in the power-save

operation mode. The maximum allowed value for the output voltage is 3.3 V. The current through the resistive

divider should be about 100 times greater than the current into the FB pin. The typical current into the FB pin

is 0.01 µA, and the voltage across R4 is typically 500 mV . Based on those two values, the recommended value

for R4 is in the range of 500 kΩ in order to set the divider current at 1 µA. From that, the value of resistor R3,

depending on the needed output voltage VOUT, can be calculated using the following equation:

R3 +R4 ǒVO

VFB *1Ǔ+500 kΩ ǒVO

500 mV *1Ǔ(1)

If, as an example, an output voltage of 2.5 V is needed, a 2-MΩ resistor should be chosen for R3.

VBAT

VOUT

LBO

R5 R3

TPS61007

LBI

9FB

COMP 2

CC1

100 pF CC2

33 nF

10 kΩ

GND

10 µF

10 V

22 µF

10 V

Low Battery

Warning

33 µH

FBGND 8

Alkaline Cell

Figure 18. Typical Application Circuit for Adjustable Output Voltage Option

The TPS61007 is an improved version of the TPS61000 adjustable output voltage device. The FBGND pin is

internally connected to GND.

TPS61000, TPS61001, TPS61002, TPS61003, TPS61004, TPS61005, TPS61006, TPS61007

SINGLE- AND DUAL-CELL BOOST CONVERTER WITH START-UP INTO FULL LOAD

SLVS279C – MARCH 2000 – REVISED APRIL 2003

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

APPLICATION INFORMATION

programming the low battery comparator threshold voltage

The current through the resistive divider should be about 100 times greater than the current into the LBI pin.

The typical current into the LBI pin is 0.01 µA. The voltage across R2 is equal to the reference voltage that is

generated on-chip, which has a value of 500 mV ±15 mV. The recommended value for R2 is therefore in the

range of 500 kΩ. From that, the value of resistor R1, depending on the desired minimum battery voltage (VBAT),

can be calculated using the following equation:

R1 +R2 ǒVTRIP

VREF *1Ǔ+500 kΩ ǒVBAT

0.5 V *1Ǔ(2)

For example, if the low-battery detection circuit should flag an error condition on the LBO output pin at a battery

voltage of 1.0 V, a resistor in the range of 500 kΩ should be chosen for R1.

The output of the low battery comparator is a simple open-drain output that goes active low if the battery voltage

drops below the programmed threshold voltage on LBI. The output requires a pullup resistor with a

recommended value of 1MΩ, and should only be pulled up to the VOUT. If not used, the LBO pin can be left

floating.

inductor selection

The output filter of inductive switching regulators is a low pass filter of second order. It consists of an inductor and

a capacitor, often referred to as storage inductor and output capacitor.

To select an inductor, keep the possible peak inductor current below the current limit threshold of the power

switch in your chosen configuration. For example, the current limit threshold of the TPS61006’s switch is

1 100 mA at an output voltage of 3.3 V . The highest peak current through the inductor and the switch depends on

the output load, the input (VBAT), and the output voltage (VOUT). Estimation of the maximum average inductor

current can be done using the following equation:

IL+IOUT xVOUT

VBAT x0.8 (3)

For example, for an output current of 100 mA at 3.3 V, at least 515-mA current flows through the inductor at a

minimum input voltage of 0.8 V.

The second parameter for choosing the inductor is the desired current ripple in the inductor. Normally it is advis-

able to work with a ripple of less than 20% of the average inductor current. A smaller ripple reduces the magnetic

hysteresis losses in the inductor as well as output voltage ripple and EMI. But in the same way, the regulation

time at load change rises. In addition, a larger inductor increases the total system cost.

TPS61000, TPS61001, TPS61002, TPS61003, TPS61004, TPS61005, TPS61006, TPS61007

SINGLE- AND DUAL-CELL BOOST CONVERTER WITH START-UP INTO FULL LOAD

SLVS279C – MARCH 2000 – REVISED APRIL 2003

16 POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

APPLICATION INFORMATION

With those parameters it is possible to calculate the value for the inductor:

L+VBAT xǒVOUT –VBATǓ

∆ILxfxV

OUT (4)

Parameter f is the switching frequency and ∆IL is the ripple current in the inductor, i.e., 20% x IL.

In this example, the desired inductor has the value of 12 µH. With this calculated value and the calculated cur-

rents, it is possible to chose a suitable inductor. Care has to be taken that load transients and losses in the circuit

can lead to higher currents as estimated in equation 3. Also, the losses in the inductor caused by magnetic hys-

teresis losses and copper losses are a major parameter for total circuit efficiency.

The following inductors from different suppliers were tested. All work with the TPS6100x converter within their

specified parameters:

Table 1. Recommended Inductors

VENDOR PART NUMBER

Coilcraft DO1608P Series

DS1608P Series

DO3308 Series

Coiltronics UP1B Series

UP2B Series

Murata LQH3N Series

Sumida CD43 Series

CD54 Series

CDR74B Series

TDK NLC453232T Series

capacitor selection

The major parameter necessary to define the output capacitor is the maximum allowed output voltage ripple of

the converter . This ripple is determined by two parameters of the capacitor, the capacitance and the ESR. It is

possible to calculate the minimum capacitance needed for the defined ripple, supposing that the ESR is zero.

Cmin +IOUT xǒVOUT –VBATǓ

fx∆VxV

OUT (5)

Parameter f is the switching frequency and ∆V is the maximum allowed ripple.

With a chosen ripple voltage of 15 mV , a minimum capacitance of 10 µF is needed. The total ripple will be larger

due to the ESR of the output capacitor . This additional component of the ripple can be calculated using the fol-

lowing equation:

∆VESR +IOUT xR

ESR (6)

TPS61000, TPS61001, TPS61002, TPS61003, TPS61004, TPS61005, TPS61006, TPS61007

SINGLE- AND DUAL-CELL BOOST CONVERTER WITH START-UP INTO FULL LOAD

SLVS279C – MARCH 2000 – REVISED APRIL 2003

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

APPLICATION INFORMATION

An additional ripple of 30 mV is the result of using a tantalum capacitor with a low ESR of 300 mΩ. The total ripple

is the sum of the ripple caused by the capacitance and the ripple caused by the ESR of the capacitor. In this

example, the total ripple is 45 mV . It is possible to improve the design by enlarging the capacitor or using smaller

capacitors in parallel to reduce the ESR or by using better capacitors with lower ESR, like ceramics. For exam-

ple, a 10-µF ceramic capacitor with an ESR of 50 mΩ is used on the evaluation module (EVM). Tradeoffs have to

be made between performance and costs of the converter circuit.

A 10-µF input capacitor is recommended to improve transient behavior of the regulator. A ceramic capacitor or a

tantalum capacitor with a 100-nF ceramic capacitor in parallel placed close to the IC is recommended.

rectifier selection

The rectifier diode has a major impact on the overall converter efficiency. Standard diodes are not suitable for

low-voltage switched mode power supplies. A Schottky diode with low forward voltage and fast reverse recovery

should be used as a rectifier to minimize overall losses of the dc-dc converter. The maximum current rating of the

diode must be high enough for the application. The maximum diode current is equal to the maximum current in

the inductor that was calculated in equation 3. The maximum reverse voltage is the output voltage. The chosen

diode should therefore have a reverse voltage rating higher than the output voltage.

Table 2. Recommended Diodes

VENDOR PART NUMBER

Motorola Surface Mount MBRM120LT3

MBR0520LT1

Motorola Axial Lead 1N1517

ROHM RB520S-30

RB160L–40

The typical forward voltage of those diodes is in the range of 0.35 to 0.45 V assuming a peak diode current of

600 mA.

compensation of the control loop

An R/C/C network must be connected to the COMP pin in order to stabilize the control loop of the converter. Both

the pole generated by the inductor L1 and the zero caused by the ESR and capacitance of the output capacitor

must be compensated. The network shown in Figure 19 satisfies these requirements.

CC2

33 nF

CC1

100 pF

10 kΩ

COMP

Figure 19. Compensation of the Control Loop

TPS61000, TPS61001, TPS61002, TPS61003, TPS61004, TPS61005, TPS61006, TPS61007

SINGLE- AND DUAL-CELL BOOST CONVERTER WITH START-UP INTO FULL LOAD

SLVS279C – MARCH 2000 – REVISED APRIL 2003

18 POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

APPLICATION INFORMATION

Resistor RC and capacitor CC2 depend on the chosen inductance. For a 33-µH inductor, the capacitance of CC2

should be chosen to 33 nF , or in other words, if the inductor is xx µH, the chosen compensation capacitor should

be xx nF, the same number value. The value of the compensation resistor is then chosen based on the require-

ment to have a time constant of 0.3 ms for the R/C network of RC and CC2; hence for a 33-nF capacitor, a 10-kΩ

resistor should be chosen for RC.

Capacitor CC1 is depending on the ESR and capacitance value of the output capacitor, and on the value chosen

for RC. Its value is calculated using following equation:

CC1 +COx ESRCOUT

3 RC(7)

For a selected output capacitor of 22 µF with an ESR of 0.2 Ω, and RC of 33 kΩ, the value of CC1 is in the range of

100 pF.

Table 3. Recommended Compensation Components

INDUCTOR

OUTPUT CAPACITOR

INDUCTOR

[µH] CAPACITANCE

[µF] ESR

[Ω]

[kΩ] CC1

[pF] CC2

[nF]

33 22 0.2 10 100 33

22 22 0.3 15 100 22

10 22 0.4 33 100 10

10 10 0.1 33 100 10

schematic of TPS6100x evaluation modules (TPS6100xEVM–156)

LBO

LBI

NC/FBGND

VBAT

COMP

GND

VOUT

LP1

C1 C3

R2 R1 IN

OUT

TPS6100x

Evaluation modules are available for device types TPS61000, TPS61002, TPS61003, and TPS61006.

TPS61000, TPS61001, TPS61002, TPS61003, TPS61004, TPS61005, TPS61006, TPS61007

SINGLE- AND DUAL-CELL BOOST CONVERTER WITH START-UP INTO FULL LOAD

SLVS279C – MARCH 2000 – REVISED APRIL 2003

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

APPLICATION INFORMATION

suggested board layout and component placement (21 mm x 21 mm board size)

Figure 20. Top Layer Layout and Component Placement

Figure 21. Bottom Layer Layout and Component Placement

TPS61000, TPS61001, TPS61002, TPS61003, TPS61004, TPS61005, TPS61006, TPS61007

SINGLE- AND DUAL-CELL BOOST CONVERTER WITH START-UP INTO FULL LOAD

SLVS279C – MARCH 2000 – REVISED APRIL 2003

20 POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

THERMAL INFORMATION

Implementation of integrated circuits in low-profile and fine-pitch surface-mount packages typically requires

special attention to power dissipation. Many system-dependent issues such as thermal coupling, airflow, added

heat sinks and convection surfaces, and the presence of other heat-generating components affect the power-

dissipation limits of a given component.

Three basic approaches for enhancing thermal performance are listed below:

•Improving the power dissipation capability of the PWB design

•Improving the thermal coupling of the component to the PWB

•Introducing airflow in the system

The maximum junction temperature (TJ) of the TPS6100x devices is 125°C. The thermal resistance of the

10-pin MSOP package (DGS) is RθJA = 294°C/W. Specified regulator operation is assured to a maximum

ambient temperature (TA) of 85 °C. Therefore, the maximum power dissipation is about 130 mW . More power

can be dissipated if the maximum ambient temperature of the application is lower.

MAXJ

MAXD

P 136

/294

85125)(

)( =

°–°

=(8)

–

Under normal operating conditions, the sum of all losses generated inside the converter IC is less than 50 mW ,

which is well below the maximum allowed power dissipation of 136 mW as calculated in equation 8. Therefore,

power dissipation is given no special attention.

Table 4 shows where the losses inside the converter are generated.

Table 4. Losses Inside the Converter

LOSSES AMOUNTS

Conduction losses in the switch 36 mW

Switching losses 8 mW

Gate drive losses 2.3 mW

Quiescent current losses < 1 mW

TOTAL < 50 mW

PACKAGE OPTION ADDENDUM

www.ti.com 30-Jul-2011

Addendum-Page 1

PACKAGING INFORMATION

Orderable Device Status (1) Package Type Package

Drawing Pins Package Qty Eco Plan (2) Lead/

Ball Finish MSL Peak Temp (3) Samples

(Requires Login)

TPS61000DGS ACTIVE MSOP DGS 10 80 Green (RoHS

& no Sb/Br) CU NIPDAU Level-1-260C-UNLIM

TPS61000DGSG4 ACTIVE MSOP DGS 10 80 Green (RoHS

& no Sb/Br) CU NIPDAU Level-1-260C-UNLIM

TPS61000DGSR ACTIVE MSOP DGS 10 2500 Green (RoHS

& no Sb/Br) CU NIPDAU Level-1-260C-UNLIM

TPS61000DGSRG4 ACTIVE MSOP DGS 10 2500 Green (RoHS

& no Sb/Br) CU NIPDAU Level-1-260C-UNLIM

TPS61000DGST PREVIEW MSOP DGS 10 TBD Call TI Call TI

TPS61002DGSR ACTIVE MSOP DGS 10 2500 Green (RoHS

& no Sb/Br) CU NIPDAU Level-1-260C-UNLIM

TPS61002DGSRG4 ACTIVE MSOP DGS 10 2500 Green (RoHS

& no Sb/Br) CU NIPDAU Level-1-260C-UNLIM

TPS61003DGS ACTIVE MSOP DGS 10 80 Green (RoHS

& no Sb/Br) CU NIPDAU Level-1-260C-UNLIM

TPS61003DGSG4 ACTIVE MSOP DGS 10 80 Green (RoHS

& no Sb/Br) CU NIPDAU Level-1-260C-UNLIM

TPS61004DGS ACTIVE MSOP DGS 10 80 Green (RoHS

& no Sb/Br) CU NIPDAU Level-1-260C-UNLIM

TPS61004DGSG4 ACTIVE MSOP DGS 10 80 Green (RoHS

& no Sb/Br) CU NIPDAU Level-1-260C-UNLIM

TPS61005DGS ACTIVE MSOP DGS 10 80 Green (RoHS

& no Sb/Br) CU NIPDAU Level-1-260C-UNLIM

TPS61005DGSG4 ACTIVE MSOP DGS 10 80 Green (RoHS

& no Sb/Br) CU NIPDAU Level-1-260C-UNLIM

TPS61005DGSR ACTIVE MSOP DGS 10 2500 Green (RoHS

& no Sb/Br) CU NIPDAU Level-1-260C-UNLIM

TPS61005DGSRG4 ACTIVE MSOP DGS 10 2500 Green (RoHS

& no Sb/Br) CU NIPDAU Level-1-260C-UNLIM

TPS61005DGST PREVIEW MSOP DGS 10 TBD Call TI Call TI

TPS61006DGS ACTIVE MSOP DGS 10 80 Green (RoHS

& no Sb/Br) CU NIPDAU Level-1-260C-UNLIM

TPS61006DGSG4 ACTIVE MSOP DGS 10 80 Green (RoHS

& no Sb/Br) CU NIPDAU Level-1-260C-UNLIM

PACKAGE OPTION ADDENDUM

www.ti.com 30-Jul-2011

Addendum-Page 2

Orderable Device Status (1) Package Type Package

Drawing Pins Package Qty Eco Plan (2) Lead/

Ball Finish MSL Peak Temp (3) Samples

(Requires Login)

TPS61006DGSR ACTIVE MSOP DGS 10 2500 Green (RoHS

& no Sb/Br) CU NIPDAU Level-1-260C-UNLIM

TPS61006DGSRG4 ACTIVE MSOP DGS 10 2500 Green (RoHS

& no Sb/Br) CU NIPDAU Level-1-260C-UNLIM

TPS61006DGST PREVIEW MSOP DGS 10 TBD Call TI Call TI

TPS61007DGS ACTIVE MSOP DGS 10 80 Green (RoHS

& no Sb/Br) CU NIPDAU Level-1-260C-UNLIM

TPS61007DGSG4 ACTIVE MSOP DGS 10 80 Green (RoHS

& no Sb/Br) CU NIPDAU Level-1-260C-UNLIM

(1) The marketing status values are defined as follows:

ACTIVE: Product device recommended for new designs.

LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect.

NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design.

PREVIEW: Device has been announced but is not in production. Samples may or may not be available.

OBSOLETE: TI has discontinued the production of the device.

(2) Eco Plan - The planned eco-friendly classification: Pb-Free (RoHS), Pb-Free (RoHS Exempt), or Green (RoHS & no Sb/Br) - please check http://www.ti.com/productcontent for the latest availability

information and additional product content details.

TBD: The Pb-Free/Green conversion plan has not been defined.

Pb-Free (RoHS): TI's terms "Lead-Free" or "Pb-Free" mean semiconductor products that are compatible with the current RoHS requirements for all 6 substances, including the requirement that

lead not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, TI Pb-Free products are suitable for use in specified lead-free processes.

Pb-Free (RoHS Exempt): This component has a RoHS exemption for either 1) lead-based flip-chip solder bumps used between the die and package, or 2) lead-based die adhesive used between

the die and leadframe. The component is otherwise considered Pb-Free (RoHS compatible) as defined above.

Green (RoHS & no Sb/Br): TI defines "Green" to mean Pb-Free (RoHS compatible), and free of Bromine (Br) and Antimony (Sb) based flame retardants (Br or Sb do not exceed 0.1% by weight

in homogeneous material)

(3) MSL, Peak Temp. -- The Moisture Sensitivity Level rating according to the JEDEC industry standard classifications, and peak solder temperature.

Important Information and Disclaimer:The information provided on this page represents TI's knowledge and belief as of the date that it is provided. TI bases its knowledge and belief on information

provided by third parties, and makes no representation or warranty as to the accuracy of such information. Efforts are underway to better integrate information from third parties. TI has taken and

continues to take reasonable steps to provide representative and accurate information but may not have conducted destructive testing or chemical analysis on incoming materials and chemicals.

TI and TI suppliers consider certain information to be proprietary, and thus CAS numbers and other limited information may not be available for release.

In no event shall TI's liability arising out of such information exceed the total purchase price of the TI part(s) at issue in this document sold by TI to Customer on an annual basis.

TAPE AND REEL INFORMATION

*All dimensions are nominal

Device Package

Type Package

Drawing Pins SPQ Reel

Diameter

(mm)

Reel

Width

W1 (mm)

(mm) B0

(mm) K0

(mm) P1

(mm) W

(mm) Pin1

Quadrant

TPS61000DGSR MSOP DGS 10 2500 330.0 12.4 5.3 3.4 1.4 8.0 12.0 Q1

TPS61002DGSR MSOP DGS 10 2500 330.0 12.4 5.3 3.4 1.4 8.0 12.0 Q1

TPS61005DGSR MSOP DGS 10 2500 330.0 12.4 5.3 3.4 1.4 8.0 12.0 Q1

TPS61006DGSR MSOP DGS 10 2500 330.0 12.4 5.3 3.4 1.4 8.0 12.0 Q1

PACKAGE MATERIALS INFORMATION

www.ti.com 3-Mar-2012

Pack Materials-Page 1

*All dimensions are nominal

Device Package Type Package Drawing Pins SPQ Length (mm) Width (mm) Height (mm)

TPS61000DGSR MSOP DGS 10 2500 358.0 335.0 35.0

TPS61002DGSR MSOP DGS 10 2500 358.0 335.0 35.0

TPS61005DGSR MSOP DGS 10 2500 358.0 335.0 35.0

TPS61006DGSR MSOP DGS 10 2500 358.0 335.0 35.0

PACKAGE MATERIALS INFORMATION

www.ti.com 3-Mar-2012

Pack Materials-Page 2

IMPORTANT NOTICE

Texas Instruments Incorporated and its subsidiaries (TI) reserve the right to make corrections, modifications, enhancements, improvements,

and other changes to its products and services at any time and to discontinue any product or service without notice. Customers should

obtain the latest relevant information before placing orders and should verify that such information is current and complete. All products are

sold subject to TI’s terms and conditions of sale supplied at the time of order acknowledgment.

TI warrants performance of its hardware products to the specifications applicable at the time of sale in accordance with TI’s standard

warranty. Testing and other quality control techniques are used to the extent TI deems necessary to support this warranty. Except where

mandated by government requirements, testing of all parameters of each product is not necessarily performed.

TI assumes no liability for applications assistance or customer product design. Customers are responsible for their products and

applications using TI components. To minimize the risks associated with customer products and applications, customers should provide

adequate design and operating safeguards.

TI does not warrant or represent that any license, either express or implied, is granted under any TI patent right, copyright, mask work right,

or other TI intellectual property right relating to any combination, machine, or process in which TI products or services are used. Information

published by TI regarding third-party products or services does not constitute a license from TI to use such products or services or a

warranty or endorsement thereof. Use of such information may require a license from a third party under the patents or other intellectual

property of the third party, or a license from TI under the patents or other intellectual property of TI.

Reproduction of TI information in TI data books or data sheets is permissible only if reproduction is without alteration and is accompanied

by all associated warranties, conditions, limitations, and notices. Reproduction of this information with alteration is an unfair and deceptive

business practice. TI is not responsible or liable for such altered documentation. Information of third parties may be subject to additional

restrictions.

Resale of TI products or services with statements different from or beyond the parameters stated by TI for that product or service voids all

express and any implied warranties for the associated TI product or service and is an unfair and deceptive business practice. TI is not

responsible or liable for any such statements.

TI products are not authorized for use in safety-critical applications (such as life support) where a failure of the TI product would reasonably

be expected to cause severe personal injury or death, unless officers of the parties have executed an agreement specifically governing

such use. Buyers represent that they have all necessary expertise in the safety and regulatory ramifications of their applications, and

acknowledge and agree that they are solely responsible for all legal, regulatory and safety-related requirements concerning their products

and any use of TI products in such safety-critical applications, notwithstanding any applications-related information or support that may be

provided by TI. Further, Buyers must fully indemnify TI and its representatives against any damages arising out of the use of TI products in

such safety-critical applications.

TI products are neither designed nor intended for use in military/aerospace applications or environments unless the TI products are

specifically designated by TI as military-grade or "enhanced plastic."Only products designated by TI as military-grade meet military

specifications. Buyers acknowledge and agree that any such use of TI products which TI has not designated as military-grade is solely at

the Buyer's risk, and that they are solely responsible for compliance with all legal and regulatory requirements in connection with such use.

TI products are neither designed nor intended for use in automotive applications or environments unless the specific TI products are

designated by TI as compliant with ISO/TS 16949 requirements. Buyers acknowledge and agree that, if they use any non-designated

products in automotive applications, TI will not be responsible for any failure to meet such requirements.

Following are URLs where you can obtain information on other Texas Instruments products and application solutions:

Products Applications

Audio www.ti.com/audio Automotive and Transportation www.ti.com/automotive

Amplifiers amplifier.ti.com Communications and Telecom www.ti.com/communications

Data Converters dataconverter.ti.com Computers and Peripherals www.ti.com/computers

DLP®Products www.dlp.com Consumer Electronics www.ti.com/consumer-apps

DSP dsp.ti.com Energy and Lighting www.ti.com/energy

Clocks and Timers www.ti.com/clocks Industrial www.ti.com/industrial

Interface interface.ti.com Medical www.ti.com/medical

Logic logic.ti.com Security www.ti.com/security

Power Mgmt power.ti.com Space, Avionics and Defense www.ti.com/space-avionics-defense

Microcontrollers microcontroller.ti.com Video and Imaging www.ti.com/video

RFID www.ti-rfid.com

OMAP Mobile Processors www.ti.com/omap

Wireless Connectivity www.ti.com/wirelessconnectivity

TI E2E Community Home Page e2e.ti.com

Mailing Address: Texas Instruments, Post Office Box 655303, Dallas, Texas 75265