1250S08-U - THAT - Datasheet.Directory

FEATURES

• Good CMRR: typ. 50 dB at 60Hz

• Low cost, self-contained

• Excellent audio performance

– Wide bandwidth: typ. >8.6 MHz

– High slew rate: typ. 12 V/μs

– Low distortion: typ. 0.0006% THD

– Low noise: typ. -103 dBu

• Low current: typ. 2 mA

• Several gains: 0 dB, ±3 dB, ±6 dB

• Industry Standard Pinout

APPLICATIONS

• Balanced Audio Line Receivers

• Instrumentation Amplifiers

• Differential Amplifiers

• Precision Summers

• Current Shunt Monitors

THAT 1250, 1253, 1256

The THAT 1250-series of precision differential

amplifiers was designed primarily for use as balanced

line receivers for audio applications. Gains of 0 db, ±3

dB, and ±6 dB are available to suit various applications

requirements.

These devices include on-board precision thin-

film resistors which offer good matching and excellent

tracking due to their monolithic construction.

Manufactured in THAT Corporation’s proprietary

complementary dielectric isolation (DI) process, the

THAT 1250-series provides the sonic benefits of

discrete designs with the simplicity, reliability, matching

and small size of an integrated solution.

All three versions of the part typically exhibit 50

dB of common-mode rejection. With 12 V/μs slew rate,

>8.6 MHz bandwidth, and 0.0006% THD, these

devices are sonically transparent. Moreover, current

consumption is typically a low 2 mA. Both surface-

mount and DIP packages are available.

The THAT 1256 is pin-compatible with the TI

INA137 and Analog Devices SSM2143, while the THAT

1250 is pin-compatible with the TI INA134 and Analog

Devices SSM2141.

Description

Sense

Vout

Ref

Vee

In+

In-

R1R2

R3R4

Gain R1 , R3R2 , R4

Part no.

THAT1250

THAT1253

THAT1256

0 dB

-3 dB

-6 dB

Figure

THAT 1250

series equivalent circuit diagram

88NC

77Vcc

66Vout

55Sense

44Vee

33In+

22In-

11Ref

SO PinDIP PinPin Name

Table 1. 1250-series pin assignments

Low Cost, Balanced

Line Receiver ICs

THAT Corporation; 45 Sumner Street; Milford, MA 01757-1656; US

Tel: +1 508 478 9200; Fax: +1 508 478 0990; Web: www.thatcorp.com

1256S08-U1256P08-U±6 dB

1253S08-U1253P08-U±3 dB

1250S08-U1250P08-U0 dB

Plastic SOPlastic DIPGain

Table 2. Ordering information

Document 600068 Rev 02 Page 2 of 8 THAT 1250 Series

Low-cost Balanced Line Receiver ICs

THAT Corporation; 45 Sumner Street; Milford, MA 01757-1656; USA

Tel: +1 508 478 9200; Fax: +1 508 478 0990; Web: www.thatcorp.com

Supply Voltages (VCC - VEE)40V

Maximum In- or In+ Voltage -50V + VCC, 50V + VEE

Max/Min Ref or Sense Voltage VCC + 0.5V, VEE - 0.5V

Maximum Output Voltage (VOM)V

CC + 0.5V, VEE - 0.5V

Storage Temperature Range (TST) -40 to +125 ºC

Operating Temperature Range (TOP) 0 to +85 ºC

Output Short-Circuit Duration (tSH) Continuous

Junction Temperature (TJ) +125 ºC

Absolute Maximum Ratings2,3

SPECIFICATIONS1

Parameter Symbol Conditions Min Typ Max Units

Supply Current ICC No signal — 2.0 2.8 mA

Supply Voltage VCC-VEE 6 — 36 V

Input Voltage Range VIN-DIFF Differential (equal and opposite swing)

1250 (0dB gain) — 21.5 — dBu

1253 (-3dB gain) — 24.4 — dBu

1256 (-6dB gain) — 27.5 — dBu

VIN-CM Common Mode

1250 (0dB gain) — 27.5 — dBu

1253 (-3dB gain) — 29.1 — dBu

1256 (-6dB gain) — 31 — dBu

Input Impedance5ZIN-DIFF Differential

1250 (0dB gain) — 18 — kΩ

1253 (-3dB gain) — 21 — kΩ

1256 (-6dB gain) — 24 — kΩ

ZIN-CM Common Mode

All versions — 18 — kΩ

Common Mode Rejection Ratio CMRR Matched source impedances; VCM = ±10V

DC 40 50 — dB

60Hz 40 50 — dB

20kHz — 50 — dB

Power Supply Rejection Ratio6PSRR ±3V to ±18V; VCC = -VEE; all gains — 90 — dB

Total Harmonic Distortion THD VIN_DIFF = 10dBV, f = 1kHz, BW = 22kHz, RL = 2 kΩ

— 0.0006 — %

Output Noise eOUT 22 Hz to 22kHz bandwidth

1250 (0dB gain) — -103 — dBu

1253 (-3dB gain) — -105 — dBu

1256 (-6dB gain) — -106 — dBu

Slew Rate SR RL = 2kΩ; CL = 300 pF, all gains — 12 — V/μs

Electrical Characteristics2,4

1. All specifications are subject to change without notice.

2. Unless otherwise noted, TA=25ºC, VCC=+15V, VEE= -15V.

3. Stresses above those listed under “Absolute Maximum Ratings” may cause permanent damage to the device. These are stress ratings only; the functional operation of

the device at these or any other conditions above those indicated in the operational sections of this specification is not impli ed. Exposure to absolute maximum rating condi-

tions for extended periods may affect device reliability.

4. 0 dBu = 0.775 Vrms.

5. While specific resistor ratios are very closely trimmed, absolute resistance values can vary ±25% from the typical values shown. Input impedance is

monitored by lot sampling.

6. Defined with respect to differential gain.

7. Parameter guaranteed over the entire range of power supply and temperature.

The THAT 1250-series ICs consist of high

performance opamps with integrated, thin-film resis-

tors. These designs take full advantage of THAT fully

complementary dielectric isolation (DI) process to

deliver excellent performance with low current

consumption. The devices are simple to apply in

many applications.

Resistor Matching, Values, and CMRR

The 1250-series devices rely upon the inherent

matching of silicon-chromium (Si-Cr), thin-film,

integrated resistors to achieve a 50 dB common

mode rejection ratio and tight gain accuracy. No

trimming is performed. As a result of their

monolithic construction, the R3/R4 ratio generally

matches within ±0.5% of the R1/R2 ratio. 0.5%

matching is about 50 dB CMRR for the 1256 and 52

dB for the 1250.

However, while the resistor ratios are tightly

controlled, the actual value of any individual resistor

is not. Lot-to-lot variations of up to ±30 % are to be

expected.

If higher CMRR is required in a simple input

stage, consider the THAT 1240-series ICs. These

parts are laser trimmed to improve the inherent

precision of our thin-film resistor process. For

THAT 1250 Series Page 3 of 8 Document 600068 Rev 02

Low-cost Balanced Line Receiver ICs

THAT Corporation; 45 Sumner Street; Milford, MA 01757-1656; USA

Tel: +1 508 478 9200; Fax: +1 508 478 0990; Web: www.thatcorp.com

Parameter Symbol Conditions Min Typ Max Units

Small signal bandwidth BW-3dB RL = 2kΩ; CL = 10 pF

1250 (0dB gain) — 8.6 — MHz

1253 (-3dB gain) — 12.2 — MHz

1256 (-6dB gain) — 18 — MHz

Output Gain Error GER-OUT f = 1 kHz -0.2 0 +0.2 dB

Output Voltage Swing VO+ RL = 2kΩ; CL = 200 pF VCC-3 VCC-2 — V

VO- RL = 2kΩ; CL = 200 pF — VEE+2 VEE+3 V

Output Offset Voltage VOFF No signal -10 — +10 mV

Output Short Circuit Current ISC RL = 0 Ω— ±25 — mA

Capacitive Load7CL— — 200 pF

Electrical Characteristics (con’t)2,4

Sense

Vout

Ref

VEE

VIN(CM)

In+

In-

½vIN(DIFF)

aCL

½vIN(DIFF)

Figure 2. THAT 1250 series test circuit

heory of Operation

demandin

applications in which the source imped-

ance balance may be less than perfect, the 1200-

series ICs offer exceptional CMRR performance via a

patented method of increasing common-mode input

impedance.

Input Considerations

The 1250-series devices are internally protected

against input overload via an unusual arrangement of

diodes connecting the + and - Input pins to the

power supply pins. The circuit of Figure 3 shows the

arrangement used for the R3 / R4 side; a similar one

applies to the other side. The zener diodes prevent

the protection network from conducting until an

input pin is raised at least 50 V above VCC or below

VEE. Thus, the protection networks protect the

devices without constraining the allowable signal

swing at the input pins. The reference (and sense)

pins are protected via more conventional reverse-

biased diodes which will conduct if these pins are

raised above VCC or below VEE.

Because the 1250-series devices are input

stages, their input pins are of necessity connected to

the outside world. This is likely to expose the parts

to ESD when cables are connected and disconnected.

Our testing indicates that the 1250-series devices will

typically withstand application of up to 1,000 volts

under the human body ESD model.

To reduce risk of damage from ESD, and to

prevent RF from reaching the devices, THAT recom-

mends the circuit of Figure 4. C3 through C5 should

be located close to the point where the input signal

comes into the chassis, preferably directly on the

input connector. The unusual circuit design

minimizes the unbalancing impact of differences in

the values of C4 and C5 by forcing the capacitance

from each input to chassis ground to depend primar-

ily on the value of C3. The circuit shown is approxi-

mately ten times less sensitive to mismatches

between C4 and C5 than the more conventional

approach in which the junction of C4 and C5 is

grounded directly6.

Designers frequently seek to improve RF bypass-

ing through the addition of R-C networks at the

inputs (series resistor followed by a capacitor to

ground at each input). Generally, THAT recommends

keeping any such series resistances under 50W, so

as not to upset the intrinsic balance between the

1250’s internal R1/R2 and R3/R4 resistor ratios.

Because the internal resistor absolute values are not

well controlled, the external resistors can interact

with the internal ones in unexpected ways. As an

alternative to a resistor as additional build-out

impedance, THAT recommends the use of a ferrite

bead or balun instead.

If it is necessary to ac-couple the inputs of the

1250-series parts, the coupling capacitors should be

sized to present negligible impedance at any frequen-

cies of interest for common mode rejection. Regard-

less of the type of coupling capacitor chosen,

variations in the values of the two capacitors,

working against the 1250-series input impedance,

can unbalance common mode input signals, convert-

ing them to balanced signals which will not be

rejected by the CMRR of the devices. For this reason,

THAT recommends dc-couplin

the inputs of the

1250-series devices.

Input Voltage Limitations

When configured, respectively, for -3 dB and

-6 dB gain, the 1253 and 1256 devices are capable of

accepting input signals above the power supply rails.

This is because the internal opamp’s inputs connect

to the outside world only through the on-chip resis-

tors R1 through R4 at nodes a and b as shown in

Figure 2. Consider the following analysis.

Differential Input Signals

For differential signals (vIN(DIFF)), the limitation to

signal handling will be output clipping. The outputs

of all the devices typically clip at within 2V of the

supply rails. Therefore, maximum differential input

signal levels are directly related to the gain and

supply rails.

Common-mode Input Signals

For common-mode input signals, there is very

little output signal. The limitation on common-mode

handling is the point at which the inputs are

overloaded. So, we must consider the inputs of the

opamp.

For common-mode signals (VIN(CM)), the common-

mode input current splits to flow through both R1/R2

and through R3/R4. Because vb is constrained to

follow Va, we will consider only the voltage at node a.

The voltage at a can be calculated as:

va=vIN(CM)R4

R3+R4

Again, solving for VIN(CM),

vIN(CM)=vaR3+R4

For the 1250, (R3 + R4) / R4 = 2. For the 1253,

(R3 + R4) / R4 = 2.4. For the 1256, (R3 + R4) / R4=3.

Furthermore, the same constraints apply to Va as in

the differential analysis.

Following the same reasoning as above, the

maximum common-mode input signal for the 1250 is

(2VCC - 4) V, and the minimum is (2VEE + 4) V. For

the 1253, these figures are (2.4VCC - 4.8) V, and

(2.4VEE + 4.8) V. For the 1256, these figures are

(3VCC - 6) V, and (3VEE + 6) V.

Therefore, for common-mode signals and ±15 V

rails, the 1250 will accept up to ~26 V in either

direction. As an ac signal, this is 52 V peak-peak,

18.4 V rms, or +27.5 dBu. With the same supply

rails, the 1253 will accept up to ~31 V in either

direction. As an ac signal, this is 62 V peak-peak,

21.9 V rms, or +29 dBu. With the same supply rails,

the 1256 will accept up to ~39 V in either direction.

As an ac signal, this is 78 V peak-peak, 27.6 V rms,

or +31 dBu.

Of course, in the real world, differential and

common-mode signals combine. The maximum

signal that can be accommodated will depend on the

Document 600068 Rev 02 Page 4 of 8 THAT 1250 Series

Low-cost Balanced Line Receiver ICs

THAT Corporation; 45 Sumner Street; Milford, MA 01757-1656; USA

Tel: +1 508 478 9200; Fax: +1 508 478 0990; Web: www.thatcorp.com

superposition of both differential and common-

mode limitations.

Output Considerations

The 1250-series devices are typically capable of

supplying 25 mA into a short circuit. While they will

survive a short, power dissipation will rise dramati-

cally if the output is shorted. Junction temperature

must be kept under 125 ºC to maintain the devices’

specifications.

These devices are stable with up to 300 pF of

load capacitance.

Power Supply Considerations

The 1250-series parts are not particularly sensi-

tive to the power supply, but they do contain wide

bandwidth opamps. Accordingly, small local bypass

capacitors should be located within a few inches o

the supply pins on these parts, as shown in Figure 4.

Selecting a Gain Variation

The three different parts offer different gain

structures to suit different applications. The 1256 is

customarily configured for -6 dB gain, but by revers-

ing the resistor connections, can also be configured

for +6 dB. The 1253 is most often configured for -3

dB gain, but can also be configured for +3 dB. The

choice of input gain is determined by the input

voltage range to be accommodated, and the power

supply voltages used within the circuit.

To minimize noise and maximize signal-to-noise

ratio, the input stage should be selected and config-

ured for the highest possible gain that will ensure

that maximum-level input signals will not clip the

input stage or succeeding stages. For example, with

±18 V supply rails, the 1250-series parts have a

maximum output signal swing of +23 dBu. In order

to accommodate +24 dBu input signals, the

maximum gain for the stage is -1 dB. With ±15 V

supply rails, the maximum output signal swing is

~+21.1 dBu; here, -3 dB is the maximum gain. In

each case, a 1253 configured for -3 dB gain is the

ideal choice. The 1250 (0dB gain only) will not

provide enough headroom at its output to support a

+24 dBu input signal. The 1256 (configured for -6

dB gain) will increase noise, thus reducing dynamic

range, by attenuating the input signal more than

necessary to support a +24 dBu input.

In fact, for most professional audio applications,

THAT recommends the -3 dB input configuration

possible only with the 1253 in order to preserve

dynamic range within a reasonable range of power

supply voltages and external headroom limits.

THAT 1250 Series Page 5 of 8 Document 600068 Rev 02

Low-cost Balanced Line Receiver ICs

THAT Corporation; 45 Sumner Street; Milford, MA 01757-1656; USA

Tel: +1 508 478 9200; Fax: +1 508 478 0990; Web: www.thatcorp.com

Figure 5. Zero dB line receiver

+In

-In 5

9k 9k

THAT1250

Output

Sense

Vout

Ref

VCC

VEE

In+

In-

In+ Ref

VCC

VEE

VCC

VEE

R3R4

Figure 3. Representative input protection circuit

470p

47p

In+

In-

Out

100n

VCC

VEE

In-

In+

Out 6

THAT1256/1253/1250

Ref

Sens

VEE

VCC 5

Figure 4. RFI and supply bypassing

The THAT 1250, 1253, and 1256 are usually

thought of as precision differential amplifiers with

gains of zero, -3 and -6 dB respectively. These

devices are primarily intended as balanced line

receivers for audio applications. However, their

topology lends itself to other applications as well.

Basic Balanced Receiver Applications

Figures 5, 6, and 7, respectively, show the THAT

1250, 1256, and 1253 configured as zero, -6 dB, and

-3 dB line receivers. Figures 8 and 9, respectively,

show the 1253 and 1256 configured as +3 dB and

+6 dB line receivers. The higher gains are achieved

by swapping the positions of the resistors within

each pair in regard to signal input vs. Output. In all

five cases, no external resistors are required to set

the desired gain.

Figure 10 shows a THAT 1250 configured as a

precision summing amplifier. This circuit uses both

the In+ and Ref pins as inputs. Because of the good

matching between the resistor pairs, the output

voltage is precisely equal to the sum of the two input

voltages.

More Complex Applications

Figure 11 shows a convenient method of driving

a typical audio ADC with balanced inputs. This

circuit accepts +24 dBu in. By using a pair of THAT

1256 ICs connected in anti-phase, the signal level

between their respective outputs is +24 dBu. An

attenuator network brings this signal down by 24 dB

while attenuating the noise of the line receivers as

well.

The output noise of a THAT 1256 is -106 dBu.

Since there are two of them, and uncorrelated noise

sources add in RMS fashion, the total noise level

going into the resistive pad will be 3 dB higher, or

-103 dBu. The pad reduces the noise level to

-127 dBu at the input to the ADC. The noise density

resulting from the line receivers will therefore be

en line receiver =10 −127dBu

20 %0.775

20kHz =2.45 nV

The thermal noise of the 249 Ω resistor is

2.05 nV/√Hz. We can assume that the noise contri-

bution of R8 and R19 will be negligible, and therefore,

the total noise density going into the input of the ADC

will be

en total =(2.45 nV

Hz )2+(2.06 nV

Hz )2=3.2 nV

The noise floor can then be calculated to be

Noise(dBu)=20 log 3.2 nV

Hz %20kHz

0.775 =−124.7 dBu

Figure 12 shows the recommended method for

controlling gain in a balanced system. In such

circuits, designers are sometimes tempted to keep

the signal balanced and use two Voltage Controlled

Amplifiers (VCAs) to independently control the gain

on each half of the balanced signal. Unfortunately,

this can result in common-mode to differential-mode

Document 600068 Rev 02 Page 6 of 8 THAT 1250 Series

Low-cost Balanced Line Receiver ICs

THAT Corporation; 45 Sumner Street; Milford, MA 01757-1656; USA

Tel: +1 508 478 9200; Fax: +1 508 478 0990; Web: www.thatcorp.com

Applications

+In

-In 5

12k 6k

THAT1256

Output

Sense

Vout

Ref

VCC

VEE

In+

In-

Figure 9. +6 dB line receiver

+In

-In 5

10.5k 7.5k

THAT1253

Out

Sense

Vout

Ref

VCC

VEE

In+

In-

Figure 8. +3 dB line receiver

+In

-In 5

12k 6k

THAT1256

Output

Sense

Vout

Ref

VCC

VEE

In+

In-

Figure 7. -6 dB line receiver

Figure 6. -3 dB line receiver

+In

-In 5

10.5k 7.5k

THAT1253

Output

Sense

Vout

Ref

VCC

VEE

In+

In-

conversion (de

radin

CMRR) when there are even

slight differences in gain between the VCAs. A better

approach is to convert the signal to single-ended,

alter the gain, and then convert back to balanced.

In Figure 12 we use a THAT 1253 -3 dB line

receiver to do the balanced-to-single-ended conver-

sion. The VCA section also has a static gain of -3 dB

due to the ratio of R2 to R3. This circuit can accept

+24 dBu at its input, since the THAT 1253 output

stage is capable of delivering 21 dBu without distor-

tion. Reducing R3 to 14 kΩ results in a 3 dB reduc-

tion in VCA output noise. This arrangement results

in 3 dB greater dynamic range compared to the case

where a -6 dB line receiver and a VCA with zero dB

static gain are used. After the VCA, the signal is

restored to 24 dBu by the THAT 1606.

Document 600068 Rev 02 Page 7 of 8 THAT 1250 Series

Low-cost Balanced Line Receiver ICs

THAT Corporation; 45 Sumner Street; Milford, MA 01757-1656; US

Tel: +1 508 478 9200; Fax: +1 508 478 0990; Web: www.thatcorp.com

6Output

Input 1

Input 2

9k 9k

THAT1250

Sense

Vout

Ref

VCC

VEE

In+

In-

Figure 10. Precision two-input summing circuit

Figure 11. Circuit for audio ADCs with balanced inputs

In Hi

In Lo

AIN- to ADC

AIN+ to ADC

2k10

249R

R19

2k10

6n8

+24 dBu In

Vout 6

In+

In-

THAT

1256

Vout 6

In+

In-

1/2 Vref of ADC

+24 dBu Zero dBu Out

Ref

Sense

Ref

Sense

1THAT

1256

Figure 12. Automated gain control of a balanced signal

The THAT 1250 series is available in 8-pin PDIP

and 8-pin surface mount (SOIC) packages. Package

dimensions are shown below;

The 1250 series packages are entirely lead-free.

The lead-frames are copper, plated with successive

layers of nickel, palladium, and gold. This approach

makes it possible to solder these devices using lead-

free and lead-bearing solders.

Neither the lead-frames nor the plastic mold

compounds used in the 1250-series contains any

hazardous substances as specified in the European

Union's Directive on the Restriction of the Use of

Certain Hazardous Substances in Electrical and

Electronic Equipment 2002/95/EG of January 27,

2003. The surface-mount package is suitable for use

in a 100% tin solder process

Document 600068 Rev 02 Page 8 of 8 THAT 1250 Series

Low-cost Balanced Line Receiver ICs

THAT Corporation; 45 Sumner Street; Milford, MA 01757-1656; US

Tel: +1 508 478 9200; Fax: +1 508 478 0990; Web: www.thatcorp.com

Parameter Symbol Conditions Min Typ Max Units

Through-hole package See Fig. 13 for dimensions 8 Pin PDIP

Thermal Resistance θJA DIP package soldered to board 100 ºC/W

Environmental Regulation Compliance Complies with January 27, 2003 RoHS requirements

Surface mount package See Fig. 14 for dimensions 8 Pin SOP

Thermal Resistance θJA SO package soldered to board 150 ºC/W

Soldering Reflow Profile JEDEC JESD22-A113-D (250 ºC)

Moisture Sensitivity Level MSL Above-referenced JEDEC soldering profile 1

Environmental Regulation Compliance Complies with January 27, 2003 RoHS requirements

Package Characteristics

Package Information

ITEM

MILLIMETERS

9.52±0.10

6.35±0.10

7.49/8.13

0.46

2.54

3.68/4.32

0.25

3.18±0.10

8.13/9.40

3.30±0.10

INCHES

0.375±0.004

0.250±0.004

0.295/0.320

0.018

0.100

0.145/0.170

0.010

0.125±0.004

0.320/0.370

0.130±0.004

Figure 13. -P (DIP) version package outline drawing

0.41/1.27H 0.016/0.05

0.228/0.244

0.0075/0.0098

0.053/0.068

0.014/0.018

0.189/0.196

INCHES

0.150/0.157

ITEM MILLIMETERS

0.36/0.46

0.19/0.25

1.35/1.73

1.27

4.80/4.98

3.81/3.99

5.80/6.20

0.050

Figure 14. -S (SO) version package outline drawing