
SEMICONDUCTOR
TECHNICAL DATA
BRUSHLESS DC
MOTOR CONTROLLER
DW SUFFIX
PLASTIC PACKAGE
CASE 751D
(SO–20L)
PIN CONNECTIONS
Order this document by MC33033/D
P SUFFIX
PLASTIC PACKAGE
CASE 738
AT
BT
Top Drive
Output
12
Bottom
Drive
Outputs
11
(Top View)
13
14
15
16
17
10
9
8
7
6
5
Sensor
Inputs
4
Error Amp
Inverting Input
Error Amp
Non Inverting Input
Oscillator
Reference Output
SC
SB
SA
60
°
/120
°
SelectFwd/Rev
Error Amp Out/
PWM Input
Current Sense
Non Inverting Input
Gnd
CT
18
19
BB
CB
3
20
Output Enable
2
AB
1
VCC
20
1
20
1
1
MOTOROLA ANALOG IC DEVICE DATA
 
 
The MC33033 is a high performance second generation, limited feature,
monolithic brushless dc motor controller which has evolved from Motorola′s
full featured MC33034 and MC33035 controllers. It contains all of the active
functions required for the implementation of open loop, three or four phase
motor control. The device consists of a rotor position decoder for proper
commutation sequencing, temperature compensated reference capable of
supplying sensor power, frequency programmable sawtooth oscillator, fully
accessible error amplifier, pulse width modulator comparator, three open
collector top drivers, and three high current totem pole bottom drivers ideally
suited for driving power MOSFETs. Unlike its predessors, it does not feature
separate drive circuit supply and ground pins, brake input, or fault output
signal.
Included in the MC33033 are protective features consisting of
undervoltage lockout, cycle–by–cycle current limiting with a selectable time
delayed latched shutdown mode, and internal thermal shutdown.
Typical motor control functions include open loop speed, forward or
reverse direction, and run enable.The MC33033 is designed to operate
brushless motors with electrical sensor phasings of 60°/300° or 120°/240°,
and can also efficiently control brush dc motors.
•10 to 30 V Operation
•Undervoltage Lockout
•6.25 V Reference Capable of Supplying Sensor Power
•Fully Accessible Error Amplifier for Closed Loop Servo Applications
•High Current Drivers Can Control External 3–Phase MOSFET Bridge
•Cycle–By–Cycle Current Limiting
•Internal Thermal Shutdown
•Selectable 60°/300° or 120°/240° Sensor Phasings
•Also Efficiently Control Brush DC Motors with External MOSFET
H–Bridge
ORDERING INFORMATION
Device Operating
Temperature Range Package
MC33033DW
TA=–40
°
to +85
°
C
SO–20L
MC33033P
T
A = –
40°
t
o +
85°C
Plastic DIP
Motorola, Inc. 1996 Rev 3
MC33033
2MOTOROLA ANALOG IC DEVICE DATA
Motor
Enable
Q
S
CT
R
RT
Oscillator
Error Amp
PWM
Thermal
Shutdown
Reference
Regulator
Lockout
Undervoltage
VCC
FWR/REV
Q
R
S
Faster
SS
VM
Speed
Set
This device contains 266 active transistors.
Representative Schematic Diagram
Rotor
Position
Decoder
Output
Buffers
Current Sense
60
°
/120
°
N
N
MC33033
3
MOTOROLA ANALOG IC DEVICE DATA
MAXIMUM RATINGS
Rating Symbol Value Unit
Power Supply Voltage VCC 30 V
Digital Inputs (Pins 3, 4, 5, 6, 18, 19) – V ref V
Oscillator Input Current (Source or Sink) IOSC 30 mA
Error Amp Input Voltage Range
(Pins 9, 10, Note 1) VIR –0.3 to V ref V
Error Amp Output Current
(Source or Sink, Note 2) IOut 10 mA
Current Sense Input Voltage Range VSense –0.3 to 5.0 V
Top Drive V oltage (Pins 1, 2, 20) VCE(top) 40 V
Top Drive Sink Current (Pins 1, 2, 20) ISink(top) 50 mA
Bottom Drive Output Current
(Source or Sink, Pins 15,16, 17) IDRV 100 mA
Power Dissipation and Thermal Characteristics
P Suffix, Dual–In–Line, Case 738
Maximum Power Dissipation @ TA = 85°C PD867 mW
Thermal Resistance, Junction–to–Air RθJA 75 °C/W
DW Suffix, Surface Mount, Case 751D
Maximum Power Dissipation @ TA = 85°C PD619 mW
Thermal Resistance, Junction–to–Air RθJA 105 °C/W
Operating Junction Temperature TJ150 °C
Operating Ambient Temperature Range TA–40 to +85 °C
Storage Temperature Range Tstg –65 to +150 °C
ELECTRICAL CHARACTERISTICS (VCC = 20 V, R T = 4.7 k, CT = 10 nF, TA = 25°C, unless otherwise noted.)
Characteristic Symbol Min Typ Max Unit
REFERENCE SECTION
Reference Output Voltage (Iref = 1.0 mA)
TA = 25°C
TA = –40° to + 85°C
Vref 5.9
5.82 6.24
–6.5
6.57
V
Line Regulation (VCC = 10 V to 30 V, Iref = 1.0 mA) Regline –1.5 30 mV
Load Regulation (Iref = 1.0 mA to 20 mA) Regload –16 30 mV
Output Short–Circuit Current (Note 3) ISC 40 75 – mA
Reference Under Voltage Lockout Threshold Vth 4.0 4.5 5.0 V
ERROR AMPLIFIER
Input Offset Voltage (TA = –40°to + 85°C) VIO –0.4 10 mV
Input Offset Current (TA = –40°to + 85°C) IIO –8.0 500 nA
Input Bias Current (TA = –40° to + 85°C) IIB ––46 –1000 nA
Input Common Mode Voltage Range VICR (0 V to V ref) V
Open Loop Voltage Gain (VO = 3.0 V, RL = 15 k) AVOL 70 80 – dB
Input Common Mode Rejection Ratio CMRR 55 86 – dB
Power Supply Rejection Ratio (VCC = 10 V to 30 V) PSRR 65 105 – dB
Output Voltage Swing
High State (RL = 15 k to Gnd)
Low State (RL = 17 k to Vref)VOH
VOL 4.6
–5.3
0.5 –
1.0
V
NOTES: 1.The input common mode voltage or input signal voltage should not be allowed to go negative by more than 0.3 V.
2.The compliance voltage must not exceed the range of –0.3 to Vref.
3.Maximum package power dissipation limits must be observed.
MC33033
4MOTOROLA ANALOG IC DEVICE DATA
ELECTRICAL CHARACTERISTICS (continued) (VCC = 20 V, RT = 4.7 k, CT = 10 nF, TA = 25°C, unless otherwise noted.)
Characteristic Symbol Min Typ Max Unit
OSCILLATOR SECTION
Oscillator Frequency fOSC 22 25 28 kHz
Frequency Change with Voltage (VCC = 10 V to 30 V) ∆fOSC/∆V – 0.01 5.0 %
Sawtooth Peak Voltage VOSC(P) – 4.1 4.5 V
Sawtooth Valley V oltage VOSC(V) 1.2 1.5 – V
LOGIC INPUTS
Input Threshold Voltage (Pins 3, 4, 5, 6, 18, 19)
High State
Low State VIH
VIL 3.0
–2.2
1.7 –
0.8
V
Sensor Inputs (Pins 4, 5, 6)
High State Input Current (VIH = 5.0 V)
Low State Input Current (VIL = 0 V) IIH
IIL –150
–600 –70
–337 –20
–150
µA
Forward/Reverse, 60°/120° Select and Output Enable
(Pins 3, 18, 19)
High State Input Current (VIH = 5.0 V)
Low State Input Current (VIL = 0 V) IIH
IIL –75
–300 –36
–175 –10
–75
µA
CURRENT–LIMIT COMPARATOR
Threshold Voltage Vth 85 101 115 mV
Input Common Mode Voltage Range VICR –3.0 – V
Input Bias Current IIB ––0.9 –5.0 µA
OUTPUTS AND POWER SECTIONS
Top Drive Output Sink Saturation (ISink = 25 mA) VCE(sat) – 0.5 1.5 V
Top Drive Output Off–State Leakage (VCE = 30 V) IDRV(leak) –0.06 100 µA
Top Drive Output Switching Time (CL = 47 pF, RL = 1.0 k)
Rise T ime
Fall T ime tr
tf–
–107
26 300
300
ns
Bottom Drive Output Voltage
High State (VCC = 30 V, Isource = 50 mA)
Low State (VCC = 30 V, Isink = 50 mA) VOH
VOL (VCC – 2.0)
–(VCC – 1.1)
1.5 –
2.0
V
Bottom Drive Output Switching T ime (CL = 1000 pF)
Rise T ime
Fall T ime tr
tf–
–38
30 200
200
ns
Under Voltage Lockout
Drive Output Enabled (VCC Increasing)
Hysteresis Vth(on)
VH8.2
0.1 8.9
0.2 10
0.3
V
Power Supply Current ICC –15 22 mA
MC33033
5
MOTOROLA ANALOG IC DEVICE DATA
24
VO, OUTPUT VOLTAGE (V)
VO, OUTPUT VOLTAGE (V)
5.0
µ
s/DIV
AV = +1.0
No Load
TA = 25
°
C
4.5
3.0
1.5
1.0
µ
s/DIV
AV = +1.0
No Load
TA = 25
°
C
3.05
3.0
2.95
Gnd
Vref
IO, OUTPUT LOAD CURRENT (mA)
f, FREQUENCY (Hz)
56
1.0 k
220
200
180
160
140
120
100
80
60
–24
–16
–8.0
0
8.0
16
32
40
48
10M1.0 M100 k10 k
40
240
AVOL, OPEN–LOOP VOLTAGE GAIN (dB)
EXCESS PHASE (DEGREES)
,
φ
Phase
Gain
TA, AMBIENT TEMPERATURE (
°
C)
–55
–4.0
–2.0
0
2.0
125
4.0
1007550250–25
f OSC OSCILLAT OR FREQUENCY CHANGE (%)
,
∆
100
1.0
RT, TIMING RESISTOR (k
Ω
)
100010010
0
10
f OSC OSCILLATOR FREQUENCY (kHz)
,
Figure 1. Oscillator Frequency versus
Timing Resistor Figure 2. Oscillator Frequency Change
versus Temperature
Figure 3. Error Amp Open Loop Gain and
Phase versus Frequency Figure 4. Error Amp Output Saturation
Voltage versus Load Current
Figure 5. Error Amp Small–Signal
Transient Response Figure 6. Error Amp Large–Signal
Transient Response
0
1.0 2.0
0
– 0.8
–1.6
1.6
0.8
5.04.03.00
Vsat, OUTPUT SATURATION VOLTAGE (V)
VCC = 20 V
TA = 25
°
CVCC = 20 V
RT = 4.7 k
CT = 10 nF
Source Saturation
(Load to Ground)
VCC = 20 V
TA = 25
°
C
VCC = 20 V
VO = 3.0 V
RL = 15 k
CL = 100 pF
TA = 25
°
CSink Saturation
(Load to V ref)
CT = 1.0 nF
CT = 10 nF
CT = 100 nF
MC33033
6MOTOROLA ANALOG IC DEVICE DATA
, OUTPUT SATURATION VOLTAGE (V)Vsat
0
ISink, SINK CURRENT (mA)
040302010
1.2
0.8
0.4
0
TA, AMBIENT TEMPERATURE (
°
C)
–25
–40
–20
–55 0
40
20
125100755025
NORMALIZED REFERENCE VOLT AGE CHANGE (mV)
∆
Vref,
0
Iref, REFERENCE OUTPUT SOURCE CURRENT (mA)
0
605040302010
–24
–20
–4.0
–8.0
– 12
– 16
Vref, REFERENCE OUTPUT VOLTAGE CHANGE (mV)
∆
Figure 7. Reference Output Voltage Change
versus Output Source Current Figure 8. Reference Output Voltage versus
Supply Voltage
Figure 9. Reference Output Voltage
versus Temperature Figure 10. Output Duty Cycle versus
PWM Input Voltage
Figure 11. Bottom Drive Response Time versus
Current Sense Input Voltage Figure 12. Top Drive Output Saturation Voltage
versus Sink Current
00
7.0
00
VCC, SUPPLY VOLTAGE (V)
6.0
40302010
5.0
4.0
3.0
2.0
1.0
Vref, REFERENCE OUTPUT VOL TAGE (V)
5.04.03.02.01.0
100
80
60
40
20
PWM INPUT VOLTAGE (V)
OUTPUT DUTY CYCLE (%)
0
VSense, CURRENT SENSE INPUT VOLTAGE (NORMALIZED TO Vth)
50
100
150
200
250
1.0 2.0 3.0 4.0 5.0 7.0 8.0 10
tHL, BOTTOM DRIVE RESPONSE TIME (ns)
No Load
TA = 25
°
C
VCC = 20 V
TA = 25
°
C
VCC = 20 V
RL =
1
CL = 1.0 nF
TA = 25
°
C
VCC = 20 V
RT = 4.7 k
CT = 10 nF
TA = 25
°
C
VCC = 20 V
No Load
VCC = 20 V
TA = 25
°
C
6.0 9.0
MC33033
7
MOTOROLA ANALOG IC DEVICE DATA
Gnd
VCC
–2.0
40
0
IO, OUTPUT LOAD CURRENT (mA)
00
–1.0
2.0
1.0
806020
, OUTPUT SATURATION VOLTAGE (V)
sat
50 ns/DIV
VCC = 20 V
CL = 15 pF
TA = 25
°
C
50 ns/DIV
VCC = 20 V
CL = 1.0 nF
TA = 25
°
C
50 ns/DIV
VCC = 20 V
RL = 1.0 k
CL = 15 pF
TA = 25
°
C
Figure 13. Top Drive Output Waveform Figure 14. Bottom Drive Output Waveform
Figure 15. Bottom Drive Output Waveform Figure 16. Bottom Drive Output Saturation
Voltage versus Load Current
Figure 17. Supply Current versus Voltage
VCC, SUPPLY VOLTAGE (V)
00
20
18
16
14
12
10
8.0
6.0
4.0
2.0
30252015105.0
CC, POWER SUPPL Y CURRENT (mA)
Sink Saturation
(Load to VCC)
Source Saturation
(Load to Ground)
VCC = 20 V
TA = 25
°
C
RT = 4.7 k
CT = 10 nF
Pins 3–6, 12, 13 = Gnd
Pins 18, 19 = Open
TA = 25
°
C
V
OUTPUT VOLTAGE (%)
I
OUTPUT VOLTAGE (%)
OUTPUT VOLTAGE (%)
0
100
0
100
0
100
MC33033
8MOTOROLA ANALOG IC DEVICE DATA
PIN FUNCTION DESCRIPTION
Pin Symbol Description
1, 2, 20 BT, AT, CTThese three open collector Top Drive Outputs are designed to drive the external upper
power switch transistors.
3 Fwd//Rev The Forward/Reverse Input is used to change the direction of motor rotation.
4, 5, 6 SA, SB, SCThese three Sensor Inputs control the commutation sequence.
7Reference Output This output provides charging current for the oscillator timing capacitor CT and a
reference for the Error Amplifier. It may also serve to furnish sensor power.
8 Oscillator The Oscillator frequency is programmed by the values selected for the timing
components, RT and CT.
9Error Amp Noninverting Input This input is normally connected to the speed set potentiometer.
10 Error Amp Inverting Input This input is normally connected to the Error Amp Output in open loop applications.
11 Error Amp Out/PWM Input This pin is available for compensation in closed loop applications.
12 Current Sense Noninverting Input A 100 mV signal, with respect to Pin 13, at this input terminates output switch conduction
during a given oscillator cycle. This pin normally connects to the top side of the current
sense resistor.
13 Gnd This pin supplies a separate ground return for the control circuit and should be
referenced back to the power source ground.
14 VCC This pin is the positive supply of the control IC. The controller is functional over a VCC
range of 10 to 30 V.
15, 16, 17 CB, BB, ABThese three totem pole Bottom Drive Outputs are designed for direct drive of the external
bottom power switch transistors.
18 60°/120° Select The electrical state of this pin configures the control circuit operation for either 60°
(high state) or 120° (low state) sensor electrical phasing inputs.
19 Output Enable A logic high at this input causes the motor to run, while a low causes it to coast.
MC33033
9
MOTOROLA ANALOG IC DEVICE DATA
INTRODUCTION
The MC33033 is one of a series of high performance
monolithic dc brushless motor controllers produced by
Motorola. It contains all of the functions required to
implement a limited–feature, open loop, three or four phase
motor control system. Constructed with Bipolar Analog
technology, it offers a high degree of performance and
ruggedness in hostile industrial environments.The MC33033
contains a rotor position decoder for proper commutation
sequencing, a temperature compensated reference capable
of supplying sensor power, a frequency programmable
sawtooth oscillator, a fully accessible error amplifier, a pulse
width modulator comparator, three open collector top drive
outputs, and three high current totem pole bottom driver
outputs ideally suited for driving power MOSFETs.
Included in the MC33033 are protective features
consisting of undervoltage lockout, cycle–by–cycle current
limiting with a latched shutdown mode, and internal thermal
shutdown.
Typical motor control functions include open loop speed
control, forward or reverse rotation, and run enable. In
addition, the MC33033 has a 60°/120°select pin which
configures the rotor position decoder for either 60° or 120°
sensor electrical phasing inputs.
FUNCTIONAL DESCRIPTION
A representative internal block diagram is shown in
Figure 18, with various applications shown in Figures 34, 36,
37, 41, 43, and 44. A discussion of the features and function
of each of the internal blocks given below and referenced to
Figures 18 and 36.
Rotor Position Decoder
An internal rotor position decoder monitors the three
sensor inputs (Pins 4, 5, 6) to provide the proper sequencing
of the top and bottom drive outputs. The Sensor Inputs are
designed to interface directly with open collector type Hall
Effect switches or opto slotted couplers. Internal pull–up
resistors are included to minimize the required number of
external components. The inputs are TTL compatible, with
their thresholds typically at 2.2 V. The MC33033 series is
designed to control three phase motors and operate with four
of the most common conventions of sensor phasing. A
60°/120°Select (Pin 18) is conveniently provided which
affords the MC33033 to configure itself to control motors
having either 60°, 120°, 240° or 300° electrical sensor
phasing. With three Sensor Inputs there are eight possible
input code combinations, six of which are valid rotor
positions. The remaining two codes are invalid and are
usually caused by an open or shorted sensor line. With six
valid input codes, the decoder can resolve the motor rotor
position to within a window of 60 electrical degrees.
The Forward/Reverse input (Pin 3) is used to change the
direction of motor rotation by reversing the voltage across the
stator winding. When the input changes state, from high to
low with a given sensor input code (for example 100), the
enabled top and bottom drive outputs with the same alpha
designation are exchanged (A T to AB, BT to BB, CT to CB). In
effect the commutation sequence is reversed and the motor
changes directional rotation.
Motor on/off control is accomplished by the Output Enable
(Pin19). When left disconnected, an internal pull–up resistor
to a positive source enables sequencing of the top and
bottom drive outputs. When grounded, the Top Drive Outputs
turn off and the bottom drives are forced low, causing the
motor to coast.
The commutation logic truth table is shown in Figure 19. In
half wave motor drive applications, the Top Drive Outputs are
not required and are typically left disconnected.
Error Amplifier
A high performance, fully compensated Error Amplifier
with access to both inputs and output (Pins 9, 10, 11) is
provided to facilitate the implementation of closed loop motor
speed control. The amplifier features a typical dc voltage gain
of 80 dB, 0.6 MHz gain bandwidth, and a wide input common
mode voltage range that extends from ground to V ref. In most
open loop speed control applications, the amplifier is
configured as a unity gain voltage follower with the
Noninverting Input connected to the speed set voltage
source. Additional configurations are shown in Figures 29
through 33.
Oscillator
The frequency of the internal ramp oscillator is
programmed by the values selected for timing components
RT and CT. Capacitor CT is charged from the Reference
Output (Pin 7) through resistor RT and discharged by an
internal discharge transistor. The ramp peak and valley
voltages are typically 4.1 V and 1.5 V respectively . To provide
a good compromise between audible noise and output
switching efficiency, an oscillator frequency in the range of 20
to 30 kHz is recommended. Refer to Figure 1 for component
selection.
Pulse Width Modulator
The use of pulse width modulation provides an energy
efficient method of controlling the motor speed by varying the
average voltage applied to each stator winding during the
commutation sequence. As CT discharges, the oscillator sets
both latches, allowing conduction of the Top and Bottom
Drive Outputs. The PWM comparator resets the upper latch,
terminating the Bottom Drive Output conduction when the
positive–going ramp of CT becomes greater than the Error
Amplifier output. The pulse width modulator timing diagram is
shown in Figure 20. Pulse width modulation for speed control
appears only at the Bottom Drive Outputs.
Current Limit
Continuous operation of a motor that is severely
over–loaded results in overheating and eventual failure.
This destructive condition can best be prevented with the
use of cycle–by–cycle current limiting. That is, each
on–cycle is treated as a separate event. Cycle–by–cycle
current limiting is accomplished by monitoring the stator
current build–up each time an output switch conducts, and
upon sensing an ove r current condition, immediately turning
off the switch and holding it off for the remaining duration of
MC33033
10 MOTOROLA ANALOG IC DEVICE DATA
60
°
/120
°
Select
Output Enable
12
20
16
Q
S
CT
R
RT
Oscillator
13
ILimit
Error Amp
PWM
Thermal
Shutdown
Reference
Regulator
Lockout
Undervoltage
VCC
42
1
17
Gnd
8
9
11
7
10
3
14
18
19
6
5
Foward/Reverse
Q
R
S
15
Faster
Noninv. Input
Rotor
Position
Decoder
Figure 18. Representative Block Diagram
VM
Top
Drive
Outputs
Bottom
Drive
Outputs
CB
Current Sense
Input
SA
BB
AB
SC
SB
Sensor Inputs
20 k
20 k
20 k
40 k
40 k
40 k
8.9 V
4.5 V
100 mV
Error Amp Out
PWM Input
Sink Only
Positive True
Logic With
Hysteresis
=
Latch
Latch
AT
BT
CT
Reference Output
MC33033
11
MOTOROLA ANALOG IC DEVICE DATA
Figure 19. Three Phase, Six Step Commutation Truth Table (Note 1)
Inputs (Note 2) Outputs (Note 3)
Sensor Electrical Phasing (Note 4) Top Drives Bottom Drives
60°120°Current
SASBSCSASBSCF/R Enable Sense ATBTCTABBBCB
1
1
1
0
0
0
0
1
1
1
0
0
0
0
1
1
1
0
1
1
0
0
0
1
0
1
1
1
0
0
0
0
0
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
0
0
0
0
0
0
0
1
1
1
1
0
1
0
0
1
1
1
1
1
1
0
0
1
0
0
1
1
0
0
0
0
0
0
1
1
1
1
0
0
0
0
(Note 5)
F/R = 1
1
1
1
0
0
0
0
1
1
1
0
0
0
0
1
1
1
0
1
1
0
0
0
1
0
1
1
1
0
0
0
0
0
1
1
1
0
0
0
0
0
0
1
1
1
1
1
1
0
0
0
0
0
0
1
1
0
0
1
1
1
1
1
1
0
0
0
0
1
1
1
1
1
0
0
0
0
1
0
1
1
0
0
0
0
0
0
1
1
0
(Note 5)
F/R = 0
1
00
11
01
01
01
0X
XX
XX
X1
11
11
10
00
00
0(Note 6)
V V V V V V X 0 X 1 1 1 0 0 0 (Note 7)
V V V V V V X 1 1 1 1 1 0 0 0 (Note 8)
NOTES: 1.V = Any one of six valid sensor or drive combinations.
X = Don’t care.
2.The digital inputs (Pins 3, 4, 5, 6, 18, 19) are all TTL compatible. The current sense input (Pin 12) has a 100 mV threshold with respect to Pin 13. A
logic 0 for this input is defined as < 85 mV, and a logic 1 is > 115 mV.
3.The top drive outputs are open collector design and active in the low (0) state.
4.With 60°/120°(Pin 18) in the high (1) state, configuration is for 60° sensor electrical phasing inputs. With Pin 18 in the low (0) state, configuration is
for 120° sensor electrical phasing inputs.
5.Valid 60°or 120° sensor combinations for corresponding valid top and bottom drive outputs.
6.Invalid sensor inputs; All top and bottom drives are off.
7.Valid sensor inputs with enable = 0; All top and bottom drives are off.
8.Valid sensor inputs with enable and current sense = 1; All top and bottom drives are off.
oscillator ramp–up period. The stator current is converted to
a voltage by inserting a ground–referenced sense resistor RS
(Figure 34) in series with the three bottom switch transistors
(Q4, Q5, Q6). The voltage developed across the sense
resistor is monitored by the current sense input (Pin 12), and
compared to the internal 100 mV reference. If the current
sense threshold is exceeded, the comparator resets the
lower latch and terminates output switch conduction. The
value for the sense resistor is:
RS
+
0.1
Istator(max)
The dual–latch PWM configuration ensures that only one
single output conduction pulse occurs during any given
oscillator cycle, whether terminated by the output of the Error
Amplifier or the current limit comparator.
Reference
The on–chip 6.25 V regulator (Pin 7) provides charging
current for the oscillator timing capacitor, a reference for the
Error Amplifier, and can supply 20 mA of current suitable for
directly powering sensors in low voltage applications. In
higher voltage applications it may become necessary to
transfer the power dissipated by the regulator of f the IC. This
is easily accomplished with the addition of an external pass
transistor as shown in Figure 21. A 6.25 V reference level
was chosen to allow implementation of the simpler NPN
circuit, where Vref – VBE exceeds the minimum voltage
required by Hall Effect sensors over temperature. With
proper transistor selection, and adequate heatsinking, up to
one amp of load current can be obtained.
Undervoltage Lockout
A dual Undervoltage Lockout has been incorporated to
prevent damage to the IC and the external power switch
transistors. Under low power supply conditions, it guarantees
that the IC and sensors are fully functional, and that there is
sufficient Bottom Drive Output voltage. The positive power
supply to the IC (VCC) is monitored to a threshold of 8.9 V.
This level ensures sufficient gate drive necessary to attain
low RDS(on) when interfacing with standard power MOSFET
devices. When directly powering the Hall sensors from the
reference, improper sensor operation can result if the
reference output voltage should fall below 4.5 V. If one or
both of the comparators detects an undervoltage condition,
the top drives are turned off and the Bottom Drive Outputs
are held in a low state. Each of the comparators contain
hysteresis to prevent oscillations when crossing their
respective thresholds.
MC33033
12 MOTOROLA ANALOG IC DEVICE DATA
Figure 20. PWM Timing Diagram
Current Sense
Input
Capacitor CT
Error Amp Out/
PWM Input
Latch “Set”
Inputs
Top Drive
Outputs
Bottom Drive
Outputs
Figure 21. Reference Output Buffers
The NPN circuit is recommended for powering Hall or opto sensors, where the
output voltage temperature coefficient is not critical. The PNP circuit is slightly
more complex, but also more accurate. Neither circuit has current limiting.
To
Control
Circuitry
6.25 V
Sensor
Power
≈
5.6 V
MPS
U51A
Vin 14
UVLO
MPS
U01A
Vin
To Control Circuitry
and Sensor Power
6.25 V
UVLO
14
36
REF
7
0.1
REF
7
Load
Figure 22. High Voltage Interface with
NPN Power Transistors Figure 23. High Voltage Interface with
N–Channel Power MOSFETs
Transistor Q1 is a common base stage used to level shift from VCC to the high
motor voltage, VM. The collector diode is required if VCC is present while VM
is low.
Load
Q4
VM
VCC Q2
Q3
Q1
17
20
1
2AT
BT
CT
Rotor
Position
Decoder
16
15
VCC = 12 V
1N4744
VM = 170 VVBoost
1.0 k 5
4
6
2
4.7 k
1.0 M
1
MOC8204
Optocoupler
17
20
1
2AT
BT
CT
Rotor
Position
Decoder
16
15
MC33033
13
MOTOROLA ANALOG IC DEVICE DATA
100 mV
12
17
16
15
Figure 24. Current Waveform Spike Suppression Figure 25. MOSFET Drive Precautions
The addition of the RC filter will eliminate current–limit instability caused
by the leading edge spike on the current waveform. Resistor RS should
be a low inductance type.
Series gate resistor Rg will damp any high frequency oscillations caused
by the MOSFET input capacitance and any series wiring induction in the
gate–source circuit. Diode D is required if the negative current into the
Bottom Drive Outputs exceeds 50 mA.
CRS
R
100 mV
12
D = 1N5819
D
Rg
Rg
D
Rg
D
17
16
15
100 mV
12
17
16
15
100 mV
12
17
16
15
Figure 26. Bipolar Transistor Drive Figure 27. Current Sensing Power MOSFETs
D
GS
RS
MK
SENSEFET
The totem pole output can furnish negative base current for
enhanced transistor turn–off, with the addition of capacitor C. Virtually lossless current sensing can be achieved with the
implementation of SENSEFET power switches.
t
+
0
–
IB
Base Charge
Removal
VPin 9
[
RS
@
I
pk
@
R
DS(on)
rDM(on)
)
R
S
Power Ground:
To Input Source Return
If : SENSEFET = MPT10N10M
RS = 200
Ω
, 1/4 W
Then :
VPin 9
[
0.75 Ipk
13 Gnd
C
C
C
Figure 28. High Voltage Boost Supply Figure 29. Differential Input Speed Controller
This circuit generates VBoost for Figure 23.
1.0
µ
/200 V VBoost
*
22
1*
1N5352A
MC1455
5
2
6
0.001 18 k
3
VM + 12
VC = 12 V
4
VM = 170 V
R
SQ
* = MUR115
8
Boost Current (mA)
VM + 4.0 40
760
20
VM + 8.0
VBoost V oltage (V)
R4
R2
R1
R3
40 k
11
VB
VA
REF
PWM
EA
7
19
9
10
VPin 11
+
VA
ǒ
R3
)
R4
R1
)
R2
Ǔ
R2
R3–
ǒ
R4
R3VB
Ǔ
MC33033
14 MOTOROLA ANALOG IC DEVICE DATA
11
PWM
EA
7
19
9
10
Resistor R1 with capacitor C sets the acceleration time constant while R2
controls the deceleration. The values of R1 and R2 should be at least ten times
greater than the speed set potentiometer to minimize time constant variations
with different speed settings.
The SN74LS145 is an open collector BCD to One of Ten decoder. When
connected as shown, input codes 0000 through 1001 steps the PWM in
increments of approximately 10% from 0 to 90% on–time. Input codes 1010
through 1 11 1 will produce 100% on–time or full motor speed.
Figure 30. Controlled Acceleration/Deceleration Figure 31. Digital Speed Controller
R1
EA
R2
7
PWM
C
Enable
Increase
Speed
19
10
9
11
16
VCC
Gnd Q0
240.4 k
8
P0
BCD
Inputs
Q9
Q8
Q7
Q6
Q5
Q4
Q3
Q2
Q1
P3
P2
P1
100 k
1
51.3 k
3
4
5
6
7
63.6 k
77.6 k
92.3 k
108 k
9126 k
11
145 k
166 k
10
5.0 V
SN74LS145
REF REF
40 k
40 k
15
14
13
12
11
REF
PWM
EA
7
19
9
10
40 k
11
REF
PWM
EA
7
19
9
10
The rotor position sensors can be used as a tachometer . By differentiating the
positive–going edges and then integrating them over time, a voltage
proportional to speed can be generated. The error amp compares this voltage
to that of the speed set to control the PWM.
This circuit can control the speed of a cooling fan proportional to the difference
between the sensor and set temperatures. The control loop is closed as the
forced air cools the NTC thermistor. For controlled heating applications,
exchange the positions of R1 and R2.
Figure 32. Closed Loop Speed Control Figure 33. Closed Loop Temperature Control
0.22
1.0 M
0.1
100 k
0.01
10 k
10 k
10 M
To Sensor
Input (Pin 4)
Increase
Speed
T
R1
R6
R5R2
R3
R4
VB
+
Vref
ǒ
R5
R6
)
1
Ǔ
R3
§§
R6
ø
R6
VPin11
+
Vref
ǒ
R3
)
R4
R1
)
R2
Ǔ
R2
R3–
ǒ
R4
R3VB
Ǔ
40 k
Drive Outputs
The three Top Drive Outputs (Pins 1, 2, 20) are open
collector NPN transistors capable of sinking 50 mA with a
minimum breakdown of 30 V. Interfacing into higher voltage
applications is easily accomplished with the circuits shown in
Figures 22 and 23.
The three totem pole Bottom Drive Outputs (Pins 15, 16,
17) are particularly suited for direct drive of N–Channel
MOSFETs or NPN bipolar transistors (Figures 24, 25, 26,
and 27). Each output is capable of sourcing and sinking up
to 100 mA.
Thermal Shutdown
Internal thermal shutdown circuity is provided to protect
the IC in the event the maximum junction temperature is
exceeded. When activated, typically at 170°C, the IC acts
as though the regulator was disabled, in turn shutting down
the IC.
SYSTEM APPLICATIONS
Three Phase Motor Commutation
The three phase application shown in Figure 34 is an open
loop motor controller with full wave, six step drive. The upper
power switch transistors are Darlington PNPs while the lower
switches are N–Channel power MOSFETs. Each of these
devices contains an internal parasitic catch diode that is used
to return the stator inductive energy back to the power supply .
The outputs are capable of driving a delta or wye connected
stator, and a grounded neutral wye if split supplies are used.
At any given rotor position, only one top and one bottom
power switch (of different totem poles) is enabled. This
configuration switches both ends of the stator winding from
supply to ground which causes the current flow to be
bidirectional or full wave. A leading edge spike is usually
present on the current waveform and can cause a
current–limit error. The spike can be eliminated by adding an
RC filter in series with the Current Sense Input. Using a low
inductance type resistor for RS will also aid in spike reduction.
Figure 35 shows the commutation waveforms over two
electrical cycles. The first cycle (0° to 360°) depicts motor
operation at full speed while the second cycle (360° to 720°)
shows a reduced speed with about 50% pulse width
modulation. The current waveforms reflect a constant torque
load and are shown synchronous to the commutation
frequency for clarity.
MC33033
15
MOTOROLA ANALOG IC DEVICE DATA
60
°
/120
°
Figure 34. Three Phase, Six Step, Full Wave Motor Controller
RS
R
C
Q5
Q6
Q4
VM
S
Motor
A
Q3
S
C
B
Q1
Q2
Enable
12
20
16
Q
S
CT
R
RT
Oscillator
13
ILimit
Error Amp
PWM
Thermal
Shutdown
Reference
Regulator
Lockout
Undervoltage
VM
42
1
17
Gnd
8
9
11
7
10
3
14
18
19
6
5
FWR/REV
Q
R
S
15
Faster
Speed
Set
Rotor
Position
Decoder
N
N
MC33033
16 MOTOROLA ANALOG IC DEVICE DATA
Figure 35. Three Phase, Six Step, Full Wave Commutation Waveforms
Rotor Electrical Position (Degrees)
100 000001
011111110
100
000001011111110
720660600540
480420360300240180120600
SA
SB
SC
Code
SC
SB
Code
SA
Sensor Inputs
60°/120°
Select Pin
Open
Sensor Inputs
60°/120°
Select Pin
Grounded
AB
BB
Q2 + Q6
CB
Q2 + Q4Q3 + Q4Q3 + Q5Q1 + Q5Q1 + Q6
Bottom Drive
Outputs
Q2 + Q6Q2 + Q4Q3 + Q4Q3 + Q5
Motor Drive
Current B
FWD/REV = 1
C
–
O
+
–
O
+
Conducting
Power Switch
Transistors
Q1 + Q5
Top Drive
Outputs
Q1 + Q6
A
BT
AT
CT
–
O
+
100 110 001011 001011110100010 010 101101
Reduced Speed (
≈
50% PWM)Full Speed (No PWM)
MC33033
17
MOTOROLA ANALOG IC DEVICE DATA
Figure 36 shows a three phase, three step, half wave motor
controller. This configuration is ideally suited for automobile
and other low voltage applications since there is only one
power switch voltage drop in series with a given stator
winding. Current flow is unidirectional or half wave because
only one end of each winding is switched. The stator flyback
voltage is clamped by a single zener and three diodes.
60
°
/120
°
Figure 36. Three Phase, Three Step, Half Wave Motor Controller Motor
Enable
12
20
16
Q
S
CT
R
RT
Oscillator
13
ILimit
Error Amp
PWM
Thermal
Shutdown
Reference
Regulator
Lockout
Undervoltage
VM
42
1
17
Gnd
8
9
11
7
10
3
14
18
19
6
5
FWR/REV
Q
R
S
15
Faster
SS
VM
Speed
Set
Rotor
Position
Decoder
N
N
MC33033
18 MOTOROLA ANALOG IC DEVICE DATA
Three Phase Closed Loop Controller
The MC33033, by itself, is capable of open loop motor
speed control. For closed loop speed control, the MC33033
requires an input voltage proportional to the motor speed.
Traditionally this has been accomplished by means of a
tachometer to generate the motor speed feedback voltage.
Figure 37 shows an application whereby an MC33039,
powered from the 6.25 V reference (Pin 7) of the MC33033,
is used to generate the required feedback voltage without
the need of a costly tachometer. The same Hall sensor
signals used by the MC33033 for rotor position decoding are
utilized by the MC33039. Every positive or negative going
transition of the Hall sensor signals on any of the sensor
lines causes the MC33039 to produce an output pulse of
defined amplitude and time duration, as determined by the
external resistor R1 and capacitor C1. The resulting output
train of pulses present at Pin 5 of the MC33039 are
integrated by the Error Amplifier of the MC33033 configured
as an integrator, to produce a dc voltage level which is
proportional to the motor speed. This speed proportional
voltage establishes the PWM reference level at Pin 11 of the
MC33033 motor controller and completes or closes the
feedback loop. The MC33033 ouputs drive a TMOS power
MOSFET 3–phase bridge. High current can be expected
during conditions of start–up and when changing direction of
the motor.
The system shown in Figure 37 is designed for a motor
having 120/240 degrees Hall sensor electrical phasing. The
system can easily be modified to accommodate 60/300
degree Hall sensor electrical phasing by removing the
jumper (J1) at Pin 18 of the MC33033.
Figure 37. Closed Loop Brushless DC Motor Control
With the MC33033 Using the MC33039
Motor
TP2
0.05/1.0 W
0.1 33
TP1
1.0 k
VM (18 to 30 V)
1000
0.1
1.1 k
Close Loop
0.1
1.0 M
0.01
Speed
Faster
5.1 k
F/R
Enable
1.0 k
470
470
470
1N5819
1.1 k 1.1 k
1.0 k
1
2
3
4
8
7
6
5
1
2
3
4
9
5
6
7
8
10
20
19
18
17
16
15
14
13
12
11
MC33033
MC33039
1.0 M
R1
750 pF
C1
10 k
SS
4.7 k
J1
100 k
100
330
0.11N4742
N
N
MC33033
19
MOTOROLA ANALOG IC DEVICE DATA
Sensor Phasing Comparison
There are four conventions used to establish the relative
phasing of the sensor signals in three phase motors. With six
step drive, an input signal change must occur every 60
electrical degrees, however, the relative signal phasing is
dependent upon the mechanical sensor placement. A
comparison of the conventions in electrical degrees is shown
in Figure 38. From the sensor phasing table (Figure 39), note
that the order of input codes for 60° phasing is the reverse of
300°. This means the MC33033, when the 60°/120° select
(Pin 18) and the FWD/REV (Pin 3) both in the high state
(open), is configured to operate a 60° sensor phasing motor
in the forward direction. Under the same conditions a 300°
sensor phasing motor would operate equally well but in the
reverse direction. One would simply have to reverse the
FWD/REV switch (FWD/REV closed) in order to cause the
300°motor to also operate in the same direction. The same
difference exists between the 120° and 240° conventions.
Figure 38. Sensor Phasing Comparison
Rotor Electrical Position (Degrees)
300°
240°
720660600540480420360300240180120600
SB
SA
120°
60°
SC
SA
SB
SC
SC
SB
SA
SC
SB
SA
Sensor Electrical Phasing
Figure 39. Sensor Phasing Table
Sensor Electrical Phasing (Degrees)
60°120°240°300°
SASBSCSASBSCSASBSCSASBSC
100101110111
110100100110
1111101011 0 0
011010001000
001011011001
000001010011
In this data sheet, the rotor position has always been given
in electrical degrees since the mechanical position is a
function of the number of rotating magnetic poles. The
relationship between the electrical and mechanical position is:
Electrical Degrees
+
Mechanical Degrees
ǒ
#Rotor Poles
2
Ǔ
An increase in the number of magnetic poles causes more
electrical revolutions for a given mechanical revolution.
General purpose three phase motors typically contain a four
pole rotor which yields two electrical revolutions for one
mechanical.
Two and Four Phase Motor Commutation
The MC33033 configured for 60° sensor inputs is capable
of providing a four step output that can be used to drive two or
four phase motors. The truth table in Figure 40 shows that by
connecting sensor inputs SB and SC together , it is possible to
truncate the number of drive output states from six to four.
The output power switches are connected to BT, CT, BB, and
CB. Figure 41 shows a four phase, four step, full wave motor
control application. Power switch transistors Q1 through Q8
are Darlington type, each with an internal parasitic catch
diode. With four step drive, only two rotor position sensors
spaced at 90 electrical degrees are required. The
commutation waveforms are shown in Figure 42.
Figure 43 shows a four phase, four step, half wave motor
controller . It has the same features as the circuit in Figure 36,
except for the deletion of speed adjust.
Figure 40. Two and Four Phase, Four Step,
Commutation Truth Table
MC33033 (60°/120° Select Pin Open)
Inputs Outputs
Sensor Electrical
Spacing* = 90°Top Drives Bottom Drives
SASBF/R BTCTBBCB
1
1
0
0
0
1
1
0
1
1
1
1
1
0
1
1
1
1
0
1
0
0
0
1
1
0
0
0
1
1
0
0
0
1
1
0
0
0
0
0
1
1
1
0
0
1
1
1
0
1
0
0
0
0
1
0
*With MC33033 sensor input SB connected to SC
MC33033
20 MOTOROLA ANALOG IC DEVICE DATA
Figure 41. Four Phase, Four Step, Full Wave Controller
CT
RT
VM
Enable
FWR/REV
8
11
10
9
7
14
19
18
3
6
5
4
12
15
16
Lockout
17
Rotor
Undervoltage
20
1
Motor
2
Reference
Thermal
Oscillator
13 Gnd
Q5
Q1
Q2
Q6
Q7
Q3
Q4
Q8
VM
R
CRS
Position
Decoder
Shutdown
Regulator
Error Amp
PWM
ILimit
S
RQ
R
SQ
A
B
D
C
S
SN
N
MC33033
21
MOTOROLA ANALOG IC DEVICE DATA
Conducting
Power Switch
Transistors
A
SA
SB
Code
Q3 + Q5
Rotor Electrical Position (Degrees)
FWD/REV = 1
–
O
+
–
–
D
C
+
O
–
O
+
B
+
CB
O
BB
CT
BT
Q2 + Q8
Q1 + Q7
Q4 + Q6
Q3 + Q5
Q2 + Q8
Q1 + Q7
Q4 + Q6
0001111000011010
Motor Drive
Current
Bottom Drive
Outputs
Top Drive
Outputs
Sensor Inputs
60°/120°
Select Pin
Open
180 270 360 450 540 630 720090
Figure 42. Four Phase, Four Step, Full Wave Commutation Waveforms
Full Speed (No PWM)
MC33033
22 MOTOROLA ANALOG IC DEVICE DATA
CT
RT
VM
Enable
FWR/REV
8
11
10
9
7
14
19
18
3
6
5
4
12
15
16
Lockout
17
Rotor
Undervoltage
20
1
2
Reference
Thermal
Oscillator
13 Gnd
R
C
Position
Decoder
Shutdown
Regulator
Error Amp
PWM
ILimit
S
RQ
R
SQ
Figure 43. Four Phase, Four Step, Half Wave Motor Controller
VM
RS
Motor
S
S
N
N
MC33033
23
MOTOROLA ANALOG IC DEVICE DATA
Brush Motor Control
Though the MC33033 was designed to control brushless
dc motors, it may also be used to control dc brush–type
motors. Figure 44 shows an application of the MC33033
driving a H–bridge affording minimal parts count to operate a
brush–type motor. Key to the operation is the input sensor
code [100] which produces a top–left (Q1) and a bottom–right
(Q3) drive when the controller’s Forward/Reverse pin is at
logic [1]; top–right (Q4), bottom–left (Q2) drive is realized
when the Forward/Reverse pin is at logic [0]. This code
supports the requirements necessary for H–bridge drive
accomplishing both direction and speed control.
The controller functions in a normal manner with a pulse
width modulated frequency of approximately 25 kHz. Motor
speed is controlled by adjusting the voltage presented to the
noninverting input of the Error Amplifier establishing the
PWM′s slice or reference level. Cycle–by–cycle current
limiting of the motor current is accomplished by sensing the
voltage (100 mV threshold) across the RS resistor to ground
of the H–bridge motor current. The over current sense circuit
makes it possible to reverse the direction of the motor , on the
fly , using the normal Forward/Reverse switch, and not have to
completely stop before reversing.
LAYOUT CONSIDERATIONS
Do not attempt to construct any of the motor control
circuits on wire–wrap or plug–in prototype boards. High
frequency printed circuit layout techniques are imperative to
prevent pulse jitter . This is usually caused by excessive noise
pick–up imposed on the current sense or error amp inputs.
The printed circuit layout should contain a ground plane with
low current signal and high drive and output buffer grounds
returning on separate paths back to the power supply input
filter capacitor VM. Ceramic bypass capacitors (0.01 µF)
connected close to the integrated circuit at VCC, Vref and
error ampliflier noninverting input may be required depending
upon circuit layout. This provides a low impedance path for
filtering any high frequency noise. All high current loops
should be kept as short as possible using heavy copper runs
to minimize radiated EMI.
Figure 44. H–Bridge Brush–Type Controller
Enable
RS
1.0 k
12
20
16
Q
S
0.005
R
10 k
Oscillator
13
ILimit
Error Amp
PWM
Thermal
Shutdown
Reference
Regulator
Lockout
Undervoltage
+12 V
4
Rotor
Position
Decoder
2
1
17
Gnd
8
9
11
7
10
3
14
18
19
6
5
FWR/REV
Q
R
S
15
0.1
10 k
Faster
0.001
22
22
DC Brush
Motor
M
+12 V
1.0 k
1.0 k
Q1*
Q2*
Q4*
Q3*
MC33033
24 MOTOROLA ANALOG IC DEVICE DATA
P SUFFIX
PLASTIC PACKAGE
CASE 738–03
ISSUE E
1.070
0.260
0.180
0.022
0.070
0.015
0.140
15
°
0.040
1.010
0.240
0.150
0.015
0.050
0.008
0.110
0
°
0.020
25.66
6.10
3.81
0.39
1.27
0.21
2.80
0
°
0.51
27.17
6.60
4.57
0.55
1.77
0.38
3.55
15
°
1.01
0.050 BSC
0.100 BSC
0.300 BSC
1.27 BSC
2.54 BSC
7.62 BSC
MIN MINMAX MAX
INCHES MILLIMETERS
DIM
A
B
C
D
E
F
G
J
K
L
M
N
NOTES:
1. DIMENSIONING AND TOLERANCING PER ANSI
Y14.5M, 1982.
2. CONTROLLING DIMENSION: INCH.
3. DIMENSION L TO CENTER OF LEAD WHEN
FORMED PARALLEL.
4. DIMENSION B DOES NOT INCLUDE MOLD
FLASH.
–A–
C
K
N
E
GF
D 20 PL
J 20 PL
L
M
–T–
SEATING
PLANE
110
1120
0.25 (0.010) T A
M M 0.25 (0.010) T B
M M
B
DW SUFFIX
PLASTIC PACKAGE
CASE 751D–04
(SO–20L)
ISSUE E
MIN MINMAX MAX
MILLIMETERS INCHES
DIM
A
B
C
D
F
G
J
K
M
P
R
0.510
0.299
0.104
0.019
0.035
0.012
0.009
7
°
0.415
0.029
0.499
0.292
0.093
0.014
0.020
0.010
0.004
0
°
0.395
0.010
12.95
7.60
2.65
0.49
0.90
0.32
0.25
7
°
10.55
0.75
12.65
7.40
2.35
0.35
0.50
0.25
0.10
0
°
10.05
0.25
NOTES:
1. DIMENSIONING AND TOLERANCING PER
ANSI Y14.5M, 1982.
2. CONTROLLING DIMENSION: MILLIMETER.
3. DIMENSIONS A AND B DO NOT INCLUDE
MOLD PROTRUSION.
4. MAXIMUM MOLD PROTRUSION 0.150
(0.006) PER SIDE.
5. DIMENSION D DOES NOT INCLUDE
DAMBAR PROTRUSION. ALLOWABLE
DAMBAR PROTRUSION SHALL BE 0.13
(0.005) TOTAL IN EXCESS OF D DIMENSION
AT MAXIMUM MATERIAL CONDITION.
1.27 BSC 0.050 BSC
–A–
–B– P 10 PL
110
1120
–T–
D 20 PL
K
C
SEATING
PLANE
R X 45°
M
0.010 (0.25) B
M M
0.010 (0.25) T A B
MS S
G 18 PL
F
J
OUTLINE DIMENSIONS
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*MC33033/D*
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