ISL6612, ISL6613 (R) Data Sheet June 15, 2010 Advanced Synchronous Rectified Buck MOSFET Drivers with Protection Features The ISL6612 and ISL6613 are high frequency MOSFET drivers specifically designed to drive upper and lower power N-Channel MOSFETs in a synchronous rectified buck converter topology. These drivers combined with HIP63xx or ISL65xx Multi-Phase Buck PWM controllers and N-Channel MOSFETs form complete core-voltage regulator solutions for advanced microprocessors. FN9153.9 Features * Pin-to-pin Compatible with HIP6601 SOIC family for Better Performance and Extra Protection Features * Dual MOSFET Drives for Synchronous Rectified Bridge * Advanced Adaptive Zero Shoot-Through Protection - Body Diode Detection - Auto-zero of rDS(ON) Conduction Offset Effect * Adjustable Gate Voltage (5V to 12V) for Optimal Efficiency The ISL6612 drives the upper gate to 12V, while the lower gate can be independently driven over a range from 5V to 12V. The ISL6613 drives both upper and lower gates over a range of 5V to 12V. This drive-voltage provides the flexibility necessary to optimize applications involving trade-offs between gate charge and conduction losses. * 36V Internal Bootstrap Schottky Diode An advanced adaptive zero shoot-through protection is integrated to prevent both the upper and lower MOSFETs from conducting simultaneously and to minimize the dead time. These products add an overvoltage protection feature operational before VCC exceeds its turn-on threshold, at which the PHASE node is connected to the gate of the low side MOSFET (LGATE). The output voltage of the converter is then limited by the threshold of the low side MOSFET, which provides some protection to the microprocessor if the upper MOSFET(s) is shorted during startup. The over-temperature protection feature prevents failures resulting from excessive power dissipation by shutting off the outputs when its junction temperature exceeds +150C (typically). The driver resets once its junction temperature returns to +108C (typically). * Three-State PWM Input for Output Stage Shutdown These drivers also feature a three-state PWM input which, working together with Intersil's multi-phase PWM controllers, prevents a negative transient on the output voltage when the output is shut down. This feature eliminates the Schottky diode that is used in some systems for protecting the load from reversed output voltage events. * Pb-Free Available (RoHS Compliant) * Bootstrap Capacitor Overcharging Prevention * Supports High Switching Frequency (up to 2MHz) - 3A Sinking Current Capability - Fast Rise/Fall Times and Low Propagation Delays * Three-State PWM Input Hysteresis for Applications With Power Sequencing Requirement * Pre-POR Overvoltage Protection * VCC Undervoltage Protection * Over Temperature Protection (OTP) with +42C Hysteresis * Expandable Bottom Copper Pad for Enhanced Heat Sinking * Dual Flat No-Lead (DFN) Package - Near Chip-Scale Package Footprint; Improves PCB Efficiency and Thinner in Profile Applications * Core Regulators for Intel(R) and AMD(R) Microprocessors * High Current DC/DC Converters * High Frequency and High Efficiency VRM and VRD Related Literature * Technical Brief TB363 "Guidelines for Handling and Processing Moisture Sensitive Surface Mount Devices (SMDs)" * Technical Brief TB417 for Power Train Design, Layout Guidelines, and Feedback Compensation Design 1 CAUTION: These devices are sensitive to electrostatic discharge; follow proper IC Handling Procedures. 1-888-INTERSIL or 1-888-468-3774 | Intersil (and design) is a registered trademark of Intersil Americas Inc. Copyright Intersil Americas Inc. 2005, 2006, 2007, 2010. All Rights Reserved All other trademarks mentioned are the property of their respective owners. ISL6612, ISL6613 Ordering Information PART NUMBER PART MARKING TEMP. RANGE (C) PACKAGE PKG. DWG. # ISL6612CBZ (Note 2) 6612 CBZ 0 to +85 8 Ld SOIC (Pb-Free) M8.15 ISL6612CBZ-T (Notes 1, 2) 6612 CBZ 0 to +85 8 Ld SOIC (Pb-Free) M8.15 ISL6612CBZA (Note 2) 6612 CBZ 0 to +85 8 Ld SOIC (Pb-Free) M8.15 ISL6612CBZA-T (Notes 1, 2) 6612 CBZ 0 to +85 8 Ld SOIC (Pb-Free) M8.15 ISL6612CRZ (Note 2) 612Z 0 to +85 10 Ld 3x3 DFN (Pb-Free) L10.3x3 ISL6612CRZ-T (Notes 1, 2) 612Z 0 to +85 10 Ld 3x3 DFN (Pb-Free) L10.3x3 ISL6612ECB-T (Note 1) ISL66 12ECB 0 to +85 8 Ld EPSOIC M8.15B ISL6612ECBZ (Note 2) 6612 ECBZ 0 to +85 8 Ld EPSOIC (Pb-Free) M8.15B ISL6612ECBZ-T (Notes 1, 2) 6612 ECBZ 0 to +85 8 Ld EPSOIC (Pb-Free) M8.15B ISL6612EIBZ (Note 2) 6612 EIBZ -40 to +85 8 Ld EPSOIC (Pb-Free) M8.15B ISL6612EIBZ-T (Notes 1, 2) 6612 EIBZ -40 to +85 8 Ld EPSOIC (Pb-Free) M8.15B ISL6612IBZ (Note 2) 6612 IBZ -40 to +85 8 Ld SOIC (Pb-Free) M8.15 ISL6612IBZ-T (Notes 1, 2) 6612 IBZ -40 to +85 8 Ld SOIC (Pb-Free) M8.15 ISL6612IRZ (Note 2) 12IZ -40 to +85 10 Ld 3x3 DFN (Pb-Free) L10.3x3 ISL6612IRZ-T (Notes 1, 2) 12IZ -40 to +85 10 Ld 3x3 DFN (Pb-Free) L10.3x3 ISL6613CBZ (Note 2) 6613 CBZ 0 to +85 8 Ld SOIC (Pb-Free) M8.15 ISL6613CBZ-T (Notes 1, 2) 6613 CBZ 0 to +85 8 Ld SOIC (Pb-Free) M8.15 ISL6613CRZ (Note 2) 613Z 0 to +85 10 Ld 3x3 DFN (Pb-Free) L10.3x3 ISL6613CRZ-T (Notes 1, 2) 613Z 0 to +85 10 Ld 3x3 DFN (Pb-Free) L10.3x3 ISL6613ECBZ (Note 2) 6613 ECBZ 0 to +85 8 Ld EPSOIC (Pb-Free) M8.15B ISL6613ECBZ-T (Notes 1, 2) 6613 ECBZ 0 to +85 8 Ld EPSOIC (Pb-Free) M8.15B ISL6613EIBZ (Note 2) 6613 EIBZ -40 to +85 8 Ld EPSOIC (Pb-Free) M8.15B ISL6613EIBZ-T (Notes 1, 2) 6613 EIBZ -40 to +85 8 Ld EPSOIC (Pb-Free) M8.15B ISL6613IBZ (Note 2) 6613 IBZ -40 to +85 8 Ld SOIC (Pb-Free) M8.15 ISL6613IBZ-T (Notes 1, 2) 6613 IBZ -40 to +85 8 Ld SOIC (Pb-Free) M8.15 ISL6613IRZ (Note 2) 13IZ -40 to +85 10 Ld 3x3 DFN (Pb-Free) L10.3x3 ISL6613IRZ-T (Notes 1, 2) 13IZ -40 to +85 10 Ld 3x3 DFN (Pb-Free) L10.3x3 NOTES: 1. Please refer to TB347 for details on reel specifications. 2. These Intersil Pb-free plastic packaged products employ special Pb-free material sets, molding compounds/die attach materials, and 100% matte tin plate plus anneal (e3 termination finish, which is RoHS compliant and compatible with both SnPb and Pb-free soldering operations). Intersil Pb-free products are MSL classified at Pb-free peak reflow temperatures that meet or exceed the Pb-free requirements of IPC/JEDEC J STD020. 3. For Moisture Sensitivity Level (MSL), please see device information page for ISL6612, ISL6613. For more information on MSL please see techbrief TB363. 2 FN9153.9 June 15, 2010 ISL6612, ISL6613 Pinouts ISL6612CB, ISL6613CB (8 LD SOIC) ISL6612ECB, ISL6613ECB (8 LD EPSOIC) TOP VIEW UGATE 1 BOOT 2 PWM GND 8 ISL6612CR, ISL6613CR (10 LD 3x3 DFN) TOP VIEW PHASE 7 PVCC 3 6 VCC 4 5 LGATE GND Block Diagram 1 UGATE BOOT 2 N/C 3 PWM 4 GND 5 10 PHASE 9 PVCC GND 8 N/C 7 VCC 6 LGATE ISL6612 AND ISL6613 UVCC BOOT VCC OTP AND PRE-POR OVP FEATURES +5V 10k POR/ PWM UGATE SHOOTTHROUGH PROTECTION PHASE (LVCC) PVCC CONTROL 8k LOGIC UVCC = VCC FOR ISL6612 UVCC = PVCC FOR ISL6613 LGATE GND PAD 3 FOR DFN AND EPSOIC-DEVICES, THE PAD ON THE BOTTOM SIDE OF THE PACKAGE MUST BE SOLDERED TO THE CIRCUIT'S GROUND. FN9153.9 June 15, 2010 ISL6612, ISL6613 Typical Application - 3 Channel Converter Using ISL65xx and ISL6612 Gate Drivers +12V +5V TO 12V VCC UGATE PVCC PWM BOOT ISL6612 PHASE LGATE GND +12V +5V TO 12V +5V VCC VFB VCC COMP UGATE PVCC PWM1 VSEN PWM2 PGOOD PWM +VCORE BOOT ISL6612 PHASE PWM3 LGATE MAIN CONTROL ISL65xx VID GND ISEN1 ISEN2 FS ISEN3 +12V +5V TO 12V GND VCC UGATE PVCC PWM BOOT ISL6612 PHASE LGATE GND 4 FN9153.9 June 15, 2010 ISL6612, ISL6613 Absolute Maximum Ratings Thermal Information Supply Voltage (VCC) . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .15V Supply Voltage (PVCC) . . . . . . . . . . . . . . . . . . . . . . . . . VCC + 0.3V Input Voltage (VPWM) . . . . . . . . . . . . . . . . . . . . . . GND - 0.3V to 7V BOOT Voltage (VBOOT-GND). . . . . . . . . . . . . . . . . . . . . . . . . . . .36V BOOT To PHASE Voltage (VBOOT-PHASE) . . . . . -0.3V to 15V (DC) . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . -0.3V to 16V (<10ns, 10J) UGATE. . . . . . . . . . . . . . . . . . . VPHASE - 0.3VDC to VBOOT + 0.3V VPHASE - 3.5V (<100ns Pulse Width, 2J) to VBOOT + 0.3V LGATE . . . . . . . . . . . . . . . . . . . . . . GND - 0.3VDC to VPVCC + 0.3V GND - 5V (<100ns Pulse Width, 2J) to VPVCC + 0.3V PHASE. . . . . . . . . . . . . . . . . . . . . . . . . . . .GND - 0.3VDC to 24VDC GND - 8V (<400ns, 20J) to 31V (<200ns, VBOOT-GND < 36V) ESD Rating Human Body Model . . . . . . . . . . . . . . . . . . . . Class I JEDEC STD Thermal Resistance JA (C/W) JC (C/W) 8 Ld SOIC Package (Note 4) . . . . . . . . 100 N/A 8 Ld EPSOIC Package (Notes 5, 6). . . 50 7 10 Ld DFN Package (Notes 5, 6) . . . . . 48 7 Maximum Junction Temperature (Plastic Package) . . . . . . . +150C Maximum Storage Temperature Range . . . . . . . . . .-65C to +150C Pb-Free Reflow Profile. . . . . . . . . . . . . . . . . . . . . . . . .see link below http://www.intersil.com/pbfree/Pb-FreeReflow.asp Recommended Operating Conditions Ambient Temperature Range. . . . . . . . . . . . . . . . . . .-40C to +85C Maximum Operating Junction Temperature. . . . . . . . . . . . . +125C Supply Voltage, VCC . . . . . . . . . . . . . . . . . . . . . . . . . . . . .12V 10% Supply Voltage Range, PVCC . . . . . . . . . . . . . . . . 5V to 12V 10% CAUTION: Do not operate at or near the maximum ratings listed for extended periods of time. Exposure to such conditions may adversely impact product reliability and result in failures not covered by warranty. NOTES: 4. JA is measured with the component mounted on a high effective thermal conductivity test board in free air. 5. JA is measured in free air with the component mounted on a high effective thermal conductivity test board with "direct attach" features. See Tech Brief TB379. 6. For JC, the "case temp" location is the center of the exposed metal pad on the package underside. Electrical Specifications Recommended Operating Conditions, Unless Otherwise Noted. PARAMETER SYMBOL TEST CONDITIONS MIN MAX (Note 8) TYP (Note 8) UNITS VCC SUPPLY CURRENT Bias Supply Current IVCC IVCC Gate Drive Bias Current IPVCC IPVCC ISL6612, fPWM = 300kHz, VVCC = 12V - 7.2 - mA ISL6613, fPWM = 300kHz, VVCC = 12V - 4.5 - mA ISL6612, fPWM = 1MHz, VVCC = 12V - 11 - mA ISL6613, fPWM = 1MHz, VVCC = 12V - 5 - mA ISL6612, fPWM = 300kHz, VPVCC = 12V - 2.5 - mA ISL6613, fPWM = 300kHz, VPVCC = 12V - 5.2 - mA ISL6612, fPWM = 1MHz, VPVCC = 12V - 7 - mA ISL6613, fPWM = 1MHz, VPVCC = 12V - 13 - mA POWER-ON RESET AND ENABLE VCC Rising Threshold TA = 0C to +85C 9.35 9.80 10.00 V VCC Rising Threshold TA = -40C to +85C 8.35 9.80 10.00 V VCC Falling Threshold TA = 0C to +85C 7.35 7.60 8.00 V VCC Falling Threshold TA = -40C to +85C 6.35 7.60 8.00 V PWM INPUT (See "TIMING DIAGRAM" on page 7) Input Current IPWM VPWM = 5V - 450 - A VPWM = 0V - -400 - A PWM Rising Threshold VCC = 12V - 3.00 - V PWM Falling Threshold VCC = 12V - 2.00 Typical Three-State Shutdown Window VCC = 12V 1.80 Three-State Lower Gate Falling Threshold VCC = 12V - Three-State Lower Gate Rising Threshold VCC = 12V Three-State Upper Gate Rising Threshold VCC = 12V Three-State Upper Gate Falling Threshold VCC = 12V 5 - V 2.40 V 1.50 - V - 1.00 - V - 3.20 - V - 2.60 - V FN9153.9 June 15, 2010 ISL6612, ISL6613 Electrical Specifications Recommended Operating Conditions, Unless Otherwise Noted. (Continued) PARAMETER SYMBOL Shutdown Holdoff Time TEST CONDITIONS MIN MAX (Note 8) TYP (Note 8) UNITS tTSSHD UGATE Rise Time - 245 - ns tRU VPVCC = 12V, 3nF Load, 10% to 90% - 26 - ns LGATE Rise Time tRL VPVCC = 12V, 3nF Load, 10% to 90% - 18 - ns UGATE Fall Time tFU VPVCC = 12V, 3nF Load, 90% to 10% - 18 - ns LGATE Fall Time tFL VPVCC = 12V, 3nF Load, 90% to 10% - 12 - ns UGATE Turn-On Propagation Delay (Note 7) tPDHU VPVCC = 12V, 3nF Load, Adaptive - 10 - ns LGATE Turn-On Propagation Delay (Note 7) tPDHL VPVCC = 12V, 3nF Load, Adaptive - 10 - ns UGATE Turn-Off Propagation Delay (Note 7) tPDLU VPVCC = 12V, 3nF Load - 10 - ns LGATE Turn-Off Propagation Delay (Note 7) tPDLL VPVCC = 12V, 3nF Load - 10 - ns LG/UG Three-State Propagation Delay (Note 7) tPDTS VPVCC = 12V, 3nF Load - 10 - ns Upper Drive Source Current IU_SOURCE VPVCC = 12V, 3nF Load - 1.25 - A Upper Drive Source Impedance RU_SOURCE 150mA Source Current 1.25 2.0 3.0 - 2 - A - 1.3 2.2 0.9 1.65 3.0 - 2 - A 0.85 1.25 2.2 OUTPUT (Note 7) Upper Drive Sink Current IU_SINK VPVCC = 12V, 3nF Load Upper Drive Transition Sink Impedance RU_SINK_TR 70ns with Respect to PWM Falling Upper Drive DC Sink Impedance RU_SINK_DC 150mA Source Current Lower Drive Source Current IL_SOURCE Lower Drive Source Impedance RL_SOURCE 150mA Source Current VPVCC = 12V, 3nF Load Lower Drive Sink Current IL_SINK VPVCC = 12V, 3nF Load Lower Drive Sink Impedance RL_SINK 150mA Sink Current - 3 - A 0.60 0.80 1.35 Thermal Shutdown Setpoint - 150 - C Thermal Recovery Setpoint - 108 - C OVER TEMPERATURE SHUTDOWN NOTES: 7. Limits should be considered typical and are not production tested. 8. Parameters with MIN and/or MAX limits are 100% tested at +25C, unless otherwise specified. Temperature limits established by characterization and are not production tested. Functional Pin Description PACKAGE PIN # SOIC DFN PIN SYMBOL 1 1 UGATE Upper gate drive output. Connect to gate of high-side power N-Channel MOSFET. 2 2 BOOT Floating bootstrap supply pin for the upper gate drive. Connect the bootstrap capacitor between this pin and the PHASE pin. The bootstrap capacitor provides the charge to turn on the upper MOSFET. See "Internal Bootstrap Device" on page 8 for guidance in choosing the capacitor value. - 3, 8 N/C 3 4 PWM The PWM signal is the control input for the driver. The PWM signal can enter three distinct states during operation; see "Three-State PWM Input" on page 7 for further details. Connect this pin to the PWM output of the controller. 4 5 GND Bias and reference ground. All signals are referenced to this node. It is also the power ground return of the driver. 5 6 LGATE FUNCTION No Connection. Lower gate drive output. Connect to gate of the low-side power N-Channel MOSFET. 6 7 VCC 7 9 PVCC This pin supplies power to both upper and lower gate drives in ISL6613; only the lower gate drive in ISL6612. Its operating range is +5V to 12V. Place a high quality low ESR ceramic capacitor from this pin to GND. Connect this pin to a +12V bias supply. Place a high quality low ESR ceramic capacitor from this pin to GND. 8 10 PHASE Connect this pin to the SOURCE of the upper MOSFET and the DRAIN of the lower MOSFET. This pin provides a return path for the upper gate drive. 9 11 PAD Connect this pad to the power ground plane (GND) via thermally enhanced connection. 6 FN9153.9 June 15, 2010 ISL6612, ISL6613 Description 1.5V<PWM<3.2V 1.0V<PWM<2.6V PWM tPDLU tPDHU tTSSHD tPDTS tPDTS UGATE tFU tRU LGATE tFL tPDLL tRL tTSSHD tPDHL FIGURE 1. TIMING DIAGRAM Operation Designed for versatility and speed, the ISL6612 and ISL6613 MOSFET drivers control both high-side and low-side N-Channel FETs of a half-bridge power train from one externally provided PWM signal. Prior to VCC exceeding its POR level, the Pre-POR overvoltage protection function is activated; the upper gate (UGATE) is held low and the lower gate (LGATE), controlled by the Pre-POR overvoltage protection circuits, is connected to the PHASE. Once the VCC voltage surpasses the VCC Rising Threshold (see "Electrical Specifications" on page 5), the PWM signal takes control of gate transitions. A rising edge on PWM initiates the turn-off of the lower MOSFET (see Timing Diagram). After a short propagation delay [tPDLL], the lower gate begins to fall. Typical fall times [tFL] are provided in "Electrical Specifications" on page 5. Adaptive shoot-through circuitry monitors the PHASE voltage and determines the upper gate delay time [tPDHU]. This prevents both the lower and upper MOSFETs from conducting simultaneously. Once this delay period is complete, the upper gate drive begins to rise [tRU] and the upper MOSFET turns on. A falling transition on PWM results in the turn-off of the upper MOSFET and the turn-on of the lower MOSFET. A short propagation delay [tPDLU] is encountered before the upper gate begins to fall [tFU]. Again, the adaptive shoot-through circuitry determines the lower gate delay time, tPDHL. The PHASE voltage and the UGATE voltage are monitored, and the lower gate is allowed to rise after PHASE drops below a level or the voltage of UGATE to PHASE reaches a level depending upon the current direction (See the following section for details). The lower gate then rises [tRL], turning on the lower MOSFET. 7 Advanced Adaptive Zero Shoot-Through Deadtime Control (Patent Pending) These drivers incorporate a unique adaptive deadtime control technique to minimize deadtime, resulting in high efficiency from the reduced freewheeling time of the lower MOSFETs' body-diode conduction, and to prevent the upper and lower MOSFETs from conducting simultaneously. This is accomplished by ensuring either rising gate turns on its MOSFET with minimum and sufficient delay after the other has turned off. During turn-off of the lower MOSFET, the PHASE voltage is monitored until it reaches a -0.2V/+0.8V trip point for a forward/reverse current, at which time the UGATE is released to rise. An auto-zero comparator is used to correct the rDS(ON) drop in the phase voltage preventing from false detection of the -0.2V phase level during rDS(ON conduction period. In the case of zero current, the UGATE is released after 35ns delay of the LGATE dropping below 0.5V. During the phase detection, the disturbance of LGATE's falling transition on the PHASE node is blanked out to prevent falsely tripping. Once the PHASE is high, the advanced adaptive shoot-through circuitry monitors the PHASE and UGATE voltages during a PWM falling edge and the subsequent UGATE turn-off. If either the UGATE falls to less than 1.75V above the PHASE or the PHASE falls to less than +0.8V, the LGATE is released to turn on. Three-State PWM Input A unique feature of these drivers and other Intersil drivers is the addition of a shutdown window to the PWM input. If the PWM signal enters and remains within the shutdown window for a set holdoff time, the driver outputs are disabled and both MOSFET gates are pulled and held low. The shutdown state is removed when the PWM signal moves outside the shutdown window. Otherwise, the PWM rising and falling thresholds (outlined in "Electrical Specifications" on page 5) determine when the lower and upper gates are enabled. FN9153.9 June 15, 2010 ISL6612, ISL6613 This feature helps prevent a negative transient on the output voltage when the output is shut down, eliminating the Schottky diode that is used in some systems for protecting the load from reversed output voltage events. In addition, more than 400mV hysteresis also incorporates into the three-state shutdown window to eliminate PWM input oscillations due to the capacitive load seen by the PWM input through the body diode of the controller's PWM output when the power-up and/or power-down sequence of bias supplies of the driver and PWM controller are required. As an example, suppose two IRLR7821 FETs are chosen as the upper MOSFETs. The gate charge, QG, from the data sheet is 10nC at 4.5V (VGS) gate-source voltage. Then the QGATE is calculated to be 53nC for UVCC (i.e. PVCC in ISL6613, VCC in ISL6612) = 12V. We will assume a 200mV droop in drive voltage over the PWM cycle. We find that a bootstrap capacitance of at least 0.267F is required. 1.6 1.4 1.2 During initial startup, the VCC voltage rise is monitored. Once the rising VCC voltage exceeds 9.8V (typically), operation of the driver is enabled and the PWM input signal takes control of the gate drives. If VCC drops below the falling threshold of 7.6V (typically), operation of the driver is disabled. 0.8 0.6 QGATE = 100nC 0.4 0.2 Prior to VCC exceeding its POR level, the upper gate is held low and the lower gate is controlled by the overvoltage protection circuits during initial startup. The PHASE is connected to the gate of the low side MOSFET (LGATE), which provides some protection to the microprocessor if the upper MOSFET(s) is shorted during initial startup. For complete protection, the low side MOSFET should have a gate threshold well below the maximum voltage rating of the load/microprocessor. When VCC drops below its POR level, both gates pull low and the Pre-POR overvoltage protection circuits are not activated until VCC resets. Internal Bootstrap Device Both drivers feature an internal bootstrap schottky diode. Simply adding an external capacitor across the BOOT and PHASE pins completes the bootstrap circuit. The bootstrap function is also designed to prevent the bootstrap capacitor from overcharging due to the large negative swing at the trailing-edge of the PHASE node. This reduces voltage stress on the boot to phase pins. The bootstrap capacitor must have a maximum voltage rating above UVCC + 5V and its capacitance value can be chosen from Equation 1: (EQ. 1) Q G1 * UVCC Q GATE = ------------------------------------ * N Q1 V GS1 where QG1 is the amount of gate charge per upper MOSFET at VGS1 gate-source voltage and NQ1 is the number of control MOSFETs. The VBOOT_CAP term is defined as the allowable droop in the rail of the upper gate drive. 8 1.0 50nC Pre-POR Overvoltage Protection Q GATE C BOOT_CAP -------------------------------------V BOOT_CAP CBOOT_CAP (F) Power-On Reset (POR) Function 20nC 0.0 0.0 0.1 0.2 0.3 0.4 0.5 0.6 0.7 0.8 0.9 1.0 VBOOT_CAP (V) FIGURE 2. BOOTSTRAP CAPACITANCE vs BOOT RIPPLE VOLTAGE Gate Drive Voltage Versatility The ISL6612 and ISL6613 provide the user flexibility in choosing the gate drive voltage for efficiency optimization. The ISL6612 upper gate drive is fixed to VCC [+12V], but the lower drive rail can range from 12V down to 5V depending on what voltage is applied to PVCC. The ISL6613 ties the upper and lower drive rails together. Simply applying a voltage from 5V up to 12V on PVCC sets both gate drive rail voltages simultaneously. Over-Temperature Protection (OTP) When the junction temperature of the IC exceeds +150C (typically), both upper and lower gates turn off. The driver stays off and does not return to normal operation until its junction temperature comes down below +108C (typically). For high frequency applications, applying a lower voltage to PVCC helps reduce the power dissipation and lower the junction temperature of the IC. This method reduces the risk of tripping OTP. Power Dissipation Package power dissipation is mainly a function of the switching frequency (fSW), the output drive impedance, the external gate resistance, and the selected MOSFET's internal gate resistance and total gate charge. Calculating the power dissipation in the driver for a desired application is critical to ensure safe operation. Exceeding the maximum allowable power dissipation level will push the IC beyond the maximum recommended operating junction temperature of +125C. The maximum allowable IC power dissipation for the SO8 package FN9153.9 June 15, 2010 ISL6612, ISL6613 is approximately 800mW at room temperature, while the power dissipation capacity in the EPSOIC and DFN packages, with an exposed heat escape pad, is more than 2W and 1.5W, respectively. Both EPSOIC and DFN packages are more suitable for high frequency applications. See "Layout Considerations" on page 9 for thermal transfer improvement suggestions. When designing the driver into an application, it is recommended that the following calculation is used to ensure safe operation at the desired frequency for the selected MOSFETs. The total gate drive power losses due to the gate charge of MOSFETs and the driver's internal circuitry and their corresponding average driver current can be estimated using Equation 2 and Equation 3, respectively, P Qg_TOT = P Qg_Q1 + P Qg_Q2 + I Q * VCC (EQ. 2) BOOT UVCC D CGD RHI1 RLO1 G RG1 CDS RGI1 CGS Q1 S PHASE FIGURE 3. TYPICAL UPPER-GATE DRIVE TURN-ON PATH LVCC D Q G1 * UVCC 2 P Qg_Q1 = --------------------------------------- * F SW * N Q1 V GS1 CGD RHI2 * LVCC 2 Q G2 P Qg_Q2 = -------------------------------------- * F SW * N Q2 V GS2 RLO2 G RG2 CDS RGI2 CGS Q G1 * UVCC * NQ1 Q G2 * LVCC * N Q2 I DR = ------------------------------------------------------ + ----------------------------------------------------- * F SW + I Q V GS1 V GS2 (EQ. 3) where the gate charge (QG1 and QG2) is defined at a particular gate to source voltage (VGS1and VGS2) in the corresponding MOSFET data sheet; IQ is the driver's total quiescent current with no load at both drive outputs; NQ1 and NQ2 are number of upper and lower MOSFETs, respectively; UVCC and LVCC are the drive voltages for both upper and lower FETs, respectively. The IQ*VCC product is the quiescent power of the driver without capacitive load and is typically 116mW at 300kHz. The total gate drive power losses are dissipated among the resistive components along the transition path. The drive resistance dissipates a portion of the total gate drive power losses, the rest will be dissipated by the external gate resistors (RG1 and RG2) and the internal gate resistors (RGI1 and RGI2) of MOSFETs. Figures 3 and 4 show the typical upper and lower gate drives turn-on transition path. The power dissipation on the driver can be roughly estimated as: P DR = P DR_UP + P DR_LOW + I Q * VCC R LO1 R HI1 P Qg_Q1 P DR_UP = -------------------------------------- + ---------------------------------------- * --------------------R + R R + R 2 HI1 EXT1 LO1 EXT1 Q2 S FIGURE 4. TYPICAL LOWER-GATE DRIVE TURN-ON PATH Layout Considerations For heat spreading, place copper underneath the IC whether it has an exposed pad or not. The copper area can be extended beyond the bottom area of the IC and/or connected to buried copper plane(s) with thermal vias. This combination of vias for vertical heat escape, extended copper plane, and buried planes for heat spreading allows the IC to achieve its full thermal potential. Place each channel power component as close to each other as possible to reduce PCB copper losses and PCB parasitics: shortest distance between DRAINs of upper FETs and SOURCEs of lower FETs; shortest distance between DRAINs of lower FETs and the power ground. Thus, smaller amplitudes of positive and negative ringing are on the switching edges of the PHASE node. However, some space in between the power components is required for good airflow. The traces from the drivers to the FETs should be kept short and wide to reduce the inductance of the traces and to promote clean drive signals. R LO2 R HI2 P Qg_Q2 P DR_LOW = -------------------------------------- + ---------------------------------------- * --------------------2 R HI2 + R EXT2 R LO2 + R EXT2 R GI1 R EXT1 = R G1 + ------------N Q1 R GI2 R EXT2 = R G2 + ------------N Q2 (EQ. 4) 9 FN9153.9 June 15, 2010 ISL6612, ISL6613 Package Outline Drawing L10.3x3 10 LEAD DUAL FLAT PACKAGE (DFN) Rev 6, 09/09 3.00 6 PIN #1 INDEX AREA A B 1 6 PIN 1 INDEX AREA (4X) 3.00 2.00 8x 0.50 2 10 x 0.23 4 0.10 1.60 TOP VIEW 10x 0.35 BOTTOM VIEW 4 (4X) 0.10 M C A B 0.415 PACKAGE OUTLINE 0.200 0.23 0.35 (10 x 0.55) SEE DETAIL "X" (10x 0.23) 1.00 MAX 0.10 C BASE PLANE 2.00 0.20 C SEATING PLANE 0.08 C SIDE VIEW (8x 0.50) C 0.20 REF 5 1.60 0.05 TYPICAL RECOMMENDED LAND PATTERN DETAIL "X" NOTES: 1. Dimensions are in millimeters. Dimensions in ( ) for Reference Only. 2. Dimensioning and tolerancing conform to AMSE Y14.5m-1994. 3. Unless otherwise specified, tolerance : Decimal 0.05 4. Lead width applies to the metallized terminal and is measured between 0.18mm and 0.30mm from the terminal tip. 5. Tiebar shown (if present) is a non-functional feature. 6. The configuration of the pin #1 identifier is optional, but must be located within the zone indicated. The pin #1 indentifier may be either a mold or mark feature. 10 FN9153.9 June 15, 2010 ISL6612, ISL6613 Small Outline Exposed Pad Plastic Packages (EPSOIC) M8.15B N INDEX AREA H 0.25(0.010) M 8 LEAD NARROW BODY SMALL OUTLINE EXPOSED PAD PLASTIC PACKAGE B M E INCHES -B1 2 3 TOP VIEW L SEATING PLANE -A- h x 45o A D -C- A1 B 0.25(0.010) M C 0.10(0.004) C A M B S SIDE VIEW SYMBOL MIN MAX MIN MAX NOTES A 0.056 0.066 1.43 1.68 - A1 0.001 0.005 0.03 0.13 - B 0.0138 0.0192 0.35 0.49 9 C 0.0075 0.0098 0.19 0.25 - D 0.189 0.196 4.80 4.98 3 E 0.150 0.157 3.81 3.99 4 e e MILLIMETERS 0.050 BSC 1.27 BSC - H 0.230 0.244 5.84 6.20 - h 0.010 0.016 0.25 0.41 5 L 0.016 0.035 0.41 0.64 6 N 8 8 7 0 8 0 8 - P - 0.094 - 2.387 11 P1 - 0.094 - 2.387 11 Rev. 4 1/09 NOTES: 1 2 3 1. Symbols are defined in the "MO Series Symbol List" in Section 2.2 of Publication Number 95. 2. Dimensioning and tolerancing per ANSI Y14.5M-1982. P1 3. Dimension "D" does not include mold flash, protrusions or gate burrs. Mold flash, protrusion and gate burrs shall not exceed 0.15mm (0.006 inch) per side. N 4. Dimension "E" does not include interlead flash or protrusions. Interlead flash and protrusions shall not exceed 0.25mm (0.010 inch) per side. P BOTTOM VIEW 5. The chamfer on the body is optional. If it is not present, a visual index feature must be located within the crosshatched area. 6. "L" is the length of terminal for soldering to a substrate. 7. "N" is the number of terminal positions. 8. Terminal numbers are shown for reference only. 9. The lead width "B", as measured 0.36mm (0.014 inch) or greater above the seating plane, shall not exceed a maximum value of 0.61mm (0.024 inch). 10. Controlling dimension: INCH. Converted millimeter dimensions are not necessarily exact. 11. Dimensions "P" and "P1" are thermal and/or electrical enhanced variations. Values shown are maximum size of exposed pad within lead count and body size. 11 FN9153.9 June 15, 2010 ISL6612, ISL6613 Small Outline Plastic Packages (SOIC) M8.15 (JEDEC MS-012-AA ISSUE C) N INDEX AREA 8 LEAD NARROW BODY SMALL OUTLINE PLASTIC PACKAGE H 0.25(0.010) M B M INCHES E SYMBOL -B1 2 3 L SEATING PLANE -A- A D h x 45 -C- e A1 B 0.25(0.010) M C 0.10(0.004) C A M MIN MAX MIN MAX NOTES A 0.0532 0.0688 1.35 1.75 - A1 0.0040 0.0098 0.10 0.25 - B 0.013 0.020 0.33 0.51 9 C 0.0075 0.0098 0.19 0.25 - D 0.1890 0.1968 4.80 5.00 3 E 0.1497 0.1574 3.80 4.00 4 e B S 0.050 BSC 1.27 BSC - H 0.2284 0.2440 5.80 6.20 - h 0.0099 0.0196 0.25 0.50 5 L 0.016 0.050 0.40 1.27 6 N NOTES: MILLIMETERS 8 0 8 8 0 7 8 1. Symbols are defined in the "MO Series Symbol List" in Section 2.2 of Publication Number 95. Rev. 1 6/05 2. Dimensioning and tolerancing per ANSI Y14.5M-1982. 3. Dimension "D" does not include mold flash, protrusions or gate burrs. Mold flash, protrusion and gate burrs shall not exceed 0.15mm (0.006 inch) per side. 4. Dimension "E" does not include interlead flash or protrusions. Interlead flash and protrusions shall not exceed 0.25mm (0.010 inch) per side. 5. The chamfer on the body is optional. If it is not present, a visual index feature must be located within the crosshatched area. 6. "L" is the length of terminal for soldering to a substrate. 7. "N" is the number of terminal positions. 8. Terminal numbers are shown for reference only. 9. The lead width "B", as measured 0.36mm (0.014 inch) or greater above the seating plane, shall not exceed a maximum value of 0.61mm (0.024 inch). 10. Controlling dimension: MILLIMETER. Converted inch dimensions are not necessarily exact. All Intersil U.S. products are manufactured, assembled and tested utilizing ISO9000 quality systems. Intersil Corporation's quality certifications can be viewed at www.intersil.com/design/quality Intersil products are sold by description only. Intersil Corporation reserves the right to make changes in circuit design, software and/or specifications at any time without notice. Accordingly, the reader is cautioned to verify that data sheets are current before placing orders. Information furnished by Intersil is believed to be accurate and reliable. However, no responsibility is assumed by Intersil or its subsidiaries for its use; nor for any infringements of patents or other rights of third parties which may result from its use. No license is granted by implication or otherwise under any patent or patent rights of Intersil or its subsidiaries. For information regarding Intersil Corporation and its products, see www.intersil.com 12 FN9153.9 June 15, 2010