THAT Corporation; 45 Sumner Street; Milford, Massachusetts 01757-1656; USA
Tel: +1 508 478-9200; Fax +1 508 478-0990; Web: www.thatcorp.com
Copyright © 2017, THAT Corporation; Doc 600031 Rev 09
Low-Noise, High Performance
Audio Preamplifier IC
THAT 1510, 1512
FEATURES
• Low Noise:
1 nV/√Hz input noise (60 dB gain)
34 nV/√Hz input noise (0dB gain) (1512)
• Low THD+N (full audio bandwidth):
0.001% ≤ 40 dB gain
0.005% @ 60 dB gain
• Low Current: 6 mA typ.
• Wide Bandwidth: 7 MHz @ G=100
• High Slew Rate: 19 V/µs
• Wide Output Swing: ±13.3 V on
±15 V supplies
• Gain adjustable from 0 to >60 dB with
one external resistor
•
Industry Standard Pinouts
APPLICATIONS
• Differential Low Noise Preamplifiers
• Differential Summing Amplifiers
• Differential Variable Gain Amplifiers
• Microphone Preamplifiers
• Moving-Coil Transducer Amplifiers
• Line Input Stages
• Audio
• Sonar
• Instrumentation
Pin
Name
DIP8
Pkg
SO8
Pkg
SO16
Pkg
SO14
Pkg
RG1 1 1 2 3
-In 2 2 4 4
+In 3 3 5 5
V- 4 4 7 6
Ref 5 5 10 10
Out 6 6 11 9
V+ 7 7 13 11
RG2 8 8 15 12
Table 1. Pin Assignments
Description
The THAT 1510 and 1512 are high perfor-
mance audio preamplifiers suitable for micro-
phone preamp and bus summing applications.
The ICs are available in a variety of packages and
pin configurations, making them pin compatible
with the Analog Devices SSM2019 and SSM2017
(discontinued), and the Texas Instruments INA217
and INA163.
Gain for both parts is adjustable via one exter-
nal resistor, making it possible to control gain
over a wide range with a single-gang potentiome-
ter. The 1510 gain equation is identical to that of
the SSM2019, reaching
6 dB
gain with a 10 kΩ
resistor. The 1512 reaches 0 dB gain with a
10
k
Ω
resistor. Because the 1512 exhibits
significantly lower noise at lower gain settings, it is
recommended over the 1510 for new designs.
Designed from the ground up in THAT's com-
plementary dielectric isolation process and
including laser-trimmed Si-Chrome thin film
resistors, the THAT 1510 and 1512 improve on
existing integrated microphone preamps by
offering lower noise at low gains, wider band-
width, higher slew rate, lower distortion, and
lower supply current. The parts feature internal
ESD overload protection on all critical pins.
In short, the THAT 1510 and 1512 provide
superior performance in a popular format at an
affordable price.
Figure 1. THAT 1510 / 1512 Equivalent Circuit Diagram
(THAT 1512 values shown in parentheses)
Part
Type
DIP8
Pkg
SO8
Pkg
SO16
Pkg
SO14
Pkg
1510 1510P08-U
1510S08-U
1510W16-U
1510S14-U
1512 1512P08-U
1512S08-U
Inquire 1512S14-U
Table 2. Ordering Information
V+
V-
-In
R
G2
R
G1
+In
Out
Ref
+
-
5k
5k
(10k)
5k
5k
(10k)
5k
5k
Output Stage
Input Stage
R
A
R
B
-A
V
-A
V
THAT 1510/1512 Low-Noise Page 2 of 8 Document 600031 Rev 09
High Performance Audio Preamplifier
THAT Corporation; 45 Sumner Street; Milford, Massachusetts 01757-1656; USA
Tel: +1 508 478-9200; Fax +1 508 478-0990; Web: www.thatcorp.com
Copyright © 2017, THAT Corporation; All rights reserved.
SPECIFICATIONS
1
Absolute Maximum Ratings
2 , 3
Positive Supply Voltage (V
CC
)
+20 V
Lead Temp. (T
LEAD
) (Soldering 10 sec) 260 °C
Negative Supply Voltage (V
EE
) -
20 V
Operating Temperature Range (T
OP
) -40 to +85°C
Input Voltage (V
IN MAX
) V
CC
+ 0.5V, V
EE
-
0.5V
Storage Temperature Range (T
ST
) -40 to +125°C
Output Short-Circuit Duration (t
SH
)
Continuous
Junction Temperature (T
J
) 150°C
Electrical Characteristics
2
1510 1512
Parameter Symbol Conditions Min Typ Max Min Typ Max Units
Supply Current I
CC
, -I
EE
No signal — 6.0 7.9 — 6.0 7.9 mA
V
CC
= -V
EE
= 20V — — 8.0 — — 8.0 mA
Input Bias Current I
B
No signal; Either input — 4.8 14 — 4.8 14 µA
connected to GND
Input Offset Current I
B-OFF
No signal -1.4 — +1.4 -1.4 — +1.4 µA
Offset Voltage
Output Stage Output Offset Vos
OO
No Signal, V
CM
=0 -5 — +5 -5 — +5 mV
Input Stage Input Offset Vos
II
-250 — +250 -250 — +250 µV
Total Output Offset G=voltage gain -5-0.25G 5+0.25G -5-0.25G 5+0.25G mV
Input Voltage Range
Common Mode V
IN-CM
Common mode, all gains — ± 13 — — ± 13 — V
Differential Mode V
IN-UNBAL
Unbalanced -13 — +13 -13 — +13 V
One input to GND, 0dB gain
Differential Gain G
diff
0 — 70 -6 — 64 dB
Ref Input Voltage Range — ± 8 — — ± 8 — V
Ref Input Impedance — 10 — — 15 — kΩ
Ref Input Gain to Output — 0 — — 0 — dB
Input Impedance Z
IN-DIFF
Differential
0dB gain — 32||1.9 — — 37||1.9 — MΩ||pF
20dB gain — 32||2.0 — — 37||2.0 — MΩ||pF
40dB gain — 32||2.5 — — 36||3.1 — MΩ||pF
60dB gain — 29||8.0 — — 31||13.9 — MΩ||pF
Z
IN-CM
Common mode
all gains — 8||7.7 — — 9||7.7 — MΩ||pF
1. All specifications are subject to change without notice.
2. Unless otherwise noted, T
A
=25ºC, V
CC
=+15V, V
EE
= -15V.
3. Stresses above those listed under “Absolute Maximum Ratings” may cause permanent damage to the device. These are stress ratings only; the functional operation of
the device at these or any other conditions above those indicated in the operational sections of this specification is not implied. Exposure to absolute maximum rating
conditions for extended periods may affect device reliability.
Recommended Operating Con ditions
Parameter Symbol Conditions Min Typ Max Units
Positive Supply Voltage V
CC
+5 +20 V
Negative Supply Voltage V
EE
-5 -20 V
THAT 1510/1512 Low-Noise Page 3 of 8 Document 600031 Rev 09
High Performance Audio Preamplifier
THAT Corporation; 45 Sumner Street; Milford, Massachusetts 01757-1656; USA
Tel: +1 508 478-9200; Fax +1 508 478-0990; Web: www.thatcorp.com
Copyright © 2017, THAT Corporation; All rights reserved.
Electrical Characteristics (con’t)
2
1510 1512
Parameter Symbol Conditions Min Typ Max Min Typ Max Units
Common Mode Rejection Ratio CMRR V
CM
=± 10V; DC to 60 Hz
0 dB gain 45 60 — 45 60 — dB
20 dB gain 65 80 — 65 80 — dB
40 dB gain 85 100 — 85 100 — dB
60 dB gain 105 120 — 105 120 — dB
Power Supply Rejection Ratio PSRR V
CC
= -V
EE
; ±5V to ±20V; DC to 60 Hz
0 dB gain — 85 — — 60 — dB
20 dB gain — 105 — — 105 — dB
40 dB gain — 120 — — 120 — dB
60 dB gain — 124 — — 124 — dB
Total Harmonic Distortion THD+N V
OUT
= 7Vrms; R
L
= 5 kΩ
f = 1kHz; BW = 20 kHz
0 dB gain — 0.0005 — — 0.001 — %
20 dB gain — 0.0012 — — 0.004 — %
40 dB gain — 0.0016 — — 0.005 — %
60 dB gain — 0.005 — — 0.008 — %
Equivalent Input Noise
e
n(IN)
f = 1kHz,
0 dB gain — 57 — — 34 — nV/√Hz
20 dB gain — 7 — — 4.6 — nV/√Hz
40 dB gain — 1.7 — — 1.4 — nV/√Hz
60 dB gain — 1 — — 1 — nV/√Hz
Input Current Noise
i
n(IN)
60 dB gain — 2.0 — — 2.0 — pA/√Hz
Noise Figure NF 60 dB gain
R
S
= 150 Ω — 1.6 — — 1.6 — dB
R
S
= 200 Ω — 1.3 — — 1.3 — dB
Slew Rate SR R
L
= 2 kΩ
C
L
= 50 pF 13 19 — 13 19 — V/µs
Bandwidth -3dB BW
-3dB
R
L
= 2 kΩ; C
L
= 10 pF
0 dB gain — 15 — — 11 — MHz
20 dB gain — 8 — — 9 — MHz
40 dB gain — 7 — — 7 — MHz
60 dB gain — 3 — — 1.6 — MHz
Output Gain Error G
ER (OUT)
f = 1kHz; R
L
= 2 kΩ
R
G
=infinite, G=0 dB -0.5 — +0.5 — — — dB
R
G
= 1.1 kΩ, G=20 dB -0.5 — +0.5 — — — dB
R
G
= 101 Ω, G=40 dB -0.5 — +0.5 — — — dB
R
G
= 10 Ω, G=60 dB -0.5 — +0.5 — — — dB
R
G
= 10 kΩ, G=0 dB — — — -0.5 — +0.5 dB
R
G
= 526.3 Ω, G=20 dB — — — -0.5 — +0.5 dB
R
G
= 50.3 Ω, G=40 dB — — — -0.5 — +0.5 dB
R
G
= 5 Ω, G=60 dB — — — -0.5 — +0.5 dB
Output Voltage Swing V
O
R
L
= 2 kΩ
all gains ±13 ±13.3 — ±13 ±13.3 — V
Output Short Circuit Current I
SC
R
L
= 0 Ω — ± 35 — — ± 35 — mA
Minimum Resistive Load R
Lmin
2 — — 2 — — kΩ
Maximum Capacitive Load C
Lmax
— — 300 — — 300 pF
Gain Equation
=
1
+
=
0
.
5
+
THAT 1510/1512 Low-Noise Page 4 of 8 Document 600031 Rev 09
High Performance Audio Preamplifier
THAT Corporation; 45 Sumner Street; Milford, Massachusetts 01757-1656; USA
Tel: +1 508 478-9200; Fax +1 508 478-0990; Web: www.thatcorp.com
Copyright © 2017, THAT Corporation; All rights reserved.
Gain Setting
A single external resistor (R
G
) between the R
G1
and R
G2
pins is all that is needed to set the gain of the
THAT 1510/1512, according to the formulae:
for the 1510:
= 1 +
or
for the 1512:
= 0.5 +
where
A
V
is the voltage gain of the part.
E
ither part may reach unity gain, but the value of
R
G
required varies significantly between the two
parts. For the 1510, gain is 0 dB when R
G
is infinite
(open); this is the minimum gain for the 1510. At
infinite R
G
, the 1512 reaches -6 dB gain; this is the
minimum gain for the 1512. With R
G
=10 kΩ, the
1512 reaches 0 dB gain.
Overall gain accuracy depends on the tolerance of
R
G
and the accuracy of the internal thin-film resistors
connected to pins R
G1
and R
G2
in the 1510/1512 (R
A
& R
B
in Figure 1). These internal resistors have a
typical initial accuracy (at room temperature) of
±0.5%, and are typically stable with temperature to
within ±100 ppm/°C. Gain will drift with tempera-
ture based on the mismatch between the temperature
coefficient of the external R
G
and that of the internal
resistors R
A
& R
B
.
For variable-gain applications where gain accura-
cy is important, THAT recommends using discrete,
switched resistors for R
G
. Where continuous control
is required, or where gain accuracy is less critical, a
potentiometer may be used. In such applications,
designers should take care in specifying the element
construction to avoid excess noise. The potentiome-
ter taper will set the circuit’s characteristic of gain vs.
pot rotation. Typically, reverse log (reverse audio)
taper elements offer the desired behavior in which
gain increases with clockwise rotation (and lower
values for R
G
). See THAT Design Note 138 for a
discussion of potentiometer taper and gain for the
1510 and 1512 compared to similar parts from other
manufacturers.
Noise Performance
Both parts exhibit excellent voltage noise perfor-
mance of ~1 nV/√Hz at high gains. With ~2 pA/√Hz
current noise, they are optimized for relatively low
source impedance applications, such as dynamic
microphones with typically a few hundred ohm
output impedances. But, because they have different
internal gain structures, the 1510 has higher
equivalent input noise at 0 dB gain (~57 nV/√Hz)
than the 1512, which runs 4.5 dB lower at
~34 nV/√Hz. The unusual and superior topology of
the THAT 1512 makes its noise performance
comparable to some of the better discrete designs
currently available.
Inputs
Simple Configurations
As shown in Figure 2, the 1510/1512 includes
protection diodes at all pins except V+ and V-.
Applications
Figure 2. THAT 1510 / 1512 Equivalent Circuit with Protection Diodes
V+
V-
-In
R
G2
R
G1
+In
Out
Ref
+
-
5k
5k
(10k)
5k
5k
(10k)
5k
5k
Output Stage
Input Stage
R
A
R
B
-A
V
-A
V
THAT 1510/1512 Low-Noise Page 5 of 8 Document 600031 Rev 09
High Performance Audio Preamplifier
THAT Corporation; 45 Sumner Street; Milford, Massachusetts 01757-1656; USA
Tel: +1 508 478-9200; Fax +1 508 478-0990; Web: www.thatcorp.com
Copyright © 2017, THAT Corporation; All rights reserved.
These diodes reduce the likelihood that acci-
dental electrostatic discharge (ESD) or electrical over
stress (EOS) will damage the ICs. Other diodes
across the base-emitter junctions of the input
transistors prevent excessive reverse biasing of these
junctions (which would degrade the noise perfor-
mance of the input devices).
Other than the protection diodes, the 1510/1512
input pins are connected only to the bases of their
respective input devices. For proper operation, the
bases must be provided a source of dc bias that will
maintain the inputs within the IC's input common-
mode range. Figure 3 shows the simplest approach;
dc bias is supplied via R
1
and R
2
. At 1 kΩ each, they
will minimize pickup of unwanted noise and
interference, as well as generate relatively little noise
due to input current noise in the 1510/1512.
However, at high gains, their inherent voltage noise,
plus the 1510/1512's input current noise drawn
across these resistors, adds significantly to the noise
at the 1510/1512's output.
Because R
G
is dc coupled in the circuit of Fig-
ure 3, the dc level at the output of the 1510/1512 will
vary with gain. In most applications, the output
should be ac-coupled to the next stage. For applica-
tions where R
G
is variable (via a pot or switched
resistors) to allow gain adjustment, R
G
should be ac-
coupled as shown in Figure 4. By adding C
G
in series
with R
G
, dc gain is fixed (at unity for the 1510, and ½
for the 1512). This constrains the output dc offset to
just over +/-5 mV, and prevents it from varying with
gain. With this low offset, ac coupling of the output is
usually unnecessary.
C
G
must be large enough not to interfere with low-
frequency response at the
smallest values of R
G
. For
60 dB gain, R
G
=10 Ω (1510) or R
G
=5 Ω (1512). For a
-3 dB point of approximately 5 Hz, C
G
=3,300 µF (1510),
or C
G
=6,800 µF (1512). For other maximum gains or
minimum frequencies, scale C
G
accordingly.
Phantom Power
Phantom power is required for many condenser
microphones. THAT recommends the circuit of
Figure 5 when phantom power is included
4
. R
3
, R
4
,
and D
1
- D
6
are used to limit the current that flows
through the 1510/1512 inputs when the circuit
inputs (-In and +In) are shorted to ground while
phantom power is turned on. This causes C
4
and/or
C
5
to discharge through other circuit components,
often generating transient currents of several amps.
R
3
and R
4
should be at least 10 Ω to limit destructive
currents. (Higher values further limit current flow,
4. In revisions 0 and 1 of this data sheet, we recommended using Schottky diodes (1N5819 types) at D
1
~ D
4
to protect the 1510/1512 inputs against overloads.
Subsequently, we discovered that the leakage of these diodes could cause problems with DC fluctuations (hence noise) at the 1510/1512 output. Upon further
investigation, we concluded that conventional rectifier diodes like the 1N4004 (the glass-passivated GP version) provide adequate protection and do not introduce
unacceptable leakage. Additionally, 1N4004 diodes are much cheaper and more readily available than the Schottky types.
Since publishing revision 4, we determined that the internal reverse-bias diodes between the pins +In/R
G2
and -In/R
G1
may be damaged by phantom power faults under
certain conditions. Small-signal diodes (D
5
and D
6
) avoid this problem by appearing in parallel with the internal diodes, diverting excess current around the 1510/1512.
Figure 3. Basic 1510 / 1512 Circuit
RG
+In
Out
-In
RG2
RG1
U1
THAT
1510/1512
-15
+15
-In
+In
R1
1k
R2
1k
C1
470p
C2
470p
C3
47p
Out
C6
100n
C9
100n
V+
V-
Ref
THAT 1510/1512 Low-Noise Page 6 of 8 Document 600031 Rev 09
High Performance Audio Preamplifier
THAT Corporation; 45 Sumner Street; Milford, Massachusetts 01757-1656; USA
Tel: +1 508 478-9200; Fax +1 508 478-0990; Web: www.thatcorp.com
Copyright © 2017, THAT Corporation; All rights reserved.
but introduce additional source impedance and
noise.) D
1
through D
4
prevent the IC's inputs from
significantly exceeding the supply rails. D
5
and D
6
steer currents around the input stage in the
1510/1512, preventing damage.
The series combination of C
4
and C
5
should be
made large to minimize high-pass filtering of the
signal based upon the sum of the values of R
1
+R
2
. As
well, keeping their reactance low relative to the
external microphone's source impedance will avoid
increasing the effects of low-frequency current noise
in the 1510/1512 input stage.
Other manufacturers have recommended, and
many pro audio products include, a zener diode
arrangement connected to the bridge rectifier instead
of the connection to V+ and V- as shown in Figure 5.
THAT does not recommend this approach, because
we find that R
3
and R
4
must be made much larger
(e.g., ≥ 51 Ω) in order to limit peak currents enough
to protect reasonably sized zener diodes (eg. ½ W).
Such large series input resistors will limit the noise
performance of the preamp. The ultimate floor is set
by the impedance of the microphone, but any
additional series resistance further degrades
performance.
For further insights into this subject, see the
Audio Engineering Society preprints "The 48 Volt
Phantom Menace," by Gary K. Hebert and Frank W.
Thomas, presented at the 110th AES Convention and
"The 48 Volt Phantom Menace Returns", by Rosalfon-
so Bortoni and Wayne Kirkwood presented at the
127th AES Convention.
Impedance and Line Input Configurations
A higher common-mode input impedance is de-
sirable (compared with that of Figures 3 and 4) when
input coupling capacitors (C
4
and C
5
) are used to
block phantom power. At low frequencies where the
reactance of C
4
and C
5
become significant (compared
to the common-mode input impedances), the two
capacitors interact with the common-mode input
impedance (seen looking to the right-side of both
capacitors) to form voltage dividers for common-
mode signals. Differences in the two capacitors'
values leads to different voltage dividers, spoiling the
low-frequency common-mode rejection of the stage.
Since C
4
and C
5
are generally large, electrolytic types,
precise matching is difficult and expensive to achieve.
High common-mode input impedance reduces the
matching requirement by decreasing the frequency at
which the capacitive reactance becomes significant
inversely with the common-mode input impedance
The "T-bias" circuit (R
1
, R
2
, and R
7
) shown in
Figure 5 accommodates this objective. In this circuit,
R
1
and R
2
are connected to a third resistor R
7
,
boosting the low-frequency common mode input
impedance (as "seen looking in" from the coupling
capacitors) to the value of R
1
+ (2*R
7
) -- approxi-
mately 45 kΩ with the values shown. The increased
Figure 4. Basic 1510 / 1512 Circuit with Variable Gain
RG
CG
+In
Out
-In
RG2
RG1
U1
THAT
1510/1512
-15
+15
-In
+In
R1
1k
R2
1k
C1
470p
C2
470p
C3
47p
Out
C6
100n
C9
100n
V+
V-
Ref
THAT 1510/1512 Low-Noise Page 7 of 8 Document 600031 Rev 09
High Performance Audio Preamplifier
THAT Corporation; 45 Sumner Street; Milford, Massachusetts 01757-1656; USA
Tel: +1 508 478-9200; Fax +1 508 478-0990; Web: www.thatcorp.com
Copyright © 2017, THAT Corporation; All rights reserved.
common mode impedance from T-bias improves LF
common mode rejection by reducing capacitor
matching requirements by more than a factor of ten
over the simpler circuit wherein R
7
=0 Ω. The circuit
works well with the values shown.
Note also that the overall common-mode input
impedance of the circuit is dominated by the
phantom-power resistors (R
5
and R
6
). For the circuit
of Figure 5, this is approximately 5.9 kΩ per leg.
The 1510/1512 can be used as a line input re-
ceiver by adding attenuation to the preamplifier
inputs and changing the circuit topology to allow
switching of input, fixed attenuation, and gain
adjustment. The optimum circuit depends on the
specific requirements of the application. For more
details and specific applications advice, please
consult THAT's application notes, or our applications
engineers at the address and telephone below or via
email at apps_support@thatcorp.com.
Reference Terminal
The "Ref" pin provides a reference for the output
signal, and is normally connected to analog ground.
If necessary, the "Ref" pin can be used for offset
correction or DC level shifting. However, in order to
prevent spoiling the excellent common-mode
rejection of the 1510/1512, the source impedance
driving the "Ref" pin should be under 1 Ω.
Package Information
Both the THAT 1510 and 1512 are available in
8-pin SOIC, 8-pin DIP, and 14-pin SOIC packages.
The 1510 is also available in a 16-pin (widebody)
SOIC package. Other version/package combina-
tions will be considered based on customer
demand.
The package dimensions are shown in Figures
6, 7, 8, & 9, while pinouts are given in Table 1.
All versions of the 1510 and 1512 are lead free
and RoHS compliant. Material Declaration Data
Sheets on the parts are available at our web site,
www.thatcorp.com or upon request.
Figure 5. Recommended 1510 / 1512 Circuit with Phantom Power
RG
+In
Out
-In
RG2
RG1
U1
THAT
1510/1512
-In
+In
R1
1k2
R2
1k2
R7
22k
C1
470p
C2
470p
C3
47p
Out
C4
22u
C5
22u
D3
1N4004GP
D4
1N4004GP
D1
1N4004GP
D5
1N4148
D6
1N4148
D2
1N4004GP
+15
-15
R6
6k8
R5
6k8
+48V
R3
R4
10
-15
+15
C6
100n
C9
100n
Ref
V+
V-
10
CG
ON
THAT 1510/1512 Low-Noise Page 8 of 8 Document 600031 Rev 09
High Performance Audio Preamplifier
THAT Corporation; 45 Sumner Street; Milford, Massachusetts 01757-1656; USA
Tel: +1 508 478-9200; Fax +1 508 478-0990; Web: www.thatcorp.com
Copyright © 2017, THAT Corporation; All rights reserved.
Figure 6. 8-pin DIP package outline
Figure 7.16-pin SO Wide package outline
Figure 9. 14-pin SOIC package outline
Figure 8. 8-pin SOIC package outline
Revision History
Revision ECO Date Changes Page
07 2322 09/16/09 Added Max. Input Voltage specification. 2
08 2829 10/02/13 Corrected typographical error in specification table. 3
09 3003 05/10/17 Redrawn. Output Short Circuit Current spec corrected. —
B
A
K
F
H
ED
G
JC
ITEM
A
B
C
D
E
F
G
H
J
K
1
MILLIMETERS
9.52±0.10
6.35±0.10
7.49/8.13
0.46
2.54
3.68/4.32
0.25
3.18±0.10
8.13/9.40
3.30±0.10
INCHES
0.375±0.004
0.250±0.004
0.295/0.320
0.018
0.100
0.145/0.170
0.010
0.125±0.004
0.320/0.370
0.130±0.004
0.41/1.27H 0.016/0.05
0.228/0.244
0.0075/0.0098
0.053/0.068
0.014/0.018
0.189/0.196
INCHES
0.150/0.157
G
H
F
CB
D
F
G
D
E
A
B
C
ITEM MILLIMETERS
0.36/0.46
0.19/0.25
1.35/1.73
1.27
4.80/4.98
3.81/3.99
5.80/6.20
0.050
A
E
E
C
B
D
A
H
F
G
1
0.41/1.27H 0.016/0.05
0.228/0.244
0.0075/0.0098
0.053/0.068
0.014/0.018
0.337/0.346
INCHES
0.150/0.157
F
G
D
E
A
B
C
ITEM MILLIMETERS
0.36/0.46
0.19/0.25
1.35/1.73
1.27
8.56/8.79
3.81/3.99
5.80/6.20
0.050
