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AD831
Low Distortion Mixer
FUNCTIONAL BLOCK DIAGRAM
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FEATURES
Doubly Balanced Mixer
Low Distortion
+24 dBm Third Order Intercept (IP3)
+10 dBm 1 dB Compression Point
Low LO Drive Required: –10 dBm
Bandwidth
500 MHz RF and LO Input Bandwidths
250 MHz Differential Current IF Output
DC to >200 MHz Single-Ended Voltage IF Output
Single- or Dual-Supply Operation
DC Coupled Using Dual Supplies
All Ports May Be DC Coupled
No Lower Frequency Limit—Operation to DC
User-Programmable Power Consumption
APPLICATIONS
High Performance RF/IF Mixer
Direct to Baseband Conversion
Image-Reject Mixers
I/Q Modulators and Demodulators
PRODUCT DESCRIPTION
The AD831 is a low distortion, wide dynamic range, monolithic
mixer for use in such applications as RF to IF downconversion
in HF and VHF receivers, the second mixer in DMR base sta-
tions, direct-to-baseband conversion, quadrature modulation and
demodulation, and doppler shift detection in ultrasound imaging
applications. The mixer includes an LO driver and a low noise
output amplier and provides both user-programmable power
consumption and third order intercept point.
The AD831 provides a +24 dBm third order intercept point for
–10 dBm LO power, thus improving system performance and
reducing system cost compared to passive mixers, by eliminating
the need for a high power LO driver and its attendant shielding
and isolation problems.
The RF, IF, and LO ports may be dc or ac coupled when the
mixer is operating from ±5 V supplies or ac coupled when oper-
ating from a single-supply of 9 V minimum. The mixer operates
with RF and LO inputs as high as 500 MHz.
The mixer’s IF output is available as either a differential current
output or a single-ended voltage output. The differential output is
from a pair of open collectors and may be ac coupled via a trans-
former or capacitor to provide a 250 MHz output bandwidth. In
downconversion applications, a single capacitor connected across
these outputs implements a low-pass lter to reduce harmonics
directly at the mixer core, simplifying output ltering. When
building a quadrature-amplitude modulator or image reject mixer,
the differential current outputs of two AD831s may be summed
by connecting them together.
An integral low noise amplier provides a single-ended voltage
output and can drive such low impedance loads as lters, 50
amplier inputs, and A/D converters. Its small signal bandwidth
exceeds 200 MHz. A single resistor connected between pins
OUT and FB sets its gain. The amplier’s low dc offset allows
its use in such direct-coupled applications as direct-to-baseband
conversion and quadrature-amplitude demodulation.
The mixer’s SSB noise gure is 10.3 dB at 70 MHz using its
output amplier and optimum source impedance. Unlike passive
mixers, the AD831 has no insertion loss and does not require an
external diplexer or passive termination.
A programmable-bias feature allows the user to reduce power
consumption, with a reduction in the 1 dB compression point and
third-order intercept. This permits a tradeoff between dynamic
range and power consumption. For example, the AD831 may be
used as a second mixer in cellular and two-way radio base stations
at reduced power while still providing a substantial performance
improvement over passive solutions.
PRODUCT HIGHLIGHTS
1. –10 dBm LO Drive for a +24 dBm Output Referred Third
Order Intercept Point
2. Single-Ended Voltage Output
3. High Port-to-Port Isolation
4. No Insertion Loss
5. Single- or Dual-Supply Operation
6. 10.3 dB Noise Figure
REV. C
–2–
AD831–SPECIFICATIONS
AD831
–3–
Parameter Conditions Min Typ Max Unit
RF INPUT
Bandwidth –10 dBm Signal Level, IP3 ≥ +20 dBm 400 MHz
10.7 MHz IF and High Side Injection
See Figure 1
1 dB Compression Point 10 dBm
Common-Mode Range ±1 V
Bias Current DC Coupled 160 500 µA
DC Input Resistance Differential or Common Mode 1.3 k
Capacitance 2 pF
IF OUTPUT
Bandwidth Single-Ended Voltage Output, –3 dB
Level = 0 dBm, RL = 100 200 MHz
Conversion Gain Terminals OUT and VFB Connected 0 dB
Output Offset Voltage DC Measurement; LO Input Switched ±1 –40 +15 +40 mV
Slew Rate 300 V/µs
Output Voltage Swing RL = 100 , Unity Gain ±1.4 V
Short Circuit Current 75 mA
LO INPUT
Bandwidth –10 dBm Input Signal Level 400 MHz
10.7 MHz IF and High Side Injection
Maximum Input Level –1 +1 V
Common-Mode Range –1 +1 V
Minimum Switching Level Differential Input Signal 200 mV p-p
Bias Current DC Coupled 17 50 µA
Resistance Differential or Common Mode 500
Capacitance 2 pF
ISOLATION BETWEEN PORTS
LO-to-RF LO = 100 MHz, RS = 50 , 10.7 MHz IF 70 dB
LO-to-IF LO = 100 MHz, RS = 50 , 10.7 MHz IF 30 dB
RF-to-IF RF = 100 MHz, RS = 50 , 10.7 MHz IF 45 dB
DISTORTION AND NOISE LO = –10 dBm, f = 100 MHz, IF = 10.7 MHz
Third Order Intercept Output Referred, ±100 mV LO Input 24 dBm
Second Order Intercept Output Referred, ±100 mV LO Input 62 dBm
1 dB Compression Point RL = 100 , RBIAS = 10 dBm
Noise Figure, SSB Matched Input, RF = 70 MHz, IF = 10.7 MHz 10.3 dB
Matched Input, RF = 150 MHz, IF = 10.7 MHz 14 dB
POWER SUPPLIES
Recommended Supply Range Dual Supply ±4.5 ±5.5 V
Single Supply 9 11 V
Quiescent Current* For Best Third Order Intercept Point Performance 100 125 mA
BIAS Pin Open Circuited
*Quiescent current is programmable.
Specications subject to change without notice.
(TA = +25C and VS = 5 V unless otherwise noted;
all values in dBm assume 50 load.)
REV. C REV. C
–2–
AD831–SPECIFICATIONS
AD831
–3–
PIN DESCRIPTION
Pin No. Mnemonic Description
1 VP Positive Supply Input
2 IFN Mixer Current Output
3 AN Amplier Negative Input
4 GND Ground
5 VN Negative Supply Input
6 RFP RF Input
7 RFN RF Input
8 VN Negative Supply Input
9 VP Positive Supply Input
10 LON Local Oscillator Input
11 LOP Local Oscillator Input
12 VP Positive Supply Input
13 GND Ground
14 BIAS Bias Input
15 VN Negative Supply Input
16 OUT Amplier Output
17 VFB Amplier Feedback Input
18 COM Amplier Output Common
19 AP Amplier Positive Input
20 IFP Mixer Current Output
ABSOLUTE MAXIMUM RATINGS1
Supply Voltage ±VS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . ±5.5 V
Input Voltages
RFHI, RFLO . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .±3 V
LOHI, LOLO . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . ±1 V
Internal Power Dissipation2 . . . . . . . . . . . . . . . . . . . . 1200 mW
Operating Temperature Range
AD831A . . . . . . . . . . . . . . . . . . . . . . . . . . . . –40°C to +85°C
Storage Temperature Range . . . . . . . . . . . . . . –65°C to +150°C
Lead Temperature Range (Soldering 60 sec) . . . . . . . . . . 300°C
PIN CONFIGURATION
20-Lead PLCC
CAUTION
ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 V readily accumulate
on the human body and test equipment and can discharge without detection. Although the AD831 features
proprietary ESD protection circuitry, permanent damage may occur on devices subjected to high energy
electrostatic discharges. Therefore, proper ESD precautions are recommended to avoid performance
degradation or loss of functionality.
ORDERING GUIDE
Temperature Package Package
Model Range Description Option
AD831AP –40°C to +85°C 20-Lead PLCC P-20A
AD831AP-REEL7 –40°C to +85°C 20-Lead PLCC P-20A
AD831AP-EB Evaluation Board
NOTES
1 Stresses above those listed under Absolute Maximum Ratings may cause permanent
damage to the device. This is a stress rating only and functional operation of the
device at these or any other conditions above those indicated in the operational
section of this specication is not implied. Exposure to absolute maximum rating
conditions for extended periods may affect device reliability.
2 Thermal Characteristics:
20-Lead PLCC Package: JA = 110°C/W; JC = 20°C/W.
Note that the JA = 110°C/W value is for the package measured while suspended
in still air; mounted on a PC board, the typical value is JA = 90°C/W due to the
conduction provided by the AD831’s package being in contact with the board, which
serves as a heat sink.
REV. C REV. C
–4–
AD831–Typical Performance Characteristics AD831
–5–
65
64
60
63
62
61
10 1000100
FREQUENCY (MHz)
SECOND ORDER INTERCEPT (dBm)
TPC 4. Second Order Intercept vs. Frequency
90
70
0
50
30
20
10
80
60
40
10 1000100
FREQUENCY (MHz)
ISOLATION (dB)
TPC 5. LO-to-RF Isolation vs. Frequency
80
70
0
40
30
20
10
50
60
10 1000100
3 x RF – IF
2 x RF – IF
RF – IF
3 x RF – IF
2 x RF – IF
RF – IF
FREQUENCY (MHz)
FREQUENCY (dB)
TPC 6. RF-to-IF Isolation vs. Frequency
TPC 1. Third Order Intercept vs. Frequency,
IF Held Constant at 10.7 MHz
80
70
0
60
50
20
10
40
30
10 1000100
FREQUENCY (MHz)
ISOLATION (dB)
TPC 2. IF-to-RF Isolation vs. Frequency
60
50
0
40
30
20
10
10 1000100
LO
FREQUENCY (MHz)
ISOLATION (dB)
3 x LO – IF
2 x LO – IF
TPC 3. LO-to-IF Isolation vs. Frequency
REV. C REV. C
–4–
AD831–Typical Performance Characteristics AD831
–5–
12
10
0
10 1000100
8
6
4
2
FREQUENCY (MHz)
1dB COMPRESSION POINT (dBm)
TPC 7. 1 dB Compression Point vs. Frequency,
Gain = 1
12
10
0
10 1000100
8
6
4
2
FREQUENCY (MHz)
1dB COMPRESSION POINT (dBm)
TPC 8. 1 dB Compression Point vs. RF Input, Gain = 2
TPC 9. Third Order Intercept vs. Frequency,
LO Held Constant at 241 MHz
1.00
0.50
–1.00
0.00
–0.25
–0.75
0.75
0.25
–0.50
10 1000100
FREQUENCY (MHz)
THIRD ORDER INTERCEPT (dBm)
TPC 10. Gain Error vs. Frequency, Gain = 1
9
8
0
7
6
5
1
4
3
2
10 1000100
FREQUENCY (MHz)
THIRD ORDER INTERCEPT (dBm)
TPC 11. 1 dB Compression Point vs. Frequency, Gain = 4
11
10
70 600100 200 300 400 500
9
8
LO LEVEL = –10dBm
IF = 10.7MHz
VS = 8V
VS = 9V
FREQUENCY (MHz)
THIRD ORDER INTERCEPT (dBm)
TPC 12. Input 1 dB Compression Point vs.
Frequency, Gain = 1, 9 V Single Supply
REV. C REV. C
AD831
–6–
AD831
–7–
�
TPC 13. Input Third Order Intercept, 9 V Single Supply
�
TPC 14. Input Second Order Intercept, 9 V Single Supply
1200
1000
0
50 250100 150 200
800
600
400
200
4.0
3.5
3.0
2.5
2.0
INPUT CAPACITANCE
INPUT RESISTANCE
INPUT CAPACITANCE
FREQUENCY (MHz)
INPUT RESISTANCE ()
TPC 15. Input Impedance vs. Frequency, ZIN = R C
FREQUENCY (MHz)
18
NOISE FIGURE (dB)
16
8
50 250100 150 200
15
13
11
9
17
14
12
10
TPC 16. Noise Figure vs. Frequency,
Matched Input
REV. C
REV. C
AD831
–6–
AD831
–7–
THEORY OF OPERATION
The AD831 consists of a mixer core, a limiting amplier, a low
noise output amplier, and a bias circuit (Figure 1).
The mixer’s RF input is converted into differential currents by
a highly linear, Class A voltage-to-current converter, formed by
transistors Q1, Q2 and resistors R1, R2. The resulting currents
drive the differential pairs Q3, Q4 and Q5, Q6. The LO input is
through a high gain, low noise limiting amplier that converts the
–10 dBm LO input into a square wave. This square wave drives
the differential pairs Q3, Q4 and Q5, Q6 and produces a high
level output at IFP and IFN—consisting of the sum and differ-
ence frequencies of the RF and LO inputs—and a series of lower
level outputs caused by odd harmonics of the LO frequency mix-
ing with the RF input.
An on-chip network supplies the bias current to the RF and LO
inputs when these are ac-coupled; this network is disabled when
the AD831 is dc-coupled.
When the integral output amplier is used, pins IFN and IFP
are connected directly to pins AFN and AFP; the on-chip load
resistors convert the output current into a voltage that drives
the output amplier. The ratio of these load resistors to resistors
R1, R2 provides nominal unity gain (0 dB) from RF-to-IF. The
expression for the gain, in decibels, is
G
dB =Ê
Ë
Áˆ
¯
˜Ê
Ë
Áˆ
¯
˜Ê
Ë
Áˆ
¯
˜
20 4 1
2 2
10
log p
p
(1)
where:
4
p
is the amplitude of the fundamental component of a
squarewave.
1
2
is the conversion loss.
p
2
is the small signal dc gain of the AD831 when the LO input
is driven fully positive or negative.
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Figure 1. Simplied Schematic Diagram
REV. C
REV. C
AD831
–8–
AD831
–9–
Low-Pass Filtering
A simple low-pass lter may be added between the mixer and
the output amplier by shunting the internal resistive loads
(an equivalent resistance of about 14 with a tolerance of 20%)
with external capacitors; these attenuate the sum component in
a downconversion application (Figure 4). The corner frequency
of this one-pole low-pass lter (f = (2 RCF)–1) should be placed
about an octave above the difference frequency IF. Thus, for a
70 MHz IF, a –3 dB frequency of 140 MHz might be chosen,
using CF = (2 14 140 MHz)–1 82 pF, the nearest
standard value.
Figure 4. Low-Pass Filtering Using External Capacitors
Using the Output Amplier
The AD831’s output amplier converts the mixer core’s differential
current output into a single-ended voltage and provides an output
as high as ±1 V peak into a 50 V load (+10 dBm). For unity gain
operation (Figure 5), the inputs AN and AP connect to the open-
collector outputs of the mixer’s core and OUT connects to VFB.
��
Figure 5. Output Amplier Connected for Unity
Gain Operation
The mixer has two open-collector outputs (differential currents) at
pins IFN and IFP. These currents may be used to provide nominal
unity RF to IF gain by connecting a center-tapped transformer
(1:1 turns ratio) to pins IFN and IFP as shown in Figure 2.
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Figure 2. Connections for Transformer Coupling to
the IF Output
Programming the Bias Current
Because the AD831’s RF port is a Class-A circuit, the maximum
RF input is proportional to the bias current. This bias current
may be reduced by connecting a resistor from the BIAS pin to the
positive supply (Figure 3). For normal operation, the BIAS pin is
left unconnected. For lowest power consumption, the BIAS pin is
connected directly to the positive supply. The range of adjustment
is 100 mA for normal operation to 45 mA total current at minimum
power consumption.
Ω
Figure 3. Programming the Quiescent Current
REV. C
REV. C
AD831
–8–
AD831
–9–
For gains other than unity, the amplier’s output at OUT is
connected via an attenuator network to VFB; this determines
the overall gain. Using resistors R1 and R2 (Figure 6), the gain
setting expression is
G R R
R
dB =+
Ê
Ë
Áˆ
¯
˜
20 1 2
2
10
log
(2)
��
Figure 6. Output Amplier Feedback Connections
for Increasing Gain
Driving Filters
The output amplier can be used for driving reverse-terminated
loads. When driving an IF band-pass lter (BPF), for example,
proper attention must be paid to providing the optimal source
and load terminations so as to achieve the specied lter response.
The AD831’s wideband highly linear output amplier affords an
opportunity to increase the RF to IF gain to compensate for a
lter’s insertion and termination losses.
Figure 7 indicates how the output amplier’s low impedance
(voltage source) output can drive a doubly terminated band-pass
lter. The typical 10 dB of loss (4 dB of insertion loss and 6 dB
due to the reverse-termination) be made up by the inclusion of a
feedback network that increases the gain of the amplier by
10 dB (3.162). When constructing a feedback circuit, the signal
path between OUT and VFB should be as short as possible.
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Figure 7. Connections for Driving a Doubly Terminated
Band-Pass Filter
Higher gains can be achieved, using different resistor ratios, but
with concomitant reduction in the bandwidth of this amplier
(Figure 8). Note also that the Johnson noise of these gain setting
resistors, as well as that of the BPF terminating resistors, is ulti-
mately reected back to the mixer’s input; thus they should be as
small as possible, consistent with the permissible loading on the
amplier’s output.
FREQUENCY (MHz)
12
10
010 1000100
1dB COMPRESSION POINT (dBm)
8
6
4
2
G = 1
G = 2
G = 4
Figure 8. Output Amplier 1 dB Compression
Point for Gains of 1, 2, and 4 (Gains of 0 dB, 6 dB,
and 12 dB, Respectively)
REV. C
REV. C
AD831
–10–
AD831
–11–
The RF input to the AD831 is shown connected by an impedance
matching network for an assumed source impedance of 50 .
TPC 15 shows the input impedance of the AD831 plotted vs.
frequency. The input circuit can be modeled as a resistance in
parallel with a capacitance. The 82 pF capacitors (CF) connected
from IFN and IFP to VP provide a low-pass lter with a cutoff
frequency of approximately 140 MHz in down-conversion appli-
cations (see the Theory of Operation section for more details).
The LO input is connected single-ended because the limiting
amplier provides a symmetric drive to the mixer. To minimize
intermodulation distortion, connect pins OUT and VFB by the
shortest possible path. The connections shown are for unity-gain
operation.
At LO frequencies less than 100 MHz, the AD831’s LO power
may be as low as –20 dBm for satisfactory operation. Above
100 MHz, the specied LO power of –10 dBm must be used.
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Figure 9. Connections for ±5 V Dual-Supply Operation Showing Impedance
Matching Network and Gain of 2 for Driving Reverse-Terminated IF Filter
APPLICATIONS
Careful component selection, circuit layout, power supply
dc coupling, and shielding are needed to minimize the AD831’s
susceptibility to interference from radio and TV stations, etc. In
bench evaluation, we recommend placing all of the components
in a shielded box and using feedthrough decoupling networks for
the supply voltage.
Circuit layout and construction are also critical, since stray capaci-
tances and lead inductances can form resonant circuits and are a
potential source of circuit peaking, oscillation, or both.
Dual-Supply Operation
Figure 9 shows the connections for dual-supply operation. Supplies
may be as low as ±4.5 V but should be no higher than ±5.5 V, due
to power dissipation.
REV. C
REV. C
AD831
–10–
AD831
–11–
Single-Supply Operation
Figure 10 is similar to the dual-supply circuit in Figure 9. Supplies
may be as low as 9 V but should not be higher than 11 V, due to
power dissipation. As in Figure 9, both the RF and LO ports are
driven single-ended and terminated.
In single-supply operation, the COM terminal is the “ground”
reference for the output amplier and must be biased to half the
supply voltage, which is done by resistors R1 and R2. The OUT
pin must be ac-coupled to the load.
Figure 10. Connections for +9 V Single-Supply Operation
REV. C
REV. C
AD831
–12–
AD831
–13–
Connections Quadrature Demodulation
Two AD831 mixers may have their RF inputs connected in parallel
and have their LO inputs driven in phase quadrature (Figure 11)
to provide demodulated in-phase (I) and quadrature (Q) outputs.
The mixers’ inputs may be connected in parallel and a single
termination resistor used if the mixers are located in close prox-
imity on the PC board.
Figure 11. Connections for Quadrature Demodulation
REV. C
REV. C
AD831
–12–
AD831
–13–
Table I. AD831 Mixer Table, 4.5 V Supplies, LO = –9 dBm
LO Level –9.0 dBm, LO Frequency 130.7 MHz, Data File imdTB10771
RF Level 0.0 dBm, RF Frequency 120 MHz
Temperature Ambient
Dut Supply ±4.50 V
VPOS Current 90 mA
VNEG Current 91 mA
Intermodulation table RF harmonics (rows) LO harmonics (columns).
First row absolute value of nRF – mLO, and second row is the sum.
0 1 2 3 4 5 6 7
0 –32.7 –35.7 –21.1 –11.6 –19.2 –35.1 –41.9
–32.7 –35.7 –21.1 –11.6 –19.2 –35.1 –41.9
1 –31.6 0.0 –37.2 –41.5 –30.4 –34.3 –25.2 –40.1
–31.6 –28.5 –26.7 –28.0 –27.2 –33.2 –34.3 –44.8
2 –45.3 –48.2 –39.4 –57.6 –44.9 –42.4 –40.2 –40.2
–45.3 –42.4 –49.4 –42.5 –51.1 –46.2 –58.1 –61.6
3 –54.5 –57.1 –57.5 –50.6 –62.6 –55.8 –59.7 –55.2
–54.5 –65.5 –46.0 –63.7 –60.6 –69.6 –72.7 –73.5
4 –67.1 –63.1 –69.9 –69.9 –69.6 –74.1 –69.7 –58.6
–67.1 –53.6 –72.9 –71.2 –70.1 –72.6 –73.5 –72.7
5 –53.5 –62.6 –73.8 –72.3 –70.7 –71.1 –74.3 –73.0
–53.5 –68.4 –70.8 –72.8 –73.4 –73.2 –73.3 –72.5
6 –73.6 –57.7 –68.6 –73.1 –73.8 –73.0 –72.9 –74.4
–73.6 –73.5 –72.7 –73.5 –73.6 –73.1 –72.4 –73.7
7 –73.8 –73.9 –63.4 –72.6 –74.6 –74.9 –73.6 –74.5
–73.8 –73.8 –73.2 –73.8 –72.6 –73.7 –73.5 –72.9
Table II. AD831 Mixer Table, 5 V Supplies, LO = –9 dBm
LO Level –9.0 dBm, LO Frequency 130.7 MHz, Data File imdTB13882
RF Level 0.0 dBm, RF Frequency 120 MHz
Temperature Ambient
Dut Supply ±5.00 V
VPOS Current 102 mA
VNEG Current 102 mA
Intermodulation table RF harmonics (rows) LO harmonics (columns).
First row absolute value of nRF – mLO, and second row is the sum.
0 1 2 3 4 5 6 7
0 –36.5 –46.5 –33.0 –17.0 –23.0 –34.2 –45.6
–36.5 –46.5 –33.0 –17.0 –23.0 –34.2 –45.6
1 –37.5 0.0 –41.2 –41.1 –38.5 –29.0 –31.7 –47.4
–37.5 –29.1 –38.7 –22.9 –28.4 –35.3 –34.3 –52.4
2 –45.9 –45.2 –47.6 –61.5 –53.7 –43.5 –41.5 –41.8
–45.9 –39.4 –35.7 –38.4 –42.3 –53.7 –52.8 –66.3
3 –46.4 –53.0 –67.0 –43.0 –60.9 –47.9 –50.7 –41.0
–46.4 –40.0 –50.0 –48.9 –57.8 –57.0 –71.8 –67.4
4 –45.1 –56.0 –48.7 –64.6 –53.5 –55.7 –53.5 –51.1
–45.1 –39.0 –48.1 –58.4 –56.1 –63.8 –70.5 –67.6
5 –35.2 –45.3 –54.1 –54.1 –53.7 –57.9 –66.6 –64.3
–35.2 –53.0 –62.4 –67.3 –67.0 –69.4 –73.2 –72.9
6 –63.4 –41.1 –53.6 –66.5 –58.8 –63.3 –61.7 –71.4
–63.4 –66.3 –67.2 –67.5 –72.9 –71.2 –71.7 –73.2
7 –67.3 –65.8 –37.8 –54.6 –62.5 –71.7 –55.2 –57.1
–67.3 –61.6 –66.3 –72.9 –71.4 –70.7 –72.1 –73.1
REV. C
REV. C
AD831
–14–
AD831
–15–
Table III. AD831 Mixer Table, 3.5 V Supplies, LO = –20 dBm
LO Level –20.0 dBm, LO Frequency 130.7 MHz, Data File G1T1K 0771
RF Level 0.0 dBm, RF Frequency 120 MHz
Temperature Ambient
Dut Supply ±3.50 V
VPOS Current 55 mA
VNEG Current 57 mA
Intermodulation table RF harmonics (rows) LO harmonics (columns).
First row absolute value of nRF – mLO, and second row is the sum.
0 1 2 3 4 5 6 7
0 –45.2 –35.7 –16.1 –21.6 –22.3 –32.0 –36.4
–45.2 –35.7 –16.1 –21.6 –22.3 –32.0 –36.4
1 –30.3 0.0 –33.7 –47.9 –37.5 –33.8 –32.0 –45.2
–30.3 –29.7 –28.2 –24.4 –26.0 –47.4 –35.9 –49.7
2 –50.3 –49.4 –47.4 –49.9 –48.8 –38.5 –40.7 –51.
–50.3 –41.0 –51.4 –34.7 –49.8 –48.6 –68.5 –67.9
3 –48.4 –55.7 –58.2 –45.0 –57.0 –68.4 –55.5 –47.7
–48.4 –52.9 –50.0 –64.5 –62.8 –73.4 –74.0 –71.8
4 –66.7 –59.7 –67.2 –62.8 –58.2 –71.5 –72.9 –63.5
–66.7 –65.9 –78.1 –74.2 –77.5 –74.4 –77.9 –77.5
5 –66.9 –71.5 –73.6 –77.6 –70.8 –70.2 –75.8 –78.1
–66.9 –76.3 –78.1 –78.2 –78.1 –78.0 –77.9 –77.9
6 –78.0 –69.7 –76.7 –78.6 –78.8 –75.4 –78.1 –79.0
–78.0 –78.3 –78.3 –78.2 –78.1 –78.0 –77.9 –77.8
7 –78.4 –78.5 –76.9 –78.7 –79.0 –79.1 –78.6 –78.9
–78.4 –78.3 –78.2 –78.2 –77.9 –77.9 –77.8 –77.5
Table IV. AD831 Mixer Table, 5 V Supplies, 1 k Bias Resistor, LO = –20 dBm
LO Level –20.0 dBm, LO Frequency 130.7 MHz, Data File G1T1K 3881
RF Level 0.0 dBm, RF Frequency 120 MHz
Temperature Ambient
Dut Supply ±3.50 V
VPOS Current 59 mA
VNEG Current 61 mA
Intermodulation table RF harmonics (rows) LO harmonics (columns).
First row absolute value of nRF – mLO, and second row is the sum.
0 1 2 3 4 5 6 7
0 –60.6 –52.3 –16.6 –12.8 –26.0 –45.0 –38.8
–60.6 –52.3 –16.6 –12.8 –26.0 –45.0 –38.8
1 –34.1 0.0 –35.2 –41.8 –29.8 –29.1 –35.3 –49.0
–34.1 –27.3 –28.7 –20.7 –32.9 –39.2 –38.2 –47.8
2 –46.6 –48.8 –40.1 –52.2 –57.9 –38.6 –45.8 –47.7
–46.6 –37.8 –47.6 –41.7 –54.2 –50.4 –64.1 –64.9
3 –41.3 –58.8 –59.5 –41.8 –61.2 –58.1 –57.5 –54.0
–41.3 –47.9 –65.2 –62.5 –64.2 –73.8 –72.3 –72.6
4 –53.9 –52.5 –73.7 –68.1 –60.3 –71.0 –63.4 –62.3
–53.9 –61.4 –70.6 –76.9 –76.8 –78.6 –78.3 –78.1
5 –66.9 –65.8 –76.6 –75.2 –65.4 –70.0 –73.6 –68.7
–66.9 –69.7 –72.9 –77.4 –77.7 –78.5 –78.4 –78.2
6 –77.4 –73.3 –73.8 –78.8 –79.2 –73.6 –74.9 –79.3
–77.4 –78.6 –78.7 –78.6 –78.6 –78.4 –78.2 –78.2
7 –78.9 –79.0 –77.9 –78.0 –79.3 –79.5 –79.3 –79.3
–78.9 –78.8 –78.7 –78.6 –78.3 –78.3 –78.1 –78.0
REV. C
REV. C
AD831
–14–
AD831
–15–
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∑
Figure 12. Third Order Intercept Characterization Setup
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Figure 13. IF-to-RF Isolation Characterization Setup
REV. C
REV. C
C00882–0–6/03(C)
–16–
AD831
Revision History
Location Page
6/03–Data Sheet Changed from REV. B to REV. C.
Updated format . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . UNIVERSAL
Changes to Figure 10 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 11
Updated OUTLINE DIMENSIONS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 16
OUTLINE DIMENSIONS
20-Lead Plastic Leaded Chip Carrier [PLCC]
(P-20A)
Dimensions shown in inches and (millimeters)
0.020 (0.50)
R
BOTTOM
VIEW
(PINS UP)
0.040 (1.01)
0.025 (0.64)
0.021 (0.53)
0.013 (0.33)
0.330 (8.38)
0.290 (7.37)
0.032 (0.81)
0.026 (0.66)
0.056 (1.42)
0.042 (1.07) 0.20 (0.51)
MIN
0.120 (3.04)
0.090 (2.29)
3
4
19
18
8
9
14
13
TOP VIEW
(PINS DOWN)
0.395 (10.02)
0.385 (9.78) SQ
0.356 (9.04)
0.350 (8.89) SQ
0.048 (1.21)
0.042 (1.07)
0.048 (1.21)
0.042 (1.07)
0.020
(0.50)
R
0.050
(1.27)
BSC
0.180 (4.57)
0.165 (4.19)
COMPLIANT TO JEDEC STANDARDS MO-047AA
CONTROLLING DIMENSIONS ARE IN INCHES; MILLIMETER DIMENSIONS
(IN PARENTHESES) ARE ROUNDED-OFF INCH EQUIVALENTS FOR
REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN
REV. C
