w WM8973L
Stereo CODEC for Portable Audio Applications
WOLFSON MICROELECTRONICS plc
T
o receive regular email updates, sign up at http://www.wolfsonmicro.com/enews
Production Data, December 2011, Rev 4.5
Copyright 2011 Wolfso n Microelectronics plc
DESCRIPTION
The WM8973L is a low power, high quality stereo CODEC
designed for portable digital audio applications.
The device integrates complete interfaces to stereo or mono
microphones and a stereo headphone. External component
requirements are drastically reduced as no separate
microphone or headphone amplifiers are required.
Advanced on-chip digital signal processing performs graphic
equaliser, 3-D sound enhancement and automatic level
control for the microphone or line input.
The WM8973L can operate as a master or a slave, with
various master clock frequencies including 12 or 24MHz for
USB devices, or standard 256fs rates like 12.288MHz and
24.576MHz. Different audio sample rates such as 96kHz,
48kHz, 44.1kHz are generated directly from the master
clock without the need for an external PLL.
The WM8973L operates at supply voltages down to 1.8V,
although the digital core can operate at voltages down to
1.42V to save power, and the maximum for all supplies is
3.6 Volts. Different sections of the chip can also be powered
down under software control.
The WM8973L is supplied in a very small and thin 5x5mm
QFN package, ideal for use in hand-held and portable
systems.
FEATURES
DAC SNR 98dB (‘A’ weighted), THD –84dB at 48kHz, 3.3V
ADC SNR 95dB (‘A’ weighted), THD -82dB at 48kHz, 3.3V
Complete Stereo / Mono Microphone Interface
- Programmable ALC / Noise Gate
On-chip 400mW BTL Speaker Driver (mono)
On-chip Headphone Driver
- >40mW output power on 16 / 3.3V
- THD –80dB at 20mW, SNR 90dB with 16 load
- No DC blocking capacitors required (capless mode)
Separately mixed mono output
Digital Graphic Equaliser
Low Power
- 7mW stereo playback (1.8V / 1.5V supplies)
- 14mW record & playback (1.8V / 1.5V supplies)
Low Supply Voltages
- Analogue 1.8V to 3.6V
- Digital core: 1.42V to 3.6V
- Digital I/O: 1.8V to 3.6V
256fs / 384fs or USB master clock rates: 12MHz, 24MHz
Audio sample rates: 8, 11.025, 16, 22.05, 24, 32, 44.1, 48,
88.2, 96kHz generated internally from master clock
5x5x0.9mm QFN package
APPLICATIONS
MP3 Player / Recorder
AAC/WMA/Multi-Format Player / Recorder
Minidisc Player / Recorder
Portable Digital Music Systems
WM8973L Production Data
w PD, Rev 4.5, December 2011
2
BLOCK DIAGRAM
Production Data WM8973L
w PD, Rev 4.5, December 2011
3
TABLE OF CONTENTS
DESCRIPTION ....................................................................................................... 1
FEATURES ............................................................................................................ 1
APPLICATIONS ..................................................................................................... 1
BLOCK DIAGRAM ................................................................................................ 2
TABLE OF CONTENTS ......................................................................................... 3
PIN CONFIGURATION .......................................................................................... 5
ORDERING INFORMATION ........... .. ........... .. .. .. .. .. ... .. .. ........... .. .. .. ... .. .. .. .. ........... .. 5
PIN DESCRIPTION ................................................................................................ 6
ABSOLUTE MAXIMUM RATINGS ........................................................................ 7
RECOMMENDED OPERATION CONDITIONS ..................................................... 7
ELECTRICAL CHARACTERISTICS ........... .. .. .. ........... .. ........... ........... .. ........... .. .. 8
OUTPUT PGA’S LINEARITY ...................................... ............. ........................ ............. . 10
HEADPHONE OUTPUT THD VERSUS POWER .......................................................... 11
SPEAKER THD AN D NOISE VERSUS POWER ................ ........................................... 12
POWER CONSUMPTION ...... .. .. .. ... .. .. ........... .. .. .. ... .. .. .. .. ........... .. .. ... .. .. .. .. .. ......... 13
SIGNAL TIMING REQUI REMENTS ....................... .. ........... .. .. ........... .. .. ........... .. 14
SYSTEM CLOCK TIMI NG .................................... ......................... ........................ ......... 14
AUDIO INTERFACE TIMING – MASTER MODE .......................................................... 14
AUDIO INTERFACE TIMING – SLAVE MODE ........... ......................... .......................... 15
INTERNAL POWER ON RESET CIRCUIT ...... .. .. ... .. ........... .......... ........... ........... 18
DEVICE DESCRIPTION ...................................................................................... 19
INTRODUCTION ............................................................................................................ 19
INPUT SIGNAL PATH .................................................................................................... 19
AUTOMATIC LEVEL CONTROL (ALC) ................. ......................... ............ ................... 26
OUTPUT SIGNAL PATH ........................................... ......................... ............ ............ .... 30
ANALOGUE OUTPUTS ................................................................................................. 35
ENABLING THE OUTPUTS ........................................................................................... 37
HEADPHONE SWITCH.................................................................................................. 37
THERMAL SHUTDOWN ................................................................................................ 39
HEADPHONE OUTPUT ................................................................................................. 39
DIGITAL AUDIO INTERFACE ..... ............ ......................... ......................... ..................... 40
AUDIO INTERFACE CONTROL .................................................................................... 44
CLOCKING AND SAMPLE RATES ................................................................................ 46
CONTROL IN TERFACE...... ............. ............ ......................... ............ ......................... .... 48
POWER SUPPLIES ....................................................................................................... 49
POWER MANAGEMENT ............................................................................................... 49
REGISTER MAP .................................................................................................. 52
DIGITAL FILTER CHARACTERISTICS .............................................................. 53
TERMINOLOGY ............................................................................................................. 53
DAC FILTER RESPONSES ........................................................................................... 54
ADC FILTER RESPONSES ........................................................................................... 55
DE-EMPHASIS FILTER RESPONSES ..................................................... ..................... 56
HIGHPASS FILTER ....................................................................................................... 57
APPLICATIONS INFORMATION .................. .. .. .. ........... .. .. ... .. .. ........... .. .. .. ... .. .... 58
RECOMMENDED EXTERNAL COMPONEN TS ............ ..................................... ........... 58
LINE INPUT CONFIGURATION ..................................................................................... 59
MICROPHONE INPUT CONFIGURATION ........................................ ........................ .... 59
MINIMISING PO P NOISE AT THE ANALOGUE OUTPUTS............................... ........... 59
POWER MANAGEMENT EXAMPLES ........................................................................... 60
WM8973L Production Data
w PD, Rev 4.5, December 2011
4
IMPORTANT NOTICE ........... .. .. .. ... .......... ... .. .. .. .. ........... .. ... .. .. .. ........... .. .. .. ... .. .... 62
ADDRESS ...................................................................................................................... 62
REVISION HISTORY ........................................................................................... 63
Production Data WM8973L
w PD, Rev 4.5, December 2011
5
PIN CONFIGURATION
ORDERING INFORMATIO N
ORDER CODE TEMPERATURE
RANGE PACKAGE MOISTURE
SENSITIVITY LEVEL PEAK SOLDERING
TEMPERATURE
WM8973CLGEFL/V -25C to +85C 32-lead QFN (5x5x0.9mm)
(Pb-free) MSL3 260oC
WM8973CLGEFL/RV -25C to +85C 32-lead QFN (5x5x0.9mm)
(Pb-free, tape and reel) MSL3 260oC
Note:
Reel quantity = 3500
WM8973L Production Data
w PD, Rev 4.5, December 2011
6
PIN DESCRIPTION
PIN NO NAME TYPE DESCRIPTION
1 MCLK
Digital Input Master Clock
2 DCVDD
Supply Digital Core Supply
3 DBVDD
Supply Digital Buffer (I/O) Supply
4 DGND
Supply Digital Ground (return path for both DCVDD and DBVDD)
5 BCLK
Digital Input / Output Audio Interface Bit Clock
6 DACDAT
Digital Input DAC Digital Audio Data
7 DACLRC
Digital Input / Output Audio Interface Left / Right Clock/Clock Out
8 ADCDAT
Digital Output ADC Digital Audio Data
9 ADCLRC
Digital Input / Output Audio Interface Left / Right Clock
10 MONOOUT
Analogue Output Mono Output
11 OUT3
Analogue Output Analogue Output 3 (can be used as Headphone Pseudo Ground)
12 ROUT1
Analogue Output Right Output 1 (Line or Headphone)
13 LOUT1
Analogue Output Left Output 1 (Line or Headphone)
14 HPGND
Supply Supply for Analogue Output Drivers (LOUT1/2, ROUT1/2)
15 ROUT2
Analogue Output Right Output 1 (Line or Headphone or Speaker)
16 LOUT2
Analogue Output Left Output 1 (Line or Headphone or Speaker)
17 HPVDD
Supply Supply for Analogue Output Drivers (LOUT1/2, ROUT1/2, MONOUT)
18 AVDD
Supply Analogue Supply
19 AGND
Supply Analogue Ground (return path for both AVDD)
20 VREF
Analogue Output Reference Voltage Decoupling Capacitor
21 VMID
Analogue Output Midrail Voltage Decoupling Capacitor
22 MICBIAS
Analogue Output Microphone Bias
23 RINPUT3 /
HPDETECT Analogue Input Right Channel Input 3 or Headphone Plug-in Detection
24 LINPUT3
Analogue Input Left Channel Input 3
25 RINPUT2
Analogue Input Right Channel Input 2
26 LINPUT2
Analogue Input Left Channel Input 2
27 RINPUT1
Analogue Input Right Channel Input 1
28 LINPUT1
Analogue Input Left Channel Input 1
29 MODE
Digital Input Control Interface Selection
30 CSB
Digital Input Chip Select / Device Address Selection
31 SDIN
Digital Input/Output Control Interface Data Input / 2-wire Acknowledge output
32 SCLK Digital Input Control Interface Clock Input
Note:
It is recommended that the QFN ground paddle should be connected to analogue ground on the application PCB.
Production Data WM8973L
w PD, Rev 4.5, December 2011
7
ABSOLUTE MAXIMUM RATINGS
Absolute Maximum Ratings are stress ratings only. Permanent damage to the device may be caused by continuously
operating at or beyond these limits. Device functional operating limits and guaranteed performance specifications are given
under Electrical Characteristics at the test conditions specified.
ESD Sensitive Device. This device is manufactured on a CMOS process. It is therefore generically susceptible
to damage from excessive static voltages. Proper ESD precautions must be taken during handling and storage
of this device.
Wolfson tests its package types according to IPC/JEDEC J-STD-020B for Moisture Sensitivity to determine acceptable storage
conditions prior to surface mount assembly. These levels are:
MSL1 = unlimited floor life at <30C / 85% Relative Humidity. Not normally stored in moisture barrier bag.
MSL2 = out of bag storage for 1 year at <30C / 60% Relative Humidity. Supplied in moisture barrier bag.
MSL3 = out of bag storage for 168 hours at <30C / 60% Relative Humidity. Supplied in moisture barrier bag.
The Moisture Sensitivity Level for each package type is specified in Ordering Information.
CONDITION MIN MAX
Supply voltages -0.3V +3.63V
Voltage range digital inputs DGND -0.3V DBVDD +0.3V
Voltage range analogue inputs AGND -0.3V AVDD +0.3V
Operating temperature range, TA -25C +85C
Storage temperature after soldering -65C +150C
Notes
1. Analogue and digital grounds must always be within 0.3V of each other.
2. All digital and analogue supplies are completely independent from each other.
3. DCVDD must be less than or equal to AVDD and DBVDD.
RECOMMENDED OPERATION CONDITIONS
PARAMETER SYMBOL MIN TYP MAX UNIT
Digital supply range (Core) DCVDD 1.42 2.0 3.6 V
Digital supply range (Buffer) DBVDD 1.7 2.0 3.6 V
Analogue supplies range AVDD, HPVDD 1.8 2.0 3.6 V
Ground DGND,AGND, HPGND 0 V
WM8973L Production Data
w PD, Rev 4.5, December 2011
8
ELECTRICAL CHARACTERISTICS
Test Conditions
DCVDD = 1.5V, DBVDD = 3.3V, AVDD = HPVDD = 3.3V, TA = +25oC, 1kHz signal, fs = 48kHz, PGA gain = 0dB, 24-bit audio
data unless otherwise stated.
PARAMETER SYMBOL TEST CONDITIONS MIN TYP MAX UNIT
Analogue Inputs (LINPUT1, RINPUT1, LINPUT2, RINPUT2, LINPUT3, RINPUT3) to ADC out
Full Scale Input Signal Level
(for ADC 0dB Input at 0dB Gain) VINFS AVDD = 3.3V 1.0 V rms
AVDD = 1.8V 0.545
Input Resistance L/RINPUT1 to ADC,
PGA gain = 0dB 22 k
L/RINPUT1 to ADC,
PGA gain = +30dB 1.5
L/RINPUT1 unused
DC Measurement 16
L/RINPUT1 unused 17
Input Capacitance 10 pF
Signal to Noise Ratio
(A-weighted) SNR AVDD = 3.3V 80 95 dB
AVDD = 1.8V 90
Dynamic Range -60dBFs 90 95 dB
Total Harmonic Distortion THD -1dBFs input,
AVDD = 3.3V -82
0.008 dB
%
-1dBFs input,
AVDD = 1.8V -74
0.02
ADC Channel Separation 1kHz signal 85 dB
Channel Matching 1kHz signal 0.2 dB
Analogue Outputs (LOUT1/2, ROUT1/2, MONOOUT)
0dB Full scale output voltage AVDD/3.3 Vrms
Mute attenuation 1kHz, full scale signal 90 dB
MONOOUT pin 81
Channel Separation analogue in
to analogue out 85 dB
DAC to Line-Out (L/ROUT2 with 10k / 50pF load)
Signal to Noise Ratio
(A-weighted) SNR AVDD=3.3V 90 98 dB
AVDD=1.8V 93
Total Harmonic Distortion THD AVDD=3.3V -84 dB
AVDD=1.8V -80
Channel Separation 1kHz signal 100 dB
Headphone Output (LOUT1/ROUT1, using capacitors)
Output Power per channel PO Output power is very closely correlated with THD; see below.
Total Harmonic Distortion THD HPVDD=1.8V, RL=32
PO=5mW 0.016
-76 %
dB
HPVDD=1.8V, RL=16
PO=5mW 0.022
-73
HPVDD=3.3V, RL=32,
PO=20mW 0.013
-78
HPVDD=3.3V, RL=16,
PO=20mW 0.018
-75
Signal to Noise Ratio
(A-weighted) SNR HPVDD = 3.3V 92 96 dB
HPVDD = 1.8V 96
Production Data WM8973L
w PD, Rev 4.5, December 2011
9
Test Conditions
DCVDD = 1.5V, DBVDD = 3.3V, AVDD = HPVDD = 3.3V, TA = +25oC, 1kHz signal, fs = 48kHz, PGA gain = 0dB, 24-bit audio
data unless otherwise stated.
PARAMETER SYMBOL TEST CONDITIONS MIN TYP MAX UNIT
Speaker Output (LOUT2/ROUT2 with 8 bridge tied load, ROUT2INV=1)
Output Power at 1% THD PO THD = 1% 330 mW (rms)
Abs. Max Power Ouptut POmax 500 mW (rms)
Total Harmonic Distortion THD Po=200mW, RL=8,
HPVDD=3.3V -63
0.07 dB
%
Signal to Noise Ratio
(A-weighted) SNR HPVDD=3.3V, RL=8 95 dB
Analogue Reference Levels
Midrail Reference Voltage VMID –3% AVDD/2 +3% V
Buffered Reference Voltage VREF –3% AVDD/2 +3% V
Microphone Bias
Bias Voltage VMICBIAS 3mA load current –5% 0.9AVDD + 5% V
Bias Current Source IMICBIAS 3 mA
Output Noise Voltage Vn 1K to 20kHz 15 nV/Hz
Digital Input / Output
Input HIGH Level VIH 0.7DBVDD V
Input LOW Level VIL 0.3DBVDD V
Output HIGH Level VOH I
OH = +1mA 0.9DBVDD V
Output LOW Level VOL I
OL = -1mA 0.1DBVDD V
HPDETECT (pin 23)
Input HIGH Level VIH 0.7AVDD V
Input LOW Level VIL 0.3AVDD V
WM8973L Production Data
w PD, Rev 4.5, December 2011
10
OUTPUT PGA’S LINEARITY
Output PGA Gains
-70.000
-60.000
-50.000
-40.000
-30.000
-20.000
-10.000
0.000
10.000
40 50 60 70 80 90 100 110 120 130
XXXVOL Register Setting (binary)
Measured Gain [dB]
LOUT1
ROUT1
LOUT2
ROUT2
MONOOUT
Output PGA Gain Step Size
0.000
0.250
0.500
0.750
1.000
1.250
1.500
1.750
2.000
40 50 60 70 80 90 100 110 120 130
XXXVOL Register Setting (binary)
Step Size [dB]
LOUT1
ROUT1
LOUT2
ROUT2
MONOOUT
Production Data WM8973L
w PD, Rev 4.5, December 2011
11
HEADPHONE OUTPUT THD VERSUS POWER
Headp hone Power vs THD+N (32Ohm load)
-100
-80
-60
-40
-20
0
0 5 10 15 20 25 30
Power (mW)
THD+N (dB
)
AVDD=1.8V
AVDD=1.8V, capless
AVDD=3.3V
AVDD=3.3V, capless
Headphone Power vs THD+N (16Ohm l oad)
-100
-80
-60
-40
-20
0
0 102030405060
Power (mW)
THD+N (dB
)
AVDD=1.8V
AVDD=1.8V, capless
AVDD=3.3V
AVDD=3.3V, capless
WM8973L Production Data
w PD, Rev 4.5, December 2011
12
SPEAKER THD AND NOISE VERSUS POWER
Production Data WM8973L
w PD, Rev 4.5, December 2011
13
POWER CONSUMPTION
The power consumption of the WM8973L depends on the following factors.
Supply voltages: Reducing the supply voltages also reduces supply currents, and therefore results in significant power
savings, especially in the digital sections of the WM8973L.
Operating mode: Significant power savings can be achieved by always disabling parts of the WM8973L that are not
used (e.g. mic pre-amps, unused outputs, DAC, ADC, etc.)
Control Register R23 Other settings Tot. Power
Bit
VMIDSEL
VREF
AINL
AINR
ADCL
ADCR
MICB
DACL
DACR
LOUT1
ROUT1
LOUT2
ROUT2
MONO
OUT3
ADCOSR
DACOSR
VSEL
V I (mA) V I (mA) V I (mA) V I (mA) mW
OFF 00000000000 0000 00011 Clocks stopped 3.30.00163.30.01903.30.00803.30.0002 0.0950
01 2.5 0.0008 2.5 0.0170 2.5 0.0050 2.5 0.0000 0.0570
00 1.8 0.0005 1.5 0.0120 1.8 0.0350 1.8 0.0000 0.0819
Standby 10100000000000000011 Interface Stopped 3.30.39003.30.03903.30.00803.30.0000 1.4421
(500 KOhm VMID string) 01 2.5 0.2880 2.5 0.0170 2.5 0.0050 2.5 0.0000 0.7750
00 1.8 0.1970 1.5 0.0120 1.8 0.0036 1.8 0.0000 0.3791
Playback to Line-out 01100000110011000011 3.33.73103.35.66003.30.30003.30.2370 32.7624
01 2.5 2.6940 2.5 3.8600 2.5 0.2200 2.5 0.2100 17.4600
00 1.8 1.8820 1.5 2.1400 1.8 0.1488 1.8 0.1500 7.1354
Playback to Line-out 01100000111100000111 3.33.51703.34.64703.30.30003.30.9500 31.0662
(64x oversampling mode) 01 2.5 2.5760 2.5 3.2030 2.5 0.2200 2.5 0.6480 16.6175
00 1.8 1.7760 1.5 1.7590 1.8 0.1488 1.8 0.4130 6.8465
Playback to 16 Ohm Headphone01100000111100000011 3.33.72603.35.67003.30.30003.30.9530 35.1417
01 2.5 2.7530 2.5 3.9250 2.5 0.2200 2.5 0.6570 18.8875
00 1.8 1.8900 1.5 2.1410 1.8 0.1488 1.8 0.4150 7.6283
Playback to 16 Ohm Headphone01100000111100010011 R24, OUT3SW=00 3.33.70603.35.64003.30.30003.31.4040 36.4650
(capless mode using OUT3) 01 2.5 2.7130 2.5 3.9000 2.5 0.2200 2.5 0.9600 19.4825
00 1.8 1.8870 1.5 2.1410 1.8 0.1488 1.8 0.6140 7.9811
Playback to 8 Ohm BTL Speake
r
01100000110011000011 R24, ROUT2INV=1 3.33.88203.35.64703.30.30003.30.2830 33.3696
01 2.5 2.8780 2.5 3.9390 2.5 0.2200 2.5 0.2100 18.1175
00 1.8 1.9800 1.5 2.1630 1.8 0.1488 1.8 0.1510 7.3481
Headphone Amp 01100000001100000011 Clocks Stopped 3.31.84003.30.02003.30.00803.30.9540 9.3126
(line-in to 16 Ohm headphone) 01 2.5 1.3300 2.5 0.0190 2.5 0.0050 2.5 0.6400 4.9850
00 1.8 0.9300 1.5 0.0130 1.8 0.0036 1.8 0.4100 2.4380
Speaker Amp 01100000000011000011 Clocks Stopped 3.31.97803.30.02003.30.00803.30.3310 7.7121
(line-in to 8 Ohm speaker) 01 R24, ROUT2INV=1 2.5 1.4300 2.5 0.0190 2.5 0.0050 2.5 0.2430 4.2425
00 1.8 0.9860 1.5 0.0130 1.8 0.0036 1.8 0.1760 2.1176
Phone Call 01100001000011100011 Clocks Stopped 3.32.52303.30.03703.30.00803.30.4420 9.9330
(mono line-in to headphone, 01 2.5 1.8520 2.5 0.0190 2.5 0.0050 2.5 0.3200 5.4900
mic to MONOOUT) 00 1.8 1.2900 1.5 0.0130 1.8 0.0036 1.8 0.2240 2.7512
Record from Line-in 01111110000000000011 3.38.66003.36.57003.30.33303.30.0000 51.3579
01 2.5 7.7100 2.5 4.2800 2.5 0.2320 2.5 0.0000 30.5550
00 1.8 6.8000 1.5 2.2100 1.8 0.1620 1.8 0.0000 15.8466
Record from Line-in 01111110000000001011 3.35.07203.35.91003.30.33903.30.0000 37.3593
(64x oversampling mode) 01 2.5 4.2550 2.5 3.7500 2.5 0.2320 2.5 0.0000 20.5925
00 1.8 3.5900 1.5 1.9100 1.8 0.1620 1.8 0.0000 9.6186
Record from mono microphone 01110101000000000011R32, LMICBOOST=11;3.34.93303.36.54003.30.33903.30.0000 38.9796
01 R23, DATSEL=01 2.5 4.2970 2.5 4.2500 2.5 0.2400 2.5 0.0000 21.9675
00 1.8 3.7210 1.5 2.2200 1.8 0.1644 1.8 0.0000 10.3237
Record from mono microphone 01110101000000000011R32, LMICBOOST=11;3.35.29003.36.50003.30.32203.30.0000 39.9696
(differential) 01 R23, DATSEL=01; 2.5 4.5600 2.5 4.2700 2.5 0.2400 2.5 0.0000 22.6750
00 R32, LINSEL=11 1.8 3.9000 1.5 2.2200 1.8 0.1656 1.8 0.0000 10.6481
Stereo Record & Playback 01111111110011000011 3.311.9273.310.8703.30.33203.30.2820 77.2563
01 2.5 10.112 2.5 7.3600 2.5 0.2340 2.5 0.2060 44.7800
00 1.8 7.3910 1.5 4.0610 1.8 0.1584 1.8 0.1480 19.9468
Stereo Record & Playback 01111111110011001111 3.38.10903.39.33003.30.33303.30.2820 59.5782
(64x oversampling mode) 01 2.5 6.5500 2.5 6.3020 2.5 0.2340 2.5 0.2070 33.2325
00 1.8 4.7000 1.5 3.3800 1.8 0.1584 1.8 0.1490 14.0833
DBVDD HPVDDR24R25 (19h) R26 (1Ah) AVDD DCVDD
Table 1 Supply Current Consumption
Notes:
1. All figures are at TA = +25oC, Slave Mode, fs = 48kHz, MCLK = 12.288 MHz (256fs), with zero signal (quiescent)
2. The power dissipated in the headphone or speaker is not included in the above table.
WM8973L Production Data
w PD, Rev 4.5, December 2011
14
SIGNAL TIMING REQUIREMENTS
SYSTEM CLOCK TIMING
MCLK
t
MCLKL
t
MCLKH
t
MCLKY
Figure 1 System Clock Timing Requirements
Test Conditions
CLKDIV2=0, DCVDD = 1.42V, DBVDD = 3.3V, DGND = 0V, TA = +25oC, Slave Mode fs = 48kHz, MCLK = 384fs, 24-bit data,
unless otherwise stated.
PARAMETER SYMBOL MIN TYP MAX UNIT
System Clock Timing Information
MCLK System clock pulse width high TMCLKL 21 ns
MCLK System clock pulse width low TMCLKH 21 ns
MCLK System clock cycle time TMCLKY 54 ns
MCLK duty cycle TMCLKDS 60:40 40:60
Test Conditions
CLKDIV2=1, DCVDD = 1.42V, DBVDD = 3.3V, DGND = 0V, TA = +25oC, Slave Mode fs = 48kHz, MCLK = 384fs, 24-bit data,
unless otherwise stated.
PARAMETER SYMBOL MIN TYP MAX UNIT
System Clock Timing Information
MCLK System clock pulse width high TMCLKL 10 ns
MCLK System clock pulse width low TMCLKH 10 ns
MCLK System clock cycle time TMCLKY 27 ns
AUDIO INTERFACE TIMING – MASTER MODE
BCLK
(Output)
ADCDAT
ADCLRC/
DACLRC
(Outputs)
t
DL
DACDAT
t
DDA
t
DHT
t
DST
Figure 2 Digital Audio Data Timing – Master Mode (see Control Interface)
Production Data WM8973L
w PD, Rev 4.5, December 2011
15
Test Conditions
DCVDD = 1.42V, DBVDD = 3.3V, DGND = 0V, TA = +25oC, Slave Mode, fs = 48kHz, MCLK = 256fs, 24-bit data, unless
otherwise stated.
PARAMETER SYMBOL MIN TYP MAX UNIT
Bit Clock Timing Information
BCLK rise time (10pF load) tBCLKR 3 ns
BCLK fall time (10pF load) tBCLKF 3 ns
BCLK duty cycle (normal mode, BCLK = MCLK/n) tBCLKDS 50:50
BCLK duty cycle (USB mode, BCLK = MCLK) tBCLKDS T
MCLKDS
Audio Data Input Timing Information
ADCLRC/DACLRC propagation delay from BCLK falling edge tDL 10 ns
ADCDAT propagation delay from BCLK falling edge tDDA 10 ns
DACDAT setup time to BCLK rising edge tDST 10 ns
DACDAT hold time from BCLK rising edge tDHT 10 ns
AUDIO INTERFACE TIMING – SLAVE MODE
BCLK
DACLRC/
ADCLRC
t
BCH
t
BCL
t
BCY
DACDAT
ADCDAT
t
LRSU
t
DS
t
LRH
t
DH
t
DD
Figure 3 Digital Audio Data Timing – Slave Mode
Test Conditions
DCVDD = 1.42V, DBVDD = 3.3V, DGND = 0V, TA = +25oC, Slave Mode, fs = 48kHz, MCLK = 256fs, 24-bit data, unless
otherwise stated.
PARAMETER SYMBOL MIN TYP MAX UNIT
Audio Data Input Timing Information
BCLK cycle time tBCY 50 ns
BCLK pulse width high tBCH 20 ns
BCLK pulse width low tBCL 20 ns
ADCLRC/DACLRC set-up time to BCLK rising edge tLRSU 10 ns
ADCLRC/DACLRC hold time from BCLK rising edge tLRH 10 ns
DACDAT hold time from BCLK rising edge tDH 10 ns
ADCDAT propagation delay from BCLK falling edge tDD 10 ns
Note:
BCLK period should always be greater than or equal to MCLK period.
WM8973L Production Data
w PD, Rev 4.5, December 2011
16
CONTROL INTERFACE TIMING – 3-WIRE MODE
CSB
SCLK
SDIN
t
CSL
t
DHO
t
DSU
t
CSH
t
SCY
t
SCH
t
SCL
t
SCS
LSB
t
CSS
Figure 4 Control Interface Timing – 3-Wire Serial Control Mode
Test Conditions
DCVDD = 1.42V, DBVDD = 3.3V, DGND = 0V, TA = +25oC, Slave Mode, fs = 48kHz, MCLK = 256fs, 24-bit data, unless
otherwise stated.
PARAMETER SYMBOL MIN TYP MAX UNIT
Program Register Input Information
SCLK rising edge to CSB rising edge tSCS 80 ns
SCLK pulse cycle time tSCY 200 ns
SCLK pulse width low tSCL 80 ns
SCLK pulse width high tSCH 80 ns
SDIN to SCLK set-up time tDSU 40 ns
SCLK to SDIN hold time tDHO 40 ns
CSB pulse width low tCSL 40 ns
CSB pulse width high tCSH 40 ns
CSB rising to SCLK rising tCSS 40 ns
Pulse width of spikes that will be suppressed tps 0 5 ns
Production Data WM8973L
w PD, Rev 4.5, December 2011
17
CONTROL INTERFACE TIMING – 2-WIRE MODE
SDIN
SCLK
t
3
t
1
t
6
t
2
t
7
t
5
t
4
t
3
t
8
t
9
Figure 5 Control Interface Timing – 2-Wire Serial Control Mode
Test Conditions
DCVDD = 1.42V, DBVDD = 3.3V, DGND = 0V, TA = +25oC, Slave Mode, fs = 48kHz, MCLK = 256fs, 24-bit data, unless
otherwise stated.
PARAMETER SYMBOL MIN TYP MAX UNIT
Program Register Input Information
SCLK Frequency 0 400 kHz
SCLK Low Pulse-Width t1 1.3 us
SCLK High Pulse-Width t2 600 ns
Hold Time (Start Condition) t3 600 ns
Setup Time (Start Condition) t4 600 ns
Data Setup Time t5 100 ns
SDIN, SCLK Rise Time t6 300 ns
SDIN, SCLK Fall Time t7 300 ns
Setup Time (Stop Condition) t8 600 ns
Data Hold Time t9 900 ns
Pulse width of spikes that will be suppressed tps 0 5 ns
WM8973L Production Data
w PD, Rev 4.5, December 2011
18
INTERNAL POWER ON RESET CIRCUIT
VDD
T1
GND
AVDD
DCVDD
DGND
Internal PORB
Power on Reset
Circuit
Figure 6 Internal Power on Reset Circuit Schematic
The WM8973 includes an internal Power-On-Reset Circuit, as shown in Figure 6, which is used to
reset the digital logic into a default state after power up. The power on reset circuit is powered from
DCVDD and monitors DCVDD and AVDD. It asserts PORB low if DCVDD or AVDD are below a
minimum threshold.
Figure 7 Typical Power-Up Sequence
Figure 7 shows a typical power-up sequence. When DCVDD and AVDD rise above the minimum
thresholds, Vpord_dcvdd and Vpord_avdd, there is enough voltage for the circuit to guarantee the
Power on Reset is asserted low and the chip is held in reset. In this condition, all writes to the control
interface are ignored. When DCVDD rises to Vpor_dcvdd_on and AVDD rises to Vpor_avdd_on,
PORB is released high and all registers are in their default state and writes to the control interface
may take place. If DCVDD and AVDD rise at different rates then PORB will only be released when
DCVDD and AVDD have both exceeded the Vpor_dcvdd_on and Vpor_avdd_on thresholds.
On power down, PORB is asserted low whenever DCVDD drops below the minimum threshold
Vpor_dcvdd_off or AVDD drops below the minimum threshold Vpor_avdd_off.
SYMBOL MIN TYP MAX UNIT
Vpord_dcvdd 0.4 0.6 0.8 V
Vpor_dcvdd_on 0.9 1.26 1.6 V
Vpor_avdd_on 0.5 0.7 0.9 V
Vpor_avdd_off 0.4 0.6 0.8 V
Table 2 Typical POR Operation (typical values, not tested)
Production Data WM8973L
w PD, Rev 4.5, December 2011
19
DEVICE DESCRIPTION
INTRODUCTION
The WM8973L is a low power audio CODEC offering a combination of high quality audio, advanced
features, low power and small size. These characteristics make it ideal for portable digital audio
applications such as MP3 and minidisk player / recorders. Stereo 24-bit multi-bit delta sigma ADCs
and DACs are used with oversampling digital interpolation and decimation filters.
The device includes three stereo analogue inputs that can be switched internally. Each can be used
as either a li ne level input or microphone input and LINPUT1/RINPUT1 and LINPUT2/RINPUT2 can
be configured as mono differential inputs. A programmable gain amplifier with automatic level control
(ALC) keeps the recording volume constant. The on-chip stereo ADC and DAC are of a high quality
using a multi-bit, low-order oversampling architecture to deliver optimum performance with low power
consumption.
The DAC output signal first enters an analogue mixer where an analogue input and/or the post-ALC
signal can be added to it. This mix is available on line and headphone outputs.
The WM8973L has a configurable digital audio interface where ADC data can be read and digital
audio playback data fed to the DAC. It supports a number of audio data formats including I2S, DSP
Mode (a burst mode in which frame sync plus 2 data packed words are transmitted), MSB-First, left
justified and MSB-First, right justified, and can operate in master or slave modes.
The WM8973L uses a unique clocking scheme that can generate many commonly used audio sample
rates from either a 12.00MHz USB clock or an industry standard 256/384 fs clock. This feature
eliminates the common requirement for an external phase-locked loop (PLL) in applications where the
master clock is not an integer multiple of the sample rate. Sample rates of 8kHz, 11.025kHz, 12kHz,
16kHz, 22.05kHz, 24kHz, 32kHz, 44.1kHz, 48kHz, 88.2k Hz and 96kHz can be generated. The digital
filters used for recording and playback are optimised for each sampling rate used.
To allow full software control over all its features, the WM8973L offers a choice of 2 or 3 wire MPU
control interface. It is fully compatible and an ideal partner for a wide range of industry standard
microprocessors, controllers and DSPs.
The design of the WM8973L has given much attention to power consumption without compromising
performance. It operates at very low voltages, and includes the ability to power off parts of the
circuitry under software control, including standby and power off modes.
INPUT SIGNAL PATH
The input signal path for each channel consists of a switch to select between three analogue inputs,
followed by a PGA (programmable gain amplifier) and an optional microphone gain boost. A
differential input of either (LINPUT1 – RINPUT1) or (LINPUT2 – RINPUT2) may also be selected. The
gain of the PGA can be controlled either by the user or by the on-chip ALC function (see Automatic
Level Control).
The signal then enters an ADC where it is digitised. Alternatively, the two channels can also be mixed
in the analogue domain and digitised in one ADC while the other ADC is switched off. The mono-mix
signal appears on both digital output channels.
SIGNAL INPUTS
The WM8973L has three sets of high impedance, low capacitance AC coupled analogue inputs,
LINPUT1/RINPUT1, LINPUT2/RINPUT2 and LINPUT3/RINPUT3. Inputs can be configured as
microphone or line level by enabling or disabling the microphone gain boost.
LINSEL and RINSEL control bits (see Table 3) are used to select independently between external
inputs and internally generated differential products (LINPUT1-RINPUT1 or LINPUT2-RINPUT2). The
choice of differential signal, LINPUT1-RINPUT1 or LINPUT2-RINPUT2 is made using DS (refer to
Table 5).
As an example, the WM8973 can be set up to convert one differential and one single ended mono
signal by applying the differential signal to LINPUT1/RINPUT1 and the single ended signal to
RINPUT2. By setting LINSEL to L-R Differential (see Table 3), DS to LINPUT1 - RINPUT1 (see Table
5) and RINSEL to RINPUT2, each mono signal can then be routed to a separate ADC or Bypass
path.
WM8973L Production Data
w PD, Rev 4.5, December 2011
20
The signal inputs are biased internally to the reference voltage VREF. Whenever the line inputs are
muted or the device placed into standby mode, the inputs are kept biased to VREF using special anti-
thump circuitry. This reduces any audible clicks that may otherwise be heard when changing inputs.
DC MEASUREMENT
For DC measurements (for example, battery voltage monitoring), the input signal at the LINPUT1
and/or RINPUT1 pins can be taken directly into the respective ADC, bypassing both PGA and
microphone boost. The ADC output then becomes unsigned relative to AVDD, instead of being a
signed (two’s complement) number relative to VREF. Setting L/RDCM will override L/RINSEL. The
input range for dc measurement is AGND to AVDD.
REGISTER
ADDRESS BIT LABEL DEFAULT DESCRIPTION
R32 (20h)
ADC Signal
Path Control
(Left)
7:6 LINSEL 00 Left Channel Input Select
00 = LINPUT1
01 = LINPUT2
10 = LINPUT3
11 = L-R Differential (either LINPUT1-
RINPUT1 or LINPUT2-RINPUT2,
selected by DS)
5:4 LMICBOOST 00 Left Channel Microphone Gain Boost
00 = Boost off (bypassed)
01 = 13dB boost
10 = 20dB boost
11 = 29dB boost
R33 (21h)
ADC Signal
Path Control
(Right)
7:6 RINSEL 00 Right Channel Input Select
00 = RINPUT1
01 = RINPUT2
10 = RINPUT3
11 = L-R Differential (either LINPUT1-
RINPUT1 or LINPUT2-RINPUT2,
selected by DS)
5:4 RMICBOOST 00 Right Channel Microphone Gain Boost
00 = Boost off (bypassed)
01 = 13dB boost
10 = 20dB boost
11 = 29dB boost
Table 3 Input Software Control
REGISTER
ADDRESS BIT LABEL DEFAULT DESCRIPTION
R31 (1Fh)
ADC input Mode 5 RDCM 0 Right Channel DC Measurement
0 = Normal Operation, PGA Enabled
1 = Measure DC level on RINPUT1
4 LDCM 0 Left Channel DC Measurement
0 = Normal Operation, PGA Enabled
1 = Measure DC level on LINPUT1
Table 4 DC Measurement Select
REGISTER
ADDRESS BIT LABEL DEFAULT DESCRIPTION
R31 (1Fh)
ADC Input Mode 8 DS 0 Differential input select
0: LINPUT1 - RINPUT1
1: LINPUT2 – RINPUT2
Table 5 Differential Input Select
Production Data WM8973L
w PD, Rev 4.5, December 2011
21
MONO MIXING
The stereo ADC can operate as a stereo or mono device, or the two channels can be mixed to mono,
either in the analogue domain (i.e. before the ADC) or in the digital domain (after the ADC).
MONOMIX selects the mode of operation. For analogue mono mix either the left or right channel A DC
can be used, allowing the unused ADC to be powered off or used for a dc measurement conversion.
The user also has the flexibility to select the data output from the audio interface using DATSEL. The
default is for left and right channel ADC data to be output, but the interface may also be configured so
that e.g. left channel ADC data is output as both left and right data for when an analogue mono mix is
selected.
Note:
If DC measurement is selected this overrides the MONOMIX selection.
REGISTER
ADDRESS BIT LABEL DEFAULT DESCRIPTION
R31 (1Fh)
ADC input
Mode
7:6 MO NOMIX
[1:0] 00 00: Stereo
01: Analogue Mono Mix (using left ADC)
10: Analogue Mono Mix (using right ADC)
11: Digital Mono Mix
Table 6 Mono Mixing
REGISTER
ADDRESS BIT LABEL DEFAULT DESCRIPTION
R23 (17h)
Additional
Control (1)
3:2 DATSEL
[1:0] 00 00: left data=left ADC; right data =right ADC
01: left data =left ADC; right data = left ADC
10: left data = right ADC; right data =right
ADC
11: left data = right ADC; right data = left
ADC
Table 7 ADC Data Output Configuration
The MICBIAS output provides a low noise reference voltage suitable for biasing electret type
microphones and the associated external resistor biasing network. Refer to the Applications
Information section for recommended external components. The output can be enabled or disables
using the MICB control bit (see also the “Power Management” section).
REGISTER
ADDRESS BIT LABEL DEFAULT DESCRIPTION
R25 (19h)
Power
Management (1)
1 MICB 0 Microphone Bias Enable
0 = OFF (high impedance output)
1 = ON
Table 8 Microphone Bias Control
The internal MICBIAS circuitry is shown below. Note that the maximum source current capability for
MICBIAS is 3mA. The external biasing resistors therefore must be large enough to li mit the MICBIAS
current to 3mA.
AGND
MICBIAS
= 1.8 x VMID
= 0.9 X AVDD
VMID
internal
resistor
internal
resistor
MICB
Figure 8 Microphone Bias Schematic
WM8973L Production Data
w PD, Rev 4.5, December 2011
22
PGA CONTROL
The PGA matches the input signal level to the ADC input range. The PGA gain is logarithmically
adjustable from +30dB to –17.25dB in 0.75dB steps. Each PGA can be controlled either by the user
or by the ALC function (see Automatic Level Control). When ALC is enabled for one or both channels,
then writing to the corresponding PGA control register has no effect.
The gain is independently adjustable on both Right and Left Line Inputs. Additionally, by controlling
the register bits LIVU and RIVU, the left and right gain settings can be simultaneously updated.
Setting the LZCEN and RZCEN bits enables a zero-cross detector which ensures that PGA gain
changes only occur when the signal is at zero, eliminating any zipper noise. If zero cross is enabled a
timeout is also available to update the gain if a zero cross does not occur. This function may be
enabled by setting TOEN in register R23 (17h).
The inputs can also be muted in the analogue domain under software control. The software control
registers are shown in Table 9. If zero crossing is enabled, it is necessary to enable zero cross
timeout to un-mute the input PGAs. This is because their outputs will not cross zero when muted.
Alternatively, zero cross can be disabled before sending the un-mute command.
REGISTER
ADDRESS BIT LABEL DEFAULT DESCRIPTION
R0 (00h)
Left Channel
PGA
8 LIVU 0 Left Volume Update
0 = Store LINVOL in intermediate
latch (no gain change)
1 = Update left and right channel
gains (left = LINVOL, right =
intermediate latch)
7 LINMUTE 1 Left Channel Input Analogue Mute
1 = Enable Mute
0 = Disable Mute
Note: LIVU must be set to un-mute.
6 LZCEN 0 Left Channel Zero Cross Detector
1 = Change gain on zero cross only
0 = Change gain immediately
5:0 LINVOL
[5:0] 010111
( 0dB ) Left Channel Input Volume Control
111111 = +30dB
111110 = +29.25dB
. . 0.75dB steps down to
000000 = -17.25dB
R1 (01h)
Right Channel
PGA
8 RIVU 0 Right Volume Update
0 = Store RINVOL in intermediate
latch (no gain change)
1 = Update left and right channel
gains (right = RINVOL, left =
intermediate latch)
7 RINMUTE 1 Right Channel Input Analogue Mute
1 = Enable Mute
0 = Disable Mute
Note: RIVU must be set to un-mute.
6 RZCEN 0 Right Channel Zero Cross Detector
1 = Change gain on zero cross only
0 = Change gain immediately
5:0 RINVOL
[5:0] 010111
( 0dB ) Right Channel Input Volume Control
111111 = +30dB
111110 = +29.25dB
. . 0.75dB steps down to
000000 = -17.25dB
R23 (17h)
Additional
Control (1)
0 TOEN 0 Timeout Enable
0 : Timeout Disabled
1 : Timeout Enabled
Table 9 Input PGA Software Control
Production Data WM8973L
w PD, Rev 4.5, December 2011
23
ANALOGUE TO DIGITAL CONVERTER (ADC)
The WM8973L uses a multi-bit, oversampled sigma-delta ADC for each channel. The use of multi-bit
feedback and high oversampling rates reduces the effects of jitter and high frequency noise. The ADC
Full Scale input level is proportional to AVDD. With a 3.3V supply voltage, the full scale level is 1.0
Volts r.m.s. Any voltage greater than full scale may overload the ADC and cause distortion.
ADC DIGITAL FILTER
The ADC filters perform true 24 bit signal processing to convert the raw multi-bit oversampled data
from the ADC to the c orrect sampling frequency to be output on the digital audio interface. The digital
filter path is illustrated in Figure 9.
FROM ADC DIGITAL
HPF
DIGITAL
FILTER
TO DIGITAL
A
UDIO
INTERFACE
DIGITAL
DECIMATOR
A
DCHPD
Figure 9 ADC Digital Filter
The ADC digital filters contain a digital high pass filter, selectable via software control. The high-pass
filter response is detailed in the Digital Filter Characteristics section. When the high-pass filter is
enabled the dc offset is continuously calculated and subtracted from the input signal. By setting
HPOR, the last calculated dc offset value is stored when the high-pass filter is disabled and will
continue to be subtracted from the input signal. If the DC offset is changed, the stored and subtracted
value will not change unless the high-pass filter is enabled. This feature can be used for calibration
purposes. In addition the highpass filter may be enabled separately on the left and right channels
(see Table 11).
The output data format can be programmed by the user to accommodate stereo or monophonic
recording on both inputs. The polarity of the output signal can also be changed under software
control. The software control is shown in Table 10.
WM8973L Production Data
w PD, Rev 4.5, December 2011
24
REGISTER
ADDRESS BIT LABEL DEFAULT DESCRIPTION
R5 (05h)
ADC and DAC
Control
6:5 ADCPOL
[1:0] 00 00 = Polarity not inverted
01 = L polarity invert
10 = R polarity invert
11 = L and R polarity invert
4 HPOR 0 Store dc offset when high-pass
filter disabled
1 = store offset
0 = clear offset
0 ADCHPD 0 ADC high-pass filter enable
(Digital)
HPFLREN = 0
1 = Disable high-pass filter on left
and right channels
0 = Enable high-pass filter on left
and right channels
HPFLREN = 1
0 = High-pass enabled on left,
disabled on right
1 = High-pass enabled on right,
disabled on left
R27 (1Bh) 5 HPFLREN 0 ADC high-pass filter left or right
enable
0 = High-pass filter enable/disable
on left and right channels
controlled by ADCHPD
1 = High-pass filter enabled on left
or right channel, as selected by
ADCHPD
Table 10 ADC Signal Path Control
HPFLREN ADCHPD HIGH PASS MODE
0 0
High-pass filter enabled on left and right
channels
0 1
High-pass filter disabled on left and right
channels
1 0
High-pass filter enabled on left channel,
disabled on right channel
1 1
High-pass filter disabled on left channel,
enabled on right channel
Table 11 ADC High Pass Filter Enable Modes
Production Data WM8973L
w PD, Rev 4.5, December 2011
25
DIGITAL ADC VOLUME CONTROL
The output of the ADCs c an be digitally amplified or attenuated over a range from –97dB to +30dB in
0.5dB steps. The volume of each channel can be controlled separately. The gain for a given eight-bit
code X is given by:
0.5 (X-195) dB for 1 X 255; MUTE for X = 0
The LAVU and RAVU control bits control the loading of digital volume control data. When LAVU or
RAVU are set to 0, the LADCVOL or RADCVOL control data will be loaded into the respective control
register, but will not actually change the digital gain setting. Both left and right gain settings are
updated when either LAVU or RAVU are set to 1. This makes it possible to update the gain of both
channels simultaneously.
REGISTER
ADDRESS BIT LABEL DEFAULT DESCRIPTION
R21 (15h)
Left ADC
Digital Volume
7:0 LADCVOL
[7:0] 11000011
( 0dB ) Left ADC Digital Volume Control
0000 0000 = Digital Mute
0000 0001 = -97dB
0000 0010 = -96.5dB
... 0.5dB steps up to
1111 1111 = +30dB
8 LAVU 0 Left ADC Volume Update
0 = Store LADCVOL in intermediate
latch (no gain change)
1 = Update left and right channel
gains (left = LADCVOL, right =
intermediate latch)
R22 (16h)
Right ADC
Digital Volume
7:0 RADCVOL
[7:0] 11000011
( 0dB ) Right ADC Digital Volume Control
0000 0000 = Digital Mute
0000 0001 = -97dB
0000 0010 = -96.5dB
... 0.5dB steps up to
1111 1111 = +30dB
8 RAVU 0 Right ADC Volume Update
0 = Store RADCVOL in intermediate
latch (no gain change)
1 = Update left and right channel
gains (left = intermediate latch, right
= RADCVOL)
Table 12 ADC Digital Volume Control
WM8973L Production Data
w PD, Rev 4.5, December 2011
26
AUTOMATIC LEVEL CONTROL (ALC)
The WM8973L has an automatic level control that aims to keep a constant recording volume
irrespective of the input signal level. This is achieved by continuously adjusting the PGA gain so that
the signal level at the ADC input remains constant. A digital peak detector monitors the ADC output
and changes the PGA gain if necessary. Note that when the ALC function is enabled, the settings of
registers 0 and 1 (LINVOL, LIVU, LIZC, LINMUTE, RINVOL, RIVU, RIZC and RINMUTE) are ignored.
hold
time decay
time attack
time
input
signal
signal
after
ALC
PGA
gain
ALC
target
level
Figure 10 ALC Operation
The ALC function is enabled using the ALCSEL control bits. When enabled, the recording volume can
be programmed between –6dB and –28.5dB (relative to ADC full scale) using the ALCL register bits.
An upper limit for the PGA gain can be imposed by setting the MAXGAIN control bits.
HLD, DCY and ATK control the hold, decay and attack times, respectively:
Hold time is the time delay between the peak level detected being below target and the PGA gain
beginning to ramp up. It can be programmed in power-of-two (2n) steps, e.g. 2.67ms, 5.33ms,
10.67ms etc. up to 43.7s. Alternatively, the hold time can also be set to zero. The hold time only
applies to gain ramp-up, there is no delay before ramping the gain down when the signal level is
above target.
Decay (Gain Ramp-Up) Time is the time that it takes for the PGA gain to ramp up across 90% of its
range (e.g. from –15B up to 27.75dB). The time it takes for the recording level to return to its target
value therefore depends on both the decay time and on the gain adjustment required. If the gain
adjustment is small, it will be shorter than the decay time. The decay time can be programmed in
power-of-two (2n) steps, from 24ms, 48ms, 96ms, etc. to 24.58s.
Attack (Gain Ramp-Down) Time is the time that it takes for the PGA gain to ramp down across 90%
of its range (e.g. from 27.75dB down to -15B gain). The time it takes for the recording level to return to
its target value therefore depends on both the attack time and on the gain adjustment required. If the
gain adjustment is small, it will be shorter than the attack time. The attack time can be programmed in
power-of-two (2n) steps, from 6ms, 12ms, 24ms, etc. to 6.14s.
When operating in stereo, the peak detector takes the maximum of left and right channel peak values,
and any new gain setting is applied to both left and right PGAs, so that the stereo image is preserved.
However, the ALC function can also be enabled on one channel only. In this case, only one PGA is
controlled by the ALC mechanism, while the other channel runs independently with its PGA gain set
through the control register.
When one ADC channel is unused or used for DC measurement, the peak detector disregards that
channel. The ALC function can also operate when the two ADC outputs are mixed to mono in the
digital domain, but not if they are mixed to mono in the analogue domain, before entering the ADCs.
Production Data WM8973L
w PD, Rev 4.5, December 2011
27
REGISTER
ADDRESS BIT LABEL DEFAULT DESCRIPTION
R17 (11h)
ALC Control 1 8:7 ALCSEL
[1:0] 00
(OFF) ALC function select
00 = ALC off (PGA gain set by register)
01 = Right channel only
10 = Left channel only
11 = Stereo (PGA registers unused)
Note: ensure that LINVOL and
RINVOL settings (reg. 0 and 1) are
the same before entering this mode.
6:4 MAXGAIN
[2:0] 111
(+30dB) Set Maximum Gain of PGA
111 : +30dB
110 : +24dB
….(-6dB steps)
001 : -6dB
000 : -12dB
3:0 ALCL
[3:0] 1011
(-12dB) ALC target – sets signal level at ADC
input
0000 = -28.5dB FS
0001 = -27.0dB FS
… (1.5dB steps)
1110 = -7.5dB FS
1111 = -6dB FS
R18 (12h)
ALC Control 2 7 ALCZC 0 (zero
cross
off)
ALC uses zero cross detection circuit.
3:0 HLD
[3:0] 0000
(0ms) ALC hold time before gain is increased.
0000 = 0ms
0001 = 2.67ms
0010 = 5.33ms
… (time doubles with every step)
1111 = 43.691s
R19 (13h)
ALC Control 3 7:4 DCY
[3:0] 0011
(192ms) ALC decay (gain ramp-up) time
0000 = 24ms
0001 = 48ms
0010 = 96ms
… (time doubles with every step)
1010 or higher = 24.58s
3:0 ATK
[3:0] 0010
(24ms) ALC attack (gain ramp-down) time
0000 = 6ms
0001 = 12ms
0010 = 24ms
… (time doubles with every step)
1010 or higher = 6.14s
Table 13 ALC Control
PEAK LIMITER
To prevent clipping when a large signal occurs just after a period of quiet, the ALC circuit includes a
limiter function. If the ADC input signal exceeds 87.5% of full scale (–1.16dB), the PGA gain is
ramped down at the maximum attack rate (as when ATK = 0000), until the signal level falls below
87.5% of full scale. This function is automatically enabled whenever the ALC is enabled.
Note:
If ATK = 0000, then the limiter makes no difference to the operation of the ALC. It is designed to
prevent clipping when long attack times are used.
WM8973L Production Data
w PD, Rev 4.5, December 2011
28
NOISE GATE
When the signal is very quiet and consists mainly of noise, the ALC function may cause “noise
pumping”, i.e. loud hissing nois e during silence periods. The WM8973L has a noise gate function that
prevents noise pumping by comparing the signal level at the LINPUT1/2/3 and/or RINPUT1/2/3 pins
against a noise gate threshold, NGTH. The noise gate cuts in when:
Signal level at ADC [dB] < NGTH [dB] + PGA gain [dB] + Mic Boost gain [dB]
This is equivalent to:
Signal level at input pin [dB] < NGTH [dB]
The ADC output can then either be muted or alternatively, the PGA gain can be held constant
(preventing it from ramping up as it normally would when the signal is quiet).
The table below summarises the noise gate control register. The NGTH control bits set the noise gate
threshold with respect to the ADC full-scale range. The threshold is adjusted in 1.5dB steps. Levels
at the extremes of the range may cause inappropriate operation, so care should be taken with set–up
of the function. Note that the noise gate only works in conjunction with the ALC function, and always
operates on the same channel(s) as the ALC (left, right, both, or none).
REGISTER
ADDRESS BIT LABEL DEFAULT DESCRIPTION
R20 (14h)
Noise Gate
Control
7:3 NGTH
[4:0] 00000 Noise gate threshold
00000 -76.5dBfs
00001 -75dBfs
… 1.5 dB steps
11110 -31.5dBfs
11111 -30dBfs
2:1 NGG
[1:0]
00 Noise gate type
X0 = PGA gain held constant
01 = mute ADC output
11 = reserved (do not use this setting)
0 NGAT 0 Noise gate function enable
1 = enable
0 = disable
Table 14 Noise Gate Control
Note:
The performance of the ADC may degrade at high input signal levels if the monitor bypass mux is
selected with MIC boost and ALC enabled.
Production Data WM8973L
w PD, Rev 4.5, December 2011
29
3D STEREO ENHANCEMENT
The WM8973L has a digital 3D enhancement option to artificially increase the separation between the
left and right channels. This effect can be used for recording or playback, but not for both
simultaneously. Selection of 3D for record or playback is controlled by register bit MODE3D.
Important:
Switching the 3D filter from record to playback or from playback to record may only be done
when ADC and DAC are disabled. The WM8973L control interface will only allow MODE3D to
be changed when ADC and DAC are disabled (i.e. bits AD CL, ADCR, DACL and DACR in reg. 26
/ 1Ah are all zero).
The 3D enhancement function is activated by the 3DEN bit, and has two programmable parameters.
The 3DDEPTH setting controls the degree of stereo expansion. Additionally, one of four filter
characteristics can be selected for the 3D processing, using the 3DVC and 3DLC control bits.
REGISTER
ADDRESS BIT LABEL DEFAULT DESCRIPTION
R16 (10h)
3D enhance 7 MODE3D 0 Playback/Record 3D select
0 = 3D selected for Record
1 = 3D selected for Playback
6 3DUC 0 Upper Cut-off frequency
0 = High (2.2kHz at 48kHz sampling)
1 = Low (1.5kHz at 48kHz sampling)
5 3DLC 0 Lower Cut-off frequency
0 = Low (200Hz at 48kHz sampling)
1 = High (500Hz at 48kHz sampling)
4:1 3DDEPTH
[3:0] 0000 Stereo depth
0000: 0% (minimum 3D effect)
0001: 6.67%
....
1110: 93.3%
1111: 100% (maximum 3D effect)
0 3DEN 0 3D function enable
1: enabled
0: disabled
Table 15 3D Stereo Enhancement Function
When 3D enhancement is enabled (and/or the graphic equaliser for playback) it may be necessary to
attenuate the signal by 6dB to avoid limiting. This is a user selectable function, enabled by setting
ADCDIV2 for the record path and DACDIV2 for the playback path.
REGISTER
ADDRESS BIT LABEL DEFAULT DESCRIPTION
R5 (05h)
ADC and DAC
control
8 ADCDIV2 0 ADC 6dB attenuate enable
0 = disabled (0dB)
1 = -6dB enabled
7 DACDIV2 0 DAC 6dB attenuate enable
0 = disabled (0dB)
1 = -6dB enabled
Table 16 ADC and DAC 6dB Attenuation Select
WM8973L Production Data
w PD, Rev 4.5, December 2011
30
OUTPUT SIGNAL PATH
The WM8973L output signal paths consist of digital filters, DACs, analogue mixers and output drivers.
The digital filters and DACs are enabled when the WM8973L is in ‘playback only’ or ‘record and
playback’ mode. The mixers and output drivers can be separately enabled by individual control bits
(see Analogue Outputs). Thus it i s possible to utilise the analogue mixing and amplification provided
by the WM8973L, irrespective of whether the DACs are running or not.
The WM8973L receives digital input data on the DACDAT pin. The digital filter block processes the
data to provide the following functions:
Digital volume control
Graphic equaliser and Dynamic Bass Boost
Sigma-Delta Modulation
Two high performance sigma-delta audio DACs convert the digital data into two analogue signals (left
and right). These can then be mixed with analogue signals from the LINPUT1/2/3 and RINPUT1/2/3
pins, and the mix is fed to the output drivers, LOUT1/ROUT1, LOUT2/ROUT2, OUT3 and
MONOOUT.
LOUT1/ROUT1/OUT3: can drive a 16 or 32 stereo headphone or stereo line output.
LOUT2/ROUT2: can drive a 16 or 32 stereo headphone or stereo line output, or an
8 mono speaker.
MONOOUT: can drive a mono line output or other load down to 10k
DIGITAL DAC VOLUME CONTROL
The signal volume from each DAC can be controlled digitally, in the same way as the ADC volume
(see Digital ADC Volume Control). The gain and attenuation range is –127dB to 0dB in 0.5dB steps.
The level of attenuation for an eight-bit code X is given by:
0.5 (X-255) dB for 1 X 255; MUTE for X = 0
The LDVU and RDVU control bits control the loading of digital volume control data. When LDVU or
RDVU are set to 0, the LDACVOL or RDACVOL control data is loaded i nto an intermediate register,
but the actual gain does not change. Both left and right gain settings are updated simultaneously
when either LDVU or RDVU are set to 1.
REGISTER
ADDRESS BIT LABEL DEFAULT DESCRIPTION
R10 (0Ah)
Left Channel
Digital Volume
8 LDVU 0 Left DAC Volume Update
0 = Store LDACVOL in intermediate
latch (no gain change)
1 = Update left and right channel
gains (left = LDACVOL, right =
intermediate latch)
7:0 LDACVOL
[7:0] 11111111
( 0dB ) Left DAC Digital Volume Control
0000 0000 = Digital Mute
0000 0001 = -127dB
0000 0010 = -126.5dB
... 0.5dB steps up to
1111 1111 = 0dB
R11 (0Bh)
Right Channel
Digital Volume
8 RDVU 0 Right DAC Volume Update
0 = Store RDACVOL in intermediate
latch (no gain change)
1 = Update left and right channel
gains (left = intermediate latch, right
= RDACVOL)
7:0 RDACVOL
[7:0] 11111111
( 0dB ) Right DAC Di gital Volume Control
similar to LDACVOL
Table 17 Digital Volume Control
Production Data WM8973L
w PD, Rev 4.5, December 2011
31
GRAPHIC EQUAL ISER
The WM8973L has a digital graphic equaliser and adaptive bass boost function. This function
operates on digital audio data before it is passed to the audio DACs. Bass enhancement can take two
different forms:
Linear bass control: bass signals are amplified or attenuated by a user programmable
gain. This is independent of signal volume, and very high bass gains on loud signals may
lead to signal clipping.
Adaptive bass boost: The bass volume is amplified by a variable gain. When the bass
volume is low, it is boosted more than when the bass volume is high. This method is
recommended because it prevents clipping, and usually sounds more pleasant to the
human ear.
Treble control applies a user programmable gain, without any adaptive boost function. Bass and
treble control are completely independent with separately programmable gains and filter
characteristics.
REGISTER
ADDRESS BIT LABEL DEFAULT DESCRIPTION
R12 (0Ch)
Bass Control 7 BB 0 Bass Boost
0 = Linear bass control
1 = Adaptive bass boost
6 BC 0 Bass Filter Characteristic
0 = Low Cutoff (130Hz at 48kHz sampling)
1 = High Cutoff (200Hz at 48kHz sampling)
3:0 BASS
[3:0] 1111
(Disabled) Bass Intensity
Code BB=0 BB=1
0000 +9dB 15 (max)
0001 +9dB 14
0010 +7.5dB 13
0011 +6dB 12
0100 +4.5dB 11
0101 +3dB 10
0110 +1.5dB 9
0111 0dB 8
1000 -1.5dB 7
1001 -3dB 6
1010 -4.5dB 5
1011 -6dB 4
1100 -6dB 3
1101 -6dB 2
1110 -6dB 1
1111 Bypass (OFF)
R13 (0Dh)
Treble Control 6 TC 0 Treble Filter Characteristic
0 = High Cutoff (8kHz at 48kHz sampling)
1 = Low Cutoff (4kHz at 48kHz sampling)
3:0 TRBL
[3:0] 1111
(Disabled) Treble Intensity
0000 or 0001 = +9dB
0010 = +7.5dB
… (1.5dB steps)
1011 to 1110 = -6dB
1111 = Disable
Table 18 Graphic Equaliser
WM8973L Production Data
w PD, Rev 4.5, December 2011
32
DIGITAL TO ANALOGUE CONVERTER (DAC)
After passing through the graphic equaliser filters, digital ‘de-emphasis’ can be applied to the audio
data if necessary (e.g. when the data comes from a CD with pre-emphasis used in the recording). De-
emphasis filtering is available for sample rates of 48kHz, 44.1kHz and 32kHz.
The WM8973L also has a Soft Mute function, which gradually attenuates the volume of the digital
signal to zero. When removed, the gain will return to the original setting. This function is enabled by
default. To play back an audio signal, it must first be disabled by setting the DACMU bit to zero.
REGISTER
ADDRESS BIT LABEL DEFAULT DESCRIPTION
R5 (05h)
ADC and DAC
Control
2:1 DEEMP
[1:0] 00 De-emphasis Control
11 = 48kHz sample rate
10 = 44.1kHz sample rate
01 = 32kHz sample rate
00 = No De-emphasis
3 DACMU 1 Digital Soft Mute
1 = mute
0 = no mute (signal active)
Table 19 DAC Control
The digital audio data is converted to oversampled bit streams in the on-chip, true 24-bit digital
interpolation filters. The bitstream data enters two multi-bit, sigma-delta DACs, which convert them to
high quality analogue audio signals. The multi-bit DAC architecture reduces high frequency noise and
sensitivity to clock jitter. It also uses a Dynamic Element Matching technique for high linearity and low
distortion.
In normal operation, the left and right channel digital audio data is converted to analogue in two
separate DACs. However, it is also possible to disable one channel, so that the same signal (left or
right) appears on both analogue output channels. Additionally, there is a mono-mix mode where the
two audio channels are mixed together digitally and then converted to analogue using only one DAC,
while the other DAC is switched off. The mono-mix signal can be selected to appear on both
analogue output channels.
The DAC output defaults to non-inverted. Setting DACINV will invert the DAC output phase on both
left and right channels.
REGISTER
ADDRESS BIT LABEL DEFAULT DESCRIPTION
R23 (17h)
Additional
Control (1)
5:4 DMONOMIX
[1:0] 00 DAC mono mix
00: stereo
01: mono ((L+R)/2) into DACL, ‘0’ into
DACR
10: mono ((L+R)/2) into DACR, ‘0’ into
DACL
11: mono ((L+R)/2) into DACL and
DACR
1 DACINV 0 DAC phase invert
0 : non-inverted
1 : inverted
Table 20 DAC Mono Mix and Phase Invert Select
Production Data WM8973L
w PD, Rev 4.5, December 2011
33
OUTPUT MIXERS
The WM8973L provides the option to mix the DAC output signal with analogue line-in signals from the
LINPUT1/2/3, RINPUT1/2/3 pins or a mono differential input (LINPUT1 – RINPUT1) or (LINPUT2 –
RINPUT2), selected by DS (see Table 5) . The level of the mixed-in signals can be controlled with
PGAs (Programmable Gain Amplifiers).
The mono mixer is designed to allow a number of signal combinations to be mixed, including the
possibility of mixing both the right and left channels together to produce a mono output. To prevent
overloading of the mixer when full-scale DAC left and right signals are input, the mixer inputs from the
DAC outputs each have a fixed gai n of -6dB . The bypass path inputs to the mono mixer have variable
gain as determined by R38/R39 bits [6:4].
REGISTER
ADDRESS BIT LABEL DEFAULT DESCRIPTION
R34 (22h)
Left Mixer (1)
2:0 LMIXSEL 000 Left Input Selection for Output Mix
000 = LINPUT1
001 = LINPUT2
010 = LINPUT3
011 = Left ADC Input (after PGA /
MICBOOST)
100 = Differential input
R36 (24h)
Right Mixer
(1)
2:0 RMIXSEL 000 Right Input Selection for Output Mix
000 = RINPUT1
001 = RINPUT2
010 = RINPUT3
011 = Right ADC Input (after PGA /
MICBOOST)
100 = Differential input
Table 21 Output Mixer Signal Selection
REGISTER
ADDRESS BIT LABEL DEFAULT DESCRIPTION
R34 (22h)
Left Mixer
Control (1)
8 LD2LO 0 Left DAC to Left Mixer
0 = Disable (Mute)
1 = Enable Path
7 LI2LO 0 LMIXSEL Signal to Left Mixer
0 = Disable (Mute)
1 = Enable Path
6:4 LI2LOVOL
[2:0] 101
(-9dB) LMIXSEL Signal to Left Mixer Volume
000 = +6dB
… (3dB steps)
111 = -15dB
R35 (23h)
Left Mixer
Control (2)
8 RD2LO 0 Right DAC to Left Mixer
0 = Disable (Mute)
1 = Enable Path
7 RI2LO 0 RMIXSEL Signal to Left Mixer
0 = Disable (Mute)
1 = Enable Path
6:4 RI2LOVOL
[2:0] 101
(-9dB) RMIXSEL Signal to Left Mixer Volume
000 = +6dB
… (3dB steps)
111 = -15dB
Table 22 Left Output Mixer Control
WM8973L Production Data
w PD, Rev 4.5, December 2011
34
REGISTER
ADDRESS BIT LABEL DEFAULT DESCRIPTION
R36 (24h)
Right Mixer
Control (1)
8 LD2RO 0 Left DAC to Right Mixer
0 = Disable (Mute)
1 = Enable Path
7 LI2RO 0 LMIXSEL Signal to Right Mixer
0 = Disable (Mute)
1 = Enable Path
6:4 LI2ROVOL
[2:0] 101
(-9dB) LMIXSEL Signal to Right Mixer Volume
000 = +6dB
… (3dB steps)
111 = -15dB
R37 (25h)
Right Mixer
Control (2)
8 RD2RO 0 Right DAC to Right Mixer
0 = Disable (Mute)
1 = Enable Path
7 RI2RO 0 RMIXSEL Signal to Right Mixer
0 = Disable (Mute)
1 = Enable Path
6:4 RI2ROVOL
[2:0] 101
(-9dB) RMIXSEL Signal to Right Mixer Volume
000 = +6dB
… (3dB steps)
111 = -15dB
Table 23 Right Output Mixer Control
REGISTER
ADDRESS BIT LABEL DEFAULT DESCRIPTION
R38 (26h)
Mono Mixer
Control (1)
8 LD2MO 0 Left DAC to Mono Mixer
0 = Disable (Mute)
1 = Enable Path
7 LI2MO 0 LMIXSEL Signal to Mono Mixer
0 = Disable (Mute)
1 = Enable Path
6:4 LI2MOVOL
[2:0] 101
(-9dB) LMIXSEL Signal to Mono Mixer
Volume
000 = +6dB
… (3dB steps)
111 = -15dB
R39 (27h)
Mono Mixer
Control (2)
8 RD2MO 0 Right DAC to Mono Mixer
0 = Disable (Mute)
1 = Enable Path
7 RI2MO 0 RMIXSEL Signal to Mono Mixer
0 = Disable (Mute)
1 = Enable Path
6:4 RI2MOVOL
[2:0] 101
(-9dB) RMIXSEL Signal to Mono Mixer
Volume
000 = +6dB
… (3dB steps)
111 = -15dB
Table 24 Mono Output Mixer Control
Production Data WM8973L
w PD, Rev 4.5, December 2011
35
ANALOGUE OUTPUTS
LOUT1/ROUT1 OUTPUTS
The LOUT1 and ROUT1 pins can drive a 16 or 32 headphone or a line output (see Headphone
Output and Line Output sections, respectively). The signal volume on LOUT1 and ROUT1 can be
independently adjusted under software control by writing to LOUT1VOL and ROUT1VOL,
respectively. Note that gains over 0dB may cause clipping if the signal is large. Any gain setting below
0101111 (minimum) mutes the output driver. The corresponding output pin remains at the same DC
level (the reference voltage on the VREF pin), so that no click noise is produced when muting or un-
muting.
A zero cross detect on the analogue output may also be enabled when changing the gain setting to
minimize audible clicks and zipper noise as the gain updates. If zero cross is enabled a timeout is
also available to update the gain if a zero cross does not occur. This function may be enabled by
setting TOEN in register R23 (17h).
REGISTER
ADDRESS BIT LABEL DEFAULT DESCRIPTION
R2 (02h)
LOUT1
Volume
8 LO1VU 0 Left Volume Update
0 = Store LOUT1VOL in intermediate
latch (no gain change)
1 = Update left and right channel gains
(left = LOUT1VOL, right = intermediate
latch)
7 LO1ZC 0 Left zero cross enable
1 = Change gain on zero cross only
0 = Change gain immediately
6:0 LOUT1VOL
[6:0] 1111001
(0dB)
LOUT1 Volume
1111111 = +6dB
… (80 steps)
0110000 = -67dB
0101111 to 0000000 = Analogue
MUTE
R3 (03h)
ROUT1
Volume
8 RO1VU 0 Right Volume Update
0 = Store ROUT1VOL in intermediate
latch (no gain change)
1 = Update left and right channel gains
(left = intermediate latch, right =
ROUT1VOL)
7 RO1ZC 0 Right zero cross enable
1 = Change gain on zero cross only
0 = Change gain immediately
6:0 ROUT1VOL
[6:0] 1111001 ROUT1 Volume
Similar to LOUT1VOL
Table 25 LOUT1/ROUT1 Volume Control
WM8973L Production Data
w PD, Rev 4.5, December 2011
36
LOUT2/ROUT2 OUTPUTS
The LOUT2 and ROUT2 output pins are essentially similar to LOUT1 and ROUT1, but they are
independently controlled and can also drive an 8 mono speaker (see Speak er Output section). For
speaker drive, the ROUT2 signal must be inverted (ROUT2INV = 1), so that the left and right channel
are mixed to mono in the speaker [L–(-R) = L+R].
REGISTER
ADDRESS BIT LABEL DEFAULT DESCRIPTION
R40 (28h)
LOUT2
Volume
6:0 LOUT2VOL
[6:0] 1111001
(0dB) Similar to LOUT1VOL
7 LO2ZC 0 Left zero cross enable
1 = Change gain on zero cross only
0 = Change gain immediately
8 LO2VU 0 Same as LO1VU
R41 (29h)
ROUT2
Volume
6:0 ROUT2VOL
[6:0] 1111001
(0dB) Similar ROUT1VOL
7 RO2ZC 0 Right zero cross enable
1 = Change gain on zero cross only
0 = Change gain immediately
8 RO2VU 0 Same as RO1VU
R24 (18h)
Additional
Control (2)
4 ROUT2INV
0 ROUT2 Invert
0 = No Inversion (0 phase shift)
1 = Signal inverted (180 phase shift)
Table 26 LOUT2/ROUT2 Volume Control
MONO OUTPUT
The MONOOUT pin can drive a mono line output. The signal volume on MONOOUT can be adjusted
under software control by writing to MONOOUTVOL.
REGISTER
ADDRESS BIT LABEL DEFAULT DESCRIPTION
R42 (2Ah)
MONOOUT
Volume
6:0 MONOOUT
VOL [6:0] 1111001
(0dB)
MONOOUT Volume
1111111 = +6dB
… (80 steps)
0110000 = -67dB
0101111 to 0000000 = Analogue MUTE
7 MOZC 0 MONOOUT zero cross enable
1 = Change gain on zero cross only
0 = Change gain immediately
Table 27 MONOOUT Volume Control
OUT3 OUTPUT
The OUT3 pin can drive a 16 or 32 headphone or a line output or be used as a DC reference for a
headphone output (see Headphone Output section). It can be selected to either drive out an inverted
ROUT1 or inverted MONOOUT for e.g. an earpiece drive between OUT3 and LOUT1 or differential
output between OUT3 and MONOOUT. OUT3 can also drive an un-inverted ROUT1 signal, which
originates at the right mixer output before the output PGA.
OUT3SW selects the mode of operation required.
REGISTER
ADDRESS BIT LABEL DEFAULT DESCRIPTION
R24 (18h)
Additional
Control (2)
8:7 OUT3SW
[1:0] 00
OUT3 select
00 : VREF
01 : ROUT1 signal (volume controlled by
ROUT1VOL)
10 : MONOOUT
11 : right mixer output (no volume
control through ROUT1VOL)
Table 28 OUT3 Select
Production Data WM8973L
w PD, Rev 4.5, December 2011
37
ENABLING THE OUTPUTS
Each analogue output of the WM8973L can be separately enabled or disabled. The analogue mixer
associated with each output is powered on or off along with the output pin. All outputs are disabled by
default. To save power, unused outputs should remain disabled.
Outputs can be enabled at any time, except when VREF is disabled (VR=0), as this may cause pop
noise (see “Power Management” and “Applications Information” sections)
REGISTER
ADDRESS BIT LABEL DEFAULT DESCRIPTION
R26 (1Ah)
Power
Management
(2)
6 LOUT1 0 LOUT1 Enable
5 ROUT1 0 ROUT1 Enable
4 LOUT2 0 LOUT2 Enable
3 ROUT2 0 ROUT2 Enable
2 MONO 0 MONOOUT Enable
1 OUT3 0 OUT3 Enable
Note: All “Enable” bits are 1 = ON, 0 = OFF
Table 29 Analogue Output Control
Whenever an analogue output is disabled, it remains connected to VREF (pin 20) through a resistor.
This helps to prevent pop noise when the output is re-enabled. The resistance between VREF and
each output can be controlled using the VROI bit in register 27. The default is low (1.5k), so that any
capacitors on the outputs can charge up quickly at start-up. If a high impedance is desired for
disabled outputs, VROI can then be set to 1, increasing the resistance to about 40k.
REGISTER
ADDRESS BIT LABEL DEFAULT DESCRIPTION
R27 (1Bh)
Additional (1) 6 VROI 0 VREF to analogue output resistance
0: 1.5 k
1: 40 k
Table 30 Disabled Outputs to VREF Resistance
HEADPHONE SWITCH
The RINPUT3/HPDETECT pin can be used as a headphone switch control input to automatically
disable the speaker output and enable the headphone output e.g. when a headphone is plugged into
a jack socket. In this mode, enabled by setting HPSWEN, HPDETE CT switches between headphone
and speaker outputs (e.g. when the pin is connected to a mechanical switch in the headphone socket
to detect plug-in). The HPSWPOL bit reverses the pin’s polarity. Note that the LOUT1, ROUT1,
LOUT2 and ROUT2 bits in register 26 must also be set for headphone and speaker output (see Table
31 and Table 32).
Note:
When RINPUT3/HPDETECT is used as the HPDETECT input, the thresholds become CMOS levels
(0.3 AVDD / 0.7 AVDD).
HPSWEN HPSWPOL HPDETECT
(PIN23) L/ROUT1
(reg. 26) L/ROUT2
(reg. 26) Headphone
enabled Speaker
enabled
0 X X 0 0 no no
0 X X 0 1 no yes
0 X X 1 0 yes no
0 X X 1 1 yes yes
1 0 0 X 0 no no
1 0 0 X 1 no yes
1 0 1 0 X no no
1 0 1 1 X yes no
1 1 0 0 X no no
1 1 0 1 X yes no
1 1 1 X 0 no no
1 1 1 X 1 no yes
Table 31 Headphone Switch Operation
WM8973L Production Data
w PD, Rev 4.5, December 2011
38
REGISTER
ADDRESS BIT LABEL DEFAULT DESCRIPTION
R24 (18h)
Additional
Control (2)
6 HPSWEN 0
Headphone Switch Enable
0 : Headphone switch disabled
1 : Headphone switch enabled
5 HPSWPOL 0 Headphone Switch Polarity
0 : HPDETECT high = headphone
1 : HPDETECT high = speaker
Table 32 Headphone Switch
Figure 11 Example Headset Detection Circuit Using Normally-Open Switch
Figure 12 Example Headset Detection Circuit Using Normally-Closed Switch
Production Data WM8973L
w PD, Rev 4.5, December 2011
39
THERMAL SHUTDOWN
The speaker and headphone outputs can drive very large currents. To protect the WM8973L from
overheating a thermal shutdown circuit is included. If the device temperature reaches approximately
1500C and the thermal shutdown circuit is enabled (TSDEN = 1 ) then the speaker and headphone
amplifiers (outputs OUT1L/R, OUT2L/R and OUT3) will be disabled.
REGISTER
ADDRESS BIT LABEL DEFAULT DESCRIPTION
R23 (17h)
Additional
Control (1)
8 TSDEN 0
Thermal Shutdown Enable
0 : thermal shutdown disabled
1 : thermal shutdown enabled
Table 33 Thermal Shutdown
HEADPHONE OUTPUT
Analogue outputs LOUT1/ROUT1, LOUT2/ROUT2, and OUT3, can drive a 16 or 32 headphone
load, either through DC blocking capacitors, or DC coupled without any capacitor.
Headphone Output using DC blocking
capacitors DC Coupled Headphone Output
(OUT3SW = 00)
Figure 13 Recommended Headphone Output Configurations
When DC blocking capacitors are used, then their capacitance and the load resistance together
determine the lower cut-off frequency, fc. Increasing the capacitance lowers fc, improving the bass
response. Smaller capacitance values will diminish the bass response. Assuming a 16 Ohm load and
C1, C2 = 220F:
fc = 1 / 2 RLC1 = 1 / (2 x 16 x 220F) = 45 Hz
In the DC coupled configuration, the headphone “ground” is connected to the OUT3 pin, which must
be enabled by setting OUT3 = 1 and OUT3SW = 00. As the OUT3 pin produces a DC voltage of
AVDD/2 (=VREF), there is no DC offset between LOUT1/ROUT1 and OUT3, and therefore no DC
blocking capacitors are required. This saves space and material cost in portable applications.
It is recommended to connect the DC coupl ed headphone outputs only to headphones, and not to the
line input of another device. Although the built-in short circuit protection will prevent any damage to
the headphone outputs, such a connection may be noisy, and may not function properly if the other
device is grounded.
SPEAKER OUTPUT
LOUT2 and ROUT2 can differentially drive a mono 8 speaker as shown below.
Figure 14 Speaker Output Connection
The right channel is inverted by setting the ROUT2INV bit, so that the signal across the loudspeaker
is the sum of left and right channels.
WM8973L Production Data
w PD, Rev 4.5, December 2011
40
LINE OUTPUT
The analogue outputs, LOUT1/ROUT1 and LOUT2/ROUT2, can be used as line outputs. Additionally,
OUT3 and MONOOUT can be used as a stereo line-out by setting OUT3SW=11 (reg. 24) and
ensuring the contents of regis ters 38 and 39 (mono-out mix) are the same as reg. 34 and 35 (left out
mix). Recommended external components are shown below.
Figure 15 Recommended Circuit for Line Output
The DC blocking capacitors and the load resistance together determine the lower cut-off frequency, fc.
Assuming a 10 kOhm load and C1, C2 = 1F:
fc = 1 / 2 (RL+R1) C1 = 1 / (2 x 10.1k x 1F) = 16 Hz
Increasing the capacitance lowers fc, improving the bass response. Smaller values of C1 and C2 will
diminish the bass response. The function of R1 and R2 is to protect the line outputs from damage
when used improperly.
DIGITAL AUDIO INTERFACE
The digital audio interface is used for inputting DAC data into the WM8973L and outputting ADC data
from it. It uses five pins:
ADCDAT: ADC data output
ADCLRC: ADC data alignment clock
DACDAT: DAC data input
DACLRC: DAC data alignment clock
BCLK: Bit clock, for synchronisation
The clock signals BCLK, ADCLRC and DACLRC can be outputs when the WM8973L operates as a
master, or inputs when it is a slave (see Master and Slave Mode Operation, below).
Four different audio data formats are supported:
Left justified
Right justified
I
2S
DSP mode
All four of these modes are MSB first. They are described in Audio Data Formats, below. Refer to the
Electrical Characteristic section for timing information.
MASTER AND SLAVE MODE OPERATION
The WM8973L can be configured as either a master or slave mode device. As a master device the
WM8973L generates BCLK, ADCLRC and DACLRC and thus controls sequencing of the data
transfer on ADCDAT and DACDAT. In slave mode, the WM8973L responds with data to clocks it
receives over the digital audio interface. The mode can be selected by writing to the MS bit (see
Table 23). Master and slave modes are illustrated below.
Figure 16 Master Mode Figure 17 Slave Mode
Production Data WM8973L
w PD, Rev 4.5, December 2011
41
AUDIO DATA FORMATS
In Left Justified mode, the MSB is available on the first rising edge of BCLK following a LRCLK
transition. The other bits up to the LSB are then transmitted in order. Depending on word length,
BCLK frequency and sample rate, there may be unused BCLK cycles before each LRCLK transition.
Figure 18 Left Justified Audio Interface (assuming n-bit word length)
In Right Justified mode, the LSB is available on the last rising edge of BCLK before a LRCLK
transition. All other bits are transmitted before (MSB first). Depending on word length, BCLK
frequency and sample rate, there may be unused BCLK cycles after each LRCLK transition.
Figure 19 Right Justified Audio Interface (assuming n-bit word length)
In I2S mode, the MSB is available on the second rising edge of BCLK following a LRCLK transition.
The other bits up to the LSB are then transmitted in order. Depending on word length, BCLK
frequency and sample rate, there may be unused BCLK cycles between the LSB of one sample and
the MSB of the next.
Figure 20 I2S Justified Audio Interface (assuming n-bit word length)
WM8973L Production Data
w PD, Rev 4.5, December 2011
42
In DSP/PCM mode, the left channel MSB is available on either the 1st (mode B) or 2nd (mode A) rising
edge of BCLK (selectable by LRP) following a rising edge of LRC. Right channel data immediately
follows left channel data. Depending on word length, BCLK frequency and sample rate, there may be
unused BCLK cycles between the LSB of the right channel data and the next sample.
In device master mode, the LRC output will resemble the frame pulse shown in Figure 21 and Figure
22. In device sl ave mode, Figure 23 and Figure 24, it is possible to use any length of frame pulse less
than 1/fs, providing the falling edge of the frame pulse occurs greater than one BCLK period before
the rising edge of the next frame pulse.
Figure 21 DSP/PCM Mode Audio Interface (mode A, LRP=0, Master)
Figure 22 DSP/PCM Mode Audio Interface (mode B, LRP=1, Master)
Figure 23 DSP/PCM Mode Audio Interface (mode A, LRP=0, Slave)
Production Data WM8973L
w PD, Rev 4.5, December 2011
43
Figure 24 DSP/PCM Mode Audio Interface (mode B, LRP=0, Slave)
WM8973L Production Data
w PD, Rev 4.5, December 2011
44
AUDIO INTERFACE CONTROL
The register bits controlling audio format, word length and master / slave mode are summarised in
Table 34. MS selects audio interface operation in master or slave mode. In Master mode BCLK,
ADCLRC and DACLRC are outputs. The frequency of ADCLRC and DACLRC is set by the sample
rate control bits SR[4:0] and USB. In Slave mode BCLK, ADCLRC and DACLRC are inputs.
REGISTER
ADDRESS BIT LABEL DEFAULT DESCRIPTION
R7 (07h)
Digital Audio
Interface
Format
7 BCLKINV 0 BCLK invert bit (for master and slave
modes)
0 = BCLK not inverted
1 = BCLK inverted
6 MS 0 Master / Slave Mode Control
1 = Enable Master Mode
0 = Enable Slave Mode
5 LRSWAP 0 Left/Right channel swap
1 = swap left and right DAC data in
audio interface
0 = output left and right data as normal
4 LRP 0 right, left and i2s modes – LRCLK
polarity
1 = invert LRCLK polarity
0 = normal LRCLK polarity
DSP Mode – mode A/B select
1 = MSB is available on 1st BCLK rising
edge after LRC rising edge (mode B)
0 = MSB is available on 2nd BCLK rising
edge after LRC rising edge (mode A)
3:2 WL[1:0] 10 Audio Data Word Length
11 = 32 bits (see Note)
10 = 24 bits
01 = 20 bits
00 = 16 bits
1:0 FORMAT[1:0] 10 Audio Data Format Select
11 = DSP Mode
10 = I2S Format
01 = Left justified
00 = Right justified
Table 34 Audio Data Format Control
Note: Right Justified mode does not support 32-bit data.
AUDIO INTERFACE O UTPUT TRISTATE
Register bit TRI, register 24(18h) bit[3] can be used to tristate the ADCDAT pin and switch ADCLRC,
DACLRC and BCLK to inputs. In Slave mode (MASTER=0) ADCLRC, DACLRC and BCLK are by
default configured as inputs and only ADCDAT will be tri-stated, (see Table 35).
REGISTER
ADDRESS BIT LABEL
DEFAULT DESCRIPTION
R24(18h)
Additional
Control (2)
3 TRI 0 Tristates ADCDAT and switches ADCLRC,
DACLRC and BCLK to inputs.
0 = ADCDAT is an output, ADCLRC, DACLRC
and BCLK are inputs (slave mode) or outputs
(master mode)
1 = ADCDAT is tristated, ADCLRC, DACLRC
and BCLK are inputs
Table 35 Tri-stating the Audio Interface
Production Data WM8973L
w PD, Rev 4.5, December 2011
45
MASTER MODE ADCLRC AND DACLRC ENABLE
In Master mode, by default ADCLRC is disabled when the ADC is disabled and DACLRC is disabled
when the DAC is disabled. Register bit LRCM, regi ster 24(18h) bit[2] changes the control so that the
ADCLRC and DACLRC are disabled only when ADC and DAC are disabled. This enables the user to
use e.g. ADCLRC for both ADC and DAC LRCLK and disable the ADC when DAC only operation is
required, (see Table 36).
REGISTER
ADDRESS BIT LABEL
DEFAULT DESCRIPTION
R24(18h)
Additional
Control (2)
2 LRCM 0 Selects disable mode for ADCLRC and
DACLRC
0 = ADCLRC disabled when ADC (Left and
Right) disabled, DACLRC disabled when
DAC (Left and Right) disabled.
1 = ADCLRC and DACLRC disabled only when
ADC (Left and Right) and DAC (Left and
Right) are disabled.
Table 36 ADCLRC/DACLRC Enable
BIT CLOCK MODE
The default master mode bit clock generator produces a bit clock frequency based on the sample rate
and input MCLK frequency as shown in Table 40. When enabled by setting the appropri ate BCM[1:0]
bits, the bit clock mode (BCM) function overrides the default master mode bit clock generator to
produce the bit clock frequency shown in the table below:
REGISTER
ADDRESS BIT LABEL
DEFAULT DESCRIPTION
R8 (08h)
Clocking and
Sample Rate
Control
8:7 BCM[1:0] 00 BCLK Frequency
00 = BCM function disabled
01 = MCLK/4
10 = MCLK/8
11 = MCLK/16
Table 37 Master Mode BCLK Frequency Control
The BCM mode bit clock generator produces 16 or 24 bit clock cycles per sample. The number of bit
clock cycles per sample in this mode is determined by the word length bits (WL[1:0]) in the Digital
Audio Interface Format register (R7). When these bits are set to 00, there will be 16 bit clock cycles
per sample. When these bits are set to 01, 10 or 11, there will be 24 bit clock cycles per sample.
Please refer to Figure 25.
The BCM generator uses the ADCLRC signal, hence the ADCLRC signal must be enabled when
using bit clock mode. To enable the ADCLRC signal, either the ADC must be powered up or, if the
ADC is not in use, the LRCM bit must be set to enable both the ADCLRC and DACLRC signals when
either the ADC or the DAC is enabled.
When the BCM function is enabled, the following restrictions apply:
1. The bit clock invert (BCLKINV) function is not available.
2. The DAC and ADC must be operated at the same sample rate.
3. DSP late digital audio interface mode is not available and must not be enabled.
Figure 25 Bit Clock Mode
Note: The shaded bit clock cycles are present only when 24-bit mode is selected. Please refer to the
"Bit Clock Mode" description for details.
WM8973L Production Data
w PD, Rev 4.5, December 2011
46
CLOCK OUTPUT
By default ADCLRC (pin 9) is the ADC word clock input/output. Under the control of ADCLRM[1:0],
register 27(1Bh) bits [8:7] the ADCLRC pin may be configured as a clock output. If ADCLRM is 01, 10
or 11 then ADCLRC pin is always an output even in slave mode or when TRI = ‘1’, (see Table 38).
The ADC then uses the DACLRC pin as its LRCLK in both master and slave modes.
REGISTER
ADDRESS BIT LABEL
DEFAULT DESCRIPTION
R27(1Bh)
Additional
Control (3)
[8:7] ADCLRM
[1:0] 00 Configures ADCLRC pin
00 = ADCLRC is ADC word clock input (slave
mode) or ADCLRC output (master mode)
01 = ADCLRC pin is MCLK output
10 = ADCLRC pin is MCLK / 5.5 output
11 = ADCLRC pin is MCLK / 6 output
Table 38 ADCLRC Clock Output
CLOCKING AND SAMPLE RATES
The WM8973L supports a wide range of master clock frequencies on the MCLK pin, and can
generate many commonly used audio sample rates directly from the master clock. The ADC and DAC
do not need to run at the same sample rate; several different combinations are possible.
There are two clocking modes:
‘Normal’ mode supports master clocks of 128fs, 192fs, 256fs, 384fs, and their multiples
(Note: fs refers to the ADC or DAC sample rate, whichever is faster)
USB mode supports 12MHz or 24MHz master clocks. This mode is intended for use in
systems with a USB interface, and eliminates the need for an external PLL to generate
another clock frequency for the audio CODEC.
REGISTER
ADDRESS BIT LABEL DEFAULT DESCRIPTION
R8 (08h)
Clocking and
Sample Rate
Control
6 CLKDIV2 0 Master Clock Divide by 2
1 = MCLK is divided by 2
0 = MCLK is not divided
5:1 SR [4:0] 00000 Sample Rate Control
0 USB 0 Clocking Mode Select
1 = USB Mode
0 = ‘Normal’ Mode
Table 39 Clocking and Sample Rate Control
The clocking of the WM8973L is controlled using the CLKDIV2, USB, and SR control bits. Setting the
CLKDIV2 bit divides MCLK by two internally. The USB bit selects between ‘Normal’ and USB mode.
Each value of SR[4:0] selects one combination of MCLK divisi on ratios and hence one combination of
sample rates (see next page). Since all sample rates are generated by dividing MCLK, their accuracy
depends on the accuracy of MCLK. If MCLK changes, the sample rates change proportionately.
Note that some sample rates (e.g. 44.1kHz in USB mode) are approximated, i.e. they differ from their
target value by a very small amount. This is not audible, as the maximum deviation is only 0.27%
(8.0214kHz instead of 8kHz in USB mode). By comparison, a half-tone step corresponds to a 5.9%
change in pitch.
The SR[4:0] bits must be set to configure the appropriate ADC and DAC sample rates in both master
and slave mode.
Production Data WM8973L
w PD, Rev 4.5, December 2011
47
MCLK
CLKDIV2=0 MCLK
CLKDIV2=1 ADC SAMPLE RATE
(ADCLRC) DAC SAMPLE RATE
(DACLRC) USB SR [4:0] FILTER
TYPE BCLK
(MS=1)
‘Normal’ Clock Mode (‘*’ indicates backward compatibility with WM8731)
12.288 MHz 24.576 MHz 8 kHz (MCLK/1536) 8 kHz (MCLK/1536) 0 00110 * 1 MCLK/4
8 kHz (MCLK/1536) 48 kHz (MCLK/256) 0 00100 * 1 MCLK/4
12 kHz (MCLK/1024) 12 kHz (MCLK/1024) 0 01000 1 MCLK/4
16 kHz (MCLK/768) 16 kHz (MCLK/768) 0 01010 1 MCLK/4
24 kHz (MCLK/512) 24 kHz (MCLK/512) 0 11100 1 MCLK/4
32 kHz (MCLK/384) 32 kHz (MCLK/384) 0 01100 * 1 MCLK/4
48 kHz (MCLK/256) 8 kHz (MCLK/1536) 0 00010 * 1 MCLK/4
48 kHz (MCLK/256) 48 kHz (MCLK/256) 0 00000 * 1 MCLK/4
96 kHz (MCLK/128) 96 kHz (MCLK/128) 0 01110 * 3 MCLK/2
11.2896MHz
22.5792MHz
8.0182 kHz (MCLK/1408) 8.0182 k Hz (MCLK/1408) 0 10110 * 1 MCLK/4
8.0182 kHz (MCLK/1408) 44.1 kHz (MCLK/256) 0 10100 * 1 MCLK/4
11.025 kHz (MCLK/1024) 11.025 kHz (MCLK/1024) 0 11000 1 MCLK/4
22.05 kHz (MCLK/512) 22.05 kHz (MCLK/512) 0 11010 1 MCLK/4
44.1 kHz (MCLK/256) 8.0182 kHz (MCLK/1408) 0 10010 * 1 MCLK/4
44.1 kHz (MCLK/256) 44.1 kHz (MCLK/256) 0 10000 * 1 MCLK/4
88.2 kHz (MCLK/128) 88.2 kHz (MCLK/128) 0 11110 * 3 MCLK/2
18.432MHz
36.864MHz
8 kHz (MCLK/2304) 8 kHz (MCLK/2304) 0 00111 * 1 MCLK/6
8 kHz (MCLK/2304) 48 kHz (MCLK/384) 0 00101 * 1 MCLK/6
12 kHz (MCLK/1536) 12 kHz (MCLK/1536) 0 01001 1 MCLK/6
16kHz (MCLK/1152) 16 kHz (MCLK/1152) 0 01011 1 MCLK/6
24kHz (MCLK/768) 24 kHz (MCLK/768) 0 11101 1 MCLK/6
32 kHz (MCLK/576) 32 kHz (MCLK/576) 0 01101 * 1 MCLK/6
48 kHz (MCLK/384) 48 kHz (MCLK/384) 0 00001 * 1 MCLK/6
48 kHz (MCLK/384) 8 kHz (MCLK/2304) 0 00011 * 1 MCLK/6
96 kHz (MCLK/192) 96 kHz (MCLK/192) 0 01111 * 3 MCLK/3
16.9344MHz
33.8688MHz
8.0182 kHz (MCLK/2112) 8.0182 k Hz (MCLK/2112) 0 10111 * 1 MCLK/6
8.0182 kHz (MCLK/2112) 44.1 kHz (MCLK/384) 0 10101 * 1 MCLK/6
11.025 kHz (MCLK/1536) 11.025 kHz (MCLK/1536) 0 11001 1 MCLK/6
22.05 kHz (MCLK/768) 22.05 kHz (MCLK/768) 0 11011 1 MCLK/6
44.1 kHz (MCLK/384) 8.0182 kHz (MCLK/2112) 0 10011 * 1 MCLK/6
44.1 kHz (MCLK/384) 44.1 kHz (MCLK/384) 0 10001 * 1 MCLK/6
88.2 kHz (MCLK/192) 88.2 kHz (MCLK/192) 0 11111 * 3 MCLK/3
USB Mode (‘*’ indicates backward compatibility with WM8731)
12.000MHz 24.000MHz 8 kHz (MCLK/1500) 8 kHz (MCLK/1500) 1 00110 * 0 MCLK
8 kHz (MCLK/1500) 48 kHz (MCLK/250) 1 00100 * 0 MCLK
8.0214 kHz (MCLK/1496) 8.0214kHz (MCLK/1496) 1 10111 * 1 MCLK
8.0214 kHz (MCLK/1496) 44.118 kHz (MCLK/272) 1 10101 * 1 MCLK
11.0259 kHz (MCLK/1088) 11.0259kHz (MCLK/1088) 1 11001 1 MCLK
12 kHz (MCLK/1000) 12 kHz (MCLK/1000) 1 01000 0 MCLK
16kHz (MCLK/750) 16kHz (MCLK/750) 1 01010 0 MCLK
22.0588kHz (MCLK/544) 22.0588kHz (MCLK/544) 1 11011 1 MCLK
24kHz (MCLK/500) 24kHz (MCLK/500) 1 11100 0 MCLK
32 kHz (MCLK/375) 32 kHz (MCLK/375) 1 01100 * 0 MCLK
44.118 kHz (MCLK/272) 8.0214kHz (MCLK/1496) 1 10011 * 1 MCLK
44.118 kHz (MCLK/272) 44.118 kHz (MCLK/272) 1 10001 * 1 MCLK
48 kHz (MCLK/250) 8 kHz (MCLK/1500) 1 00010 * 0 MCLK
48 kHz (MCLK/250) 48 kHz (MCLK/250) 1 00000 * 0 MCLK
88.235kHz (MCLK/136) 88.235kHz (MCLK/136) 1 11111 * 3 MCLK
96 kHz (MCLK/125) 96 kHz (MCLK/125) 1 01110 * 2 MCLK
Table 40 Master Clock and Sample Rates
WM8973L Production Data
w PD, Rev 4.5, December 2011
48
CONTROL INTERFACE
SELECTION OF CONTROL MODE
The WM8973L is controlled by writing to registers through a serial control interface. A control word
consists of 16 bits. The first 7 bits (B15 to B9) are address bits that select which control register is
accessed. The remaining 9 bits (B8 to B0) are data bits, corresponding to the 9 bits in each control
register. The control interface can operate as either a 3-wire or 2-wire MPU interface. The MODE pin
selects the interface format.
MODE INTERFACE FORMAT
Low 2 wire
High 3 wire
Table 41 Control Interface Mode Selection
3-WIRE SERIAL CONTROL MODE
In 3-wire mode, every rising edge of SCLK cl ocks in one data bit from the SDIN pin. A rising edge on
CSB latches in a complete control word consisting of the last 16 bits.
B15 B14 B13 B12 B11 B10 B9 B8 B7 B6 B5 B4 B3 B2 B1 B0
SDIN
SCLK
CSB
control register address control register data bits
latch
Figure 26 3-Wire Serial Control Interface
2-WIRE SERIAL CONTROL MODE
The WM8973L supports software control via a 2-wire serial bus. Many devices can be controlled by
the same bus, and each device has a unique 7-bit address (this is not the same as the 7-bit address
of each register in the WM8973L).
The WM8973L operates as a slave device only. The controller indicates the start of data transfer with
a high to low transition on SDIN while SCLK remains high. This indicates that a device address and
data will follow. All devices on the 2-wire bus respond to the start condition and shift in the next eight
bits on SDIN (7-bit address + Read/Write bit, MSB first). If the device address recei ved matches the
address of the WM8973L and the R/W bit is ‘0’, indicating a write, then the WM8973L responds by
pulling SDIN low on the next clock pulse (ACK). If the address is not recognised or the R/W bit is ‘1’,
the WM8973L returns to the idle condition and wait for a new start condition and valid address.
Once the WM8973L has acknowledged a correct address, the controller sends the first byte of control
data (B15 to B8, i.e. the WM8973L register address plus the first bit of register data). The WM8973L
then acknowledges the first data byte by pulling SDIN low for one clock pulse. The controller then
sends the second byte of control data (B7 to B0, i.e. the remaining 8 bits of register data), and the
WM8973L acknowledges again by pulling SDIN low.
The transfer of data is complete when there is a low to high transition on SDIN while SCLK is high.
After receiving a complete address and data sequence the WM8973L returns to the idle state and
waits for another start condition. If a start or stop condition is detected out of sequence at any point
during data transfer (i.e. SDIN changes while SCLK is high), the device jumps to the idle condition.
SDIN
SCLK
register address and
1st register data bit
DEVICE ADDRESS
(7 BI TS) RD / WR
BIT ACK
(LOW) CONTROL BYTE 1
(BITS 15 TO 8) CONTROL BYTE 2
(BITS 7 T O 0)
remaining 8 bits of
register data STOPSTART
ACK
(LOW) ACK
(LOW)
Figure 27 2-Wire Serial Control Interface
Production Data WM8973L
w PD, Rev 4.5, December 2011
49
The WM8973L has two possible device addresses, which can be selected using the CSB pin.
CSB STATE DEVICE ADDRESS
Low 0011010 (0 x 34h)
High 0011011 (0 x 36h)
Table 42 2-Wire MPU Interface Address Selection
POWER SUPPLIES
The WM8973L can use up to four separate power supplies:
AVDD / AGND: Analogue supply, powers all analogue functions except the headphone drivers.
AVDD can range from 1.8V to 3.6V and has the most significant impact on overall power
consumption (except for power consumed in the headphone). A large AVDD slightly improves
audio quality.
HPVDD / HPGND: Headphone supply, powers the headphone drivers. HPVDD is normally tied
to AVDD, but it requires separate layout and decoupling capacitors to curb harmonic distortion.
If HPVDD is lower than AVDD, the output signal may be clipped.
DCVDD: Digital core supply, powers all digital functions except the audio and control interfaces.
DCVDD can range from 1.42V to 3.6V, and has no effect on audio quality. The return path for
DCVDD is DGND, which is shared with DBVDD.
DBVDD: Digital buffer supply, powers the audio and control interface buffers. This makes it
possible to run the digital core at very low voltages, saving power, while interfacing to other
digital devices using a higher voltage. DBVDD draws much less power than DCVDD, and has
no effect on audio quality. DBVDD can range from 1.8V to 3.6V. The return path for DBVDD is
DGND, which is shared with DCVDD.
It is possible to use the same supply voltage on all four. However, digital and analogue supplies
should be routed and decoupled separately to keep digital switching noise out of the analogue signal
paths.
POWER MANAGEMENT
The WM8973L has two control registers that allow users to select which functions are active. For
minimum power consumption, unused functions should be disabled. To avoid any pop or click noise,
it is important to enable or disable functions in the correct order (see Applications Information).
VMIDSEL is the enable for the Vmid reference, which defaults to disabled and can be enabled as a
50k potential divider or, for l ow power maintenance of Vref when all other blocks are disabled, as a
500k potential divider.
WM8973L Production Data
w PD, Rev 4.5, December 2011
50
REGISTER
ADDRESS BIT LABEL DEFAULT DESCRIPTION
R25 (19h)
Power
Management
(1)
8:7 VMIDSEL 00 Vmid divider enable and select
00 – Vmid disabled (for OFF mode)
01 – 50k divider enabled (for
playback/record)
10 – 500k divider enabled (for low-power
standby)
11 – 5k divider enabled (for fast start-up)
6 VREF 0 VREF (necessary for all other functions)
0 = Power down
1 = Power up
5 AINL 0 Analogue in PGA Left
0 = Power down
1 = Power up
4 AINR 0 Analogue in PGA Ri ght
0 = Power down
1 = Power up
3 ADCL 0 ADC Left
0 = Power down
1 = Power up
2 ADCR 0 ADC Right
0 = Power down
1 = Power up
1 MICB 0 MICBIAS
0 = Power down
1 = Power up
R26 (1Ah)
Power
Management
(2)
8 DACL 0 DAC Left
0 = Power down
1 = Power up
7 DACR 0 DAC Right
0 = Power down
1 = Power up
6 LOUT1 0 LOUT1 Output Buffer*
0 = Power down
1 = Power up
5 ROUT1 0 ROUT1 Output Buffer*
0 = Power down
1 = Power up
4 LOUT2 0 LOUT2 Output Buffer*
0 = Power down
1 = Power up
3 ROUT2 0 ROUT2 Output Buffer*
0 = Power down
1 = Power up
2 MONO 0 MONOOUT Output Buffer and Mono Mixer
0 = Power down
1 = Power up
1 OUT3 0 OUT3 Output Buffer
0 = Power down
1 = Power up
* The left mixer is enabled when LOUT1=1 or LOUT2=1. The right mixer is enabled when
ROUT1=1 or ROUT2=1.
Table 43 Power Management
Production Data WM8973L
w PD, Rev 4.5, December 2011
51
STOPPING THE MASTER CLOCK
In order to minimise power consumed in the digital core of the WM8973L, the master clock may be
stopped in Standby and OFF modes. If this cannot be done externally at the clock source, the
DIGENB bit (R25, bit 0) can be set to stop the MCLK signal from propagating into the device core. In
Standby mode, setting DIGENB will typically provide an additional power saving on DCVDD of 20uA.
However, since setting DIGENB has no effect on the power consumption of other system components
external to the WM8973L, it is preferable to disable the master clock at its source wherever possible.
REGISTER
ADDRESS BIT LABEL DEFAULT DESCRIPTION
R25 (19h)
Additional Control
(1)
0 DIGENB 0 Master clock disable
0: master clock enabled
1: master clock disabled
Table 44 ADC and DAC Oversampling Rate Selection
NOTE: Before DIGENB can be set, the control bits ADCL, ADCR, DACL and DACR must be set
to zero and a waiting time of 1ms must be observed. Any failure to follow this procedure may
prevent DACs and ADCs from re-starting correctly.
SAVING POWER BY REDUCING OVERSAMPLING RATE
The default mode of operation of the ADC and DAC digital filters is in 128x oversampling mode.
Under the control of ADCOSR and DACOSR the oversampling rate may be halved. This will result in
a slight decrease in noise performance but will also reduce the power consumption of the device. In
USB mode ADCOSR must be set to 0, i.e. 128x oversampling.
REGISTER
ADDRESS BIT LABEL DEFAULT DESCRIPTION
R24 (18h)
Additional Control
(2)
1 ADCOSR 0 ADC oversample rate select
1 = 64x (lowest power)
0 = 128x (best SNR)
0 DACOSR 0 DAC oversample rate select
1 = 64x (lowest power)
0 = 128x (best SNR)
Table 45 ADC and DAC Oversampling Rate Selection
ADCOSR set to ‘1’, 64x oversample mode, is not supported in USB mode (USB=1).
SAVING POWER AT HIGHER SUPPLY VOLTAGES
The analogue supplies to the WM8973L can run from 1.8V to 3.6V. By default, all analogue circuitry
on the device is optimized to run at 3.3V. This set-up is also good for all other supply voltages down
to 1.8V. At lower voltages, performance can be improved by increasing the bias current. If low power
operation is preferred the bias current can be left at the default setting. This is controlled as shown
below.
REGISTER
ADDRESS BIT LABEL DEFAULT DESCRIPTION
R23 (17h)
Additional
Control(1)
7:6 VSEL
[1:0] 11 Analogue Bias optimization
00: Highest bias current, optimized for AVDD=1.8V
01: Bias current optimized for AVDD=2.5V
1X: Lowest bias current, optimized for AVDD=3.3V
WM8973L Production Data
w PD, Rev 4.5, December 2011
52
REGISTER MAP
REGISTER ADDRESS
(Bit 15
–
9) remarks Bit[8] Bit[7] Bit[6] Bit[5] Bit[4] Bit[3] Bit[2] Bit[1] Bit[0] default page ref
R0 (00h) 0000000 Left Input volume LIVU LINMUTE LIZC LINVOL 010010111 22
R1 (01h) 0000001 Right Input volume RIVU RINMUTE RI ZC RINVOL 010010111 22
R2 (02h) 0000010 LOUT1 volume LO1VU LO1ZC LOUT1VOL[6:0] 001111001 35
R3 (03h) 0000011 ROUT1 volume RO1VU RO1ZC ROUT1VOL[6:0] 001111001 35
R4 (04h) 0000100 Reserved 0 0 0 0 0 0 0 0 0 000000000
-
R5 (05h) 0000101 ADC & DAC Control ADCDIV2 DACDIV2 ADCPOL[1:0] HPOR DACMU DEEMPH[1:0] ADCHPD 000001000
22,29,32
R6 (06h) 0000110 Reserved 0 0 0 0 0 0 0 0 0 000000000
-
R7 (07h) 0000111 Audio Interface 0 BCLKINV MS LRSWAP LRP WL[1:0] FORMAT[1:0] 000001010 44
R8 (08h) 0001000 Sample rate BCM[1:0] CLKDIV2 SR[4:0] USB 000000000 46
R9 (09h) 0001001 Reserved 0 0 0 0 0 0 0 0 0 000000000
-
R10 (0Ah) 0001010 Left DAC volume LDVU LDACVOL[7:0] 011111111 30
R11 (0Bh) 0001011 Right DAC volume RDVU RDACVOL[7:0] 011111111 30
R12 (0Ch) 0001100 Bass control 0 BB BC 0 0 BASS[3:0] 000001111 31
R13 (0Dh) 0001101 Treble control 0 0 TC 0 0 TRBL[3:0] 000001111 31
R15 (0Fh) 0001111 Reset writing to this register resets all registers to their default state not reset -
R16 (10h) 0010000 3D control 0 MODE3D 3DUC 3DLC 3DDEPTH[3:0] 3DEN 000000000 29
R17 (11h) 0010001 ALC1 ALCSEL[1:0] MAXGAIN[2:0] ALCL[3:0] 001111011 27
R18 (12h) 0010010 ALC2 0 ALCZC 0 0 0 HLD[3:0] 000000000 27
R19 (13h) 0010011 ALC3 0 DCY[3:0] ATK[3:0] 000110010 27
R20 (14h) 0010100 Noise Gate 0 NGTH[4:0] NGG[1:0] NGAT 000000000 28
R21 (15h) 0010101 Left ADC volume LAVU LADCVOL[7:0] 011000011 25
R22 (16h) 0010110 Right ADC volume RAVU RADCVOL[7:0] 011000011 25
R23 (17h) 0010111 Additional control(1) TSDEN VSEL[1:0] DMONOMIX[1:0] DATSEL[1:0] DACINV TOEN 011000000
21,22,32,39
R24 (18h) 0011000 Additional control(2) OUT3SW[1:0] HPSWEN
HPSWPOL
ROUT2INV
TRI LRCM ADCOSR DACOSR 000000000
36, 38,Error!
Bookmark
not defined.
R25 (19h) 0011001 Pwr Mgmt (1) VMIDSEL[1:0] VREF AINL AINR ADCL ADCR MICB DIGENB 000000000 50
R26 (1Ah) 0011010 Pwr Mgmt (2) DACL DACR LOUT1 ROUT1 LOUT2 ROUT2 MONO OUT3 0 000000000 50
R27 (1Bh) 0011011 Additional Control (3) ADCLRM[1:0] VROI HPFLREN 0 0 0 0 0 000000000 35
R31 (1Fh) 0011111 ADC input mode DS MONOMIX[1:0] RDCM LDCM 0 0 0 0 000000000 20
R32 (20h) 0100000 ADCL signal path 0 LINSEL[1:0] LMICBOOST[1:0] 0 0 0 0 000000000 20
R33 (21h) 01000 01 ADCR signal path 0 RINSEL[1:0] RMICBOOST[1 :0] 0 0 0 0 0000000 00 20
R34 (22h) 0100010 Left out Mix (1) LD2LO LI2LO LI2LOVOL[2:0] 0 LMIXSEL[2:0] 001010000 33
R35 (23h) 0100011 Left out Mix (2) RD2LO RI2LO RI2LOVOL[2:0] 0 0 0 0 001010000 33
R36 (24h) 0100100 Right out Mix (1) LD2RO LI2RO LI2ROVOL[2:0] 0 RMIXSEL[2:0] 001010000 34
R37 (25h) 0100101 Right out Mix (2) RD2RO RI2RO RI2ROVOL[2:0] 0 0 0 0 001010000 34
R38 (26h) 0100110 Mono out Mix (1) LD2MO LI2MO LI2MOVOL[2:0] 0 0 0 0 001010000 34
R39 (27h) 0100111 Mono out Mix (2) RD2MO RI2MO RI2MOVOL[2:0] 0 0 0 0 001010000 34
R40 (28h) 0101000 LOUT2 volume LO2VU LO2ZC LOUT2VOL[6:0] 001111001 36
R41 (29h) 0101001 ROUT2 volume RO2VU RO2ZC ROUT2VOL[6:0] 001111001 36
R42 (2Ah) 0101010 MONOOUT volume 0 MOZC MOUTVOL[6:0] 001111001 36
Production Data WM8973L
w PD, Rev 4.5, December 2011
53
DIGITAL FILTER CHARACTERISTICS
The ADC and DAC employ different digital filters. There are 4 types of digital filter, called Type 0, 1, 2
and 3. The performance of Types 0 and 1 is listed in the table below, the responses of all filters is
shown in the proceeding pages.
PARAMETER TEST CONDITIONS MIN TYP MAX UNIT
ADC Filter Type 0 (USB Mode, 250fs operation)
Passband +/- 0.05dB 0 0.416fs
-6dB 0.5fs
Passband Ripple +/- 0.05 dB
Stopband 0.584fs
Stopband Attenuation f > 0.584fs -60 dB
ADC Filter Type 1 (USB mode, 272fs or Normal mode operation)
Passband +/- 0.05dB 0 0.4535fs
-6dB 0.5fs
Passband Ripple +/- 0.05 dB
Stopband 0.5465fs
Stopband Attenuation f > 0.5465fs -60 dB
High Pass Filter Corner
Frequency -3dB 3.7 Hz
-0.5dB 10.4
-0.1dB 21.6
DAC Filter Type 0 (USB mode, 250fs operation)
Passband +/- 0.03dB 0 0.416fs
-6dB 0.5fs
Passband Ripple +/-0.03 dB
Stopband 0.584fs
Stopband Attenuation f > 0.584fs -50 dB
DAC Filter Type 1 (USB mode, 272fs or Normal mode operation)
Passband +/- 0.03dB 0 0.4535fs
-6dB 0.5fs
Passband Ripple +/- 0.03 dB
Stopband 0.5465fs
Stopband Attenuation f > 0.5465fs -50 dB
Table 46 Digital Filter Characteristics
DAC FILTERS ADC FILTERS
Mode Group Delay Mode Group Delay
0 (250 USB) 11/FS 0 (250 USB) 13/FS
1 (256/272) 16/FS 1 (256/272) 23/FS
2 (250 USB, 96k mode) 4/FS 2 (250 USB, 96k mode) 4/FS
3 (256/272, 88.2/96k mode) 3/FS 3 (256/272, 88.2/96k mode) 5/FS
Table 47 ADC/DAC Digital Filters Group Delay
TERMINOLOGY
1. Stop Band Attenuation (dB) – the degree to which the frequency spectrum is attenuated (outside audio band)
2. Pass-band Ripple – any variation of the frequency response in the pass-band region
WM8973L Production Data
w PD, Rev 4.5, December 2011
54
DAC FILTER RESPONSES
-100
-80
-60
-40
-20
0
0 0.5 1 1.5 2 2.5 3
Response (dB)
Frequency (Fs)
-0.06
-0.05
-0.04
-0.03
-0.02
-0.01
0
0.01
0.02
0 0.05 0.1 0.15 0.2 0.25 0.3 0.35 0.4 0.45 0.5
Response (dB)
Frequency (Fs)
Figure 28 DAC Digital Filter Frequency Response – Type 0 Figure 29 DAC Digital Filter Ripple – Type 0
-100
-80
-60
-40
-20
0
0 0.5 1 1.5 2 2.5 3
Response (dB)
Frequency (Fs)
-0.06
-0.05
-0.04
-0.03
-0.02
-0.01
0
0.01
0.02
0 0.05 0.1 0.15 0.2 0.25 0.3 0.35 0.4 0.45 0.5
Response (dB)
Frequency (Fs)
Figure 30 DAC Digital Filter Frequency Response – Type 1 Figure 31 DAC Digital Filter Ripple – Type 1
-100
-80
-60
-40
-20
0
0 0.5 1 1.5 2 2.5 3
Response (dB)
Frequency (Fs)
-0.06
-0.05
-0.04
-0.03
-0.02
-0.01
0
0.01
0.02
0 0.05 0.1 0.15 0.2 0.25
Response (dB)
Frequency (Fs)
Figure 32 DAC Digital Filter Frequency Response – Type 2 Figure 33 DAC Digi tal Filter Ripple – Type 2
Production Data WM8973L
w PD, Rev 4.5, December 2011
55
-100
-80
-60
-40
-20
0
0 0.5 1 1.5 2 2.5 3
Response (dB)
Frequency (Fs)
-0.25
-0.2
-0.15
-0.1
-0.05
0
0.05
0.1
0.15
0.2
0.25
0 0.05 0.1 0.15 0.2 0.25
Response (dB)
Frequency (Fs)
Figure 34 DAC Digital Filter Frequency Response – Type 3 Figure 35 DAC Digital Filter Ripple – Type 3
ADC FILTER RESPONSES
-100
-80
-60
-40
-20
0
0 0.5 1 1.5 2 2.5 3
Response (dB)
Frequency (Fs)
-0.04
-0.03
-0.02
-0.01
0
0.01
0.02
0.03
0.04
0 0.05 0.1 0.15 0.2 0.25 0.3 0.35 0.4 0.45 0.5
Response (dB)
Frequency (Fs)
Figure 36 ADC Digital Filter Frequency Response – Type 0 Figure 37 ADC Digital Filter Ripple – Type 0
-100
-80
-60
-40
-20
0
0 0.5 1 1.5 2 2.5 3
Response (dB)
Frequency (Fs)
-0.06
-0.05
-0.04
-0.03
-0.02
-0.01
0
0.01
0.02
0 0.05 0.1 0.15 0.2 0.25 0.3 0.35 0.4 0.45 0.5
Response (dB)
Frequency (Fs)
Figure 38 ADC Digital Filter Frequency Response – Type 1 Figure 39 ADC Digital Filter Ripple – Type 1
WM8973L Production Data
w PD, Rev 4.5, December 2011
56
-100
-80
-60
-40
-20
0
0 0.5 1 1.5 2 2.5 3
Response (dB)
Frequency (Fs)
-0.25
-0.2
-0.15
-0.1
-0.05
0
0.05
0.1
0.15
0.2
0.25
0 0.05 0.1 0.15 0.2 0.25
Response (dB)
Frequency (Fs)
Figure 40 ADC Digital Filter Frequency Response – Type 2 Figure 41 ADC Digital Filter Ripple – Type 2
-100
-80
-60
-40
-20
0
0 0.5 1 1.5 2 2.5 3
Response (dB)
Frequency (Fs)
-0.25
-0.2
-0.15
-0.1
-0.05
0
0.05
0.1
0.15
0.2
0.25
0 0.05 0.1 0.15 0.2 0.25
Response (dB)
Frequency (Fs)
Figure 42 ADC Digital Filter Frequency Response – Type 2 Figure 43 ADC Digital Filter Ripple – Type 3
DE-EMPHASIS FILTER RESPONSES
-10
-8
-6
-4
-2
0
0 2000 4000 6000 8000 10000 12000 14000 1600
0
Response (dB)
Frequency (Fs)
-0.4
-0.3
-0.2
-0.1
0
0.1
0.2
0.3
0.4
0 2000 4000 6000 8000 10000 12000 14000 16000
Response (dB)
Frequency (Fs)
Figure 44 De-emphasis Frequency Response (32kHz) Figure 45 De-emphasis Error (32kHz)
Production Data WM8973L
w PD, Rev 4.5, December 2011
57
-10
-8
-6
-4
-2
0
0 5000 10000 15000 2000
0
Response (dB)
Frequency (Fs)
-0.4
-0.3
-0.2
-0.1
0
0.1
0.2
0.3
0.4
0 5000 10000 15000 20000
Response (dB)
Frequency (Fs)
Figure 46 De-emphasis Frequency Response (44.1kHz) Figure 47 De-emphasis Error (44.1kHz)
-10
-8
-6
-4
-2
0
0 5000 10000 15000 20000
Response (dB)
Frequency (Fs)
-0.4
-0.3
-0.2
-0.1
0
0.1
0.2
0.3
0.4
0 5000 10000 15000 20000
Response (dB)
Frequency (Fs)
Figure 48 De-emphasis Frequency Response (48kHz) Figure 49 De-emphasis Error (48kHz)
HIGHPASS FILTER
The WM8973L has a selectable digital highpass filter in the ADC filter path to remove DC offsets. The filter response is
characterised by the following polynomial:
Figure 50 ADC Highpass Filter Response
1 - z
-1
1 - 0.9995z
-1
H(z) =
-15
-10
-5
0
0 0.0005 0.001 0.0015 0.002
Response (dB)
Frequency (Fs)
WM8973L Production Data
w PD, Rev 4.5, December 2011
58
APPLICATIONS INFORMATIO N
RECOMMENDED EXTERNAL COMPONENTS
Figure 51 Recommended External Components Diagram
Production Data WM8973L
w PD, Rev 4.5, December 2011
59
LINE INPUT CONFIGURATION
When LINPUT1/RINPUT1 or LINPUT2/RINPUT2 are used as line inputs, the microphone boost and
ALC functions should normally be disabled.
In order to avoid clipping, the user must ensure that the input signal does not exceed AVDD. This
may require a potential divider circuit in some applications. It is also recommended to remove RF
interference picked up on any cables using a simple first-order RC filter, as high-frequency
components in the input signal may otherwise cause aliasing distortion in the audio band. AC signals
with no DC bias should be fed to the WM8973L through a DC blocking capacitor, e.g. 1F.
MICROPHONE INPUT CONFIGURATION
Figure 52 Recommended Circuit for Line Input
For interfacing to a microphone, the ALC function should be enabled and the microphone boost
switched on. Microphones held close to a speaker’s mouth would normally use the 13dB gain setting,
while tabletop or room microphones would need a 29dB boost.
The recommended application circuit is shown above. R1 and R2 form part of the biasing network
(refer to Microphone Bias section). R1 connected to MICBIAS is necessary only for electret type
microphones that require a voltage bias. R2 should always be present to prevent the microphone
input from charging to a high voltage which may damage the microphone on connection. R1 and R2
should be large so as not to attenuate the signal from the microphone, which can have source
impedance greater than 2kOhm. C1 together with the source impedance of the microphone and the
WM8973L input impedance forms an RF filter. C2 is a DC blocking capacitor to allow the microphone
to be biased at a different DC voltage to the MICIN signal.
MINIMISING POP NOISE AT THE ANALOGUE OUTPUTS
To minimise any pop or click noise when the system is powered up or down, the following procedures
are recommended.
POWER UP
Switch on power supplies. By default the WM8973L is in Standby Mode, the DAC is
digitally muted and the Audio Interface, Line outputs and Headphone outputs are all OFF
(DACMU = 1 Power Management registers 1 and 2 are all zeros).
Enable Vmid and VREF.
Enable DACs as required
Enable line and / or headphone output buffers as required.
Set DACMU = 0 to soft-un-mute the audio DACs.
POWER DOWN
Set DACMU = 1 to soft-mute the audio DACs.
Disable all output buffers.
Switch off the power supplies.
R2
47kOhm C1
220pF
C2
1uF
A
GND
A
GND
A
GND
LINPUT1/2/3
RINPUT1/2/3
FROM
MICROPHONE
R1
680 Ohm to 2.2kOhm
check microphone's specification
MICBIAS
WM8973L Production Data
w PD, Rev 4.5, December 2011
60
POWER MANAGEMENT EXAMPLES
OPERATION MODE POWER MANAGEMENT (1) POWER MANAGEMENT (2)
VREF
AINL/R
PGAs ADCs DACs Output Buffers
PGL PGR ADL ADR MBI DAL DAR LO1 RO1 LO2 RO2 MO HPD
Stereo Headphone Playback 1 0 0 0 0 0 0 1 1 1 1 0 0 0 x
Stereo Line-in Record 1 1 1 1 1 1 0 0 0 0 0 0 0 0 0
Stereo Microphone Record 1 1 1 1 1 1 1 0 0 0 0 0 0 0 0
Mono Microphone Record 1 1 1 0 1 0 1 0 0 0 0 0 0 0 0
Stereo Line-in to Headphone Out 1 1 0 0 0 0 0 0 0 1 1 0 0 0 x
Phone Call 1 1 1 0 0 0 1 0 0 1 1 0 0 1 x
Speaker Phone Call [ROUT2INV = 1] 1 1 1 0 0 0 1 0 0 0 0 1 1 1 0
Record Phone Call [L channel = mic with
boost, R channel = RX, enable mono mix] 1 1 1 1 1 1 1 0 0 1 1 0 0 1 x
Table 48 Register Settings for Power Management
Production Data WM8973L
w PD, Rev 4.5, December 2011
61
PACKAGE DIMENSIONS
DM101.A
FL: 32 PIN QFN PLASTIC PACKAGE 5 X 5 X 0.9 mm BODY, 0.50 mm LEAD PITCH
E2
b
B
16 15
8
9
e
C0.08
Cccc
A
A1
C
A3
SEATING PLANE
1
L
INDEX AREA
(D/2 X E/2)
TOP VIEW
D
Caaa
2 X
Caaa
2 X
E
1
17
24
25 32
D2
BC
bbbMA
5
4
NOTES:
1. DIMENSION b APPLIES TO METALLIZED TERMINAL AND IS MEASURED BETWEEN 0.15 mm AND 0.30 mm FROM TERMINAL TIP.
2. FALLS WITHIN J E DEC, MO-220, VARIATION VHHD-5.
3. ALL DIMENSIONS ARE IN MILLIMETRES.
4. THE TERMINAL #1 IDENTIFIER AND TERMINAL NUMBERING CONVENTION SHALL CONFORM TO JEDEC 95-1 SPP-002.
5. COPLANARITY APPLIES TO THE EXPOSED HEAT SINK SLUG AS WELL AS THE TERMINALS.
6. REFER TO APPLICATION NOTE WAN_0118 FOR FURTHER INFORMATION REGARDING PCB FOOTPRINTS AND QFN PACKAGE SOLDERING.
7. THIS DRAWING IS SUBJECT TO CHANGE WITHOUT NOTICE.
DETAIL 1
A3 G
T
H
W
b
Exposed lead
Half etch tie bar
Dimensions (mm)
Symbols MIN NOM MAX NOTE
A
A1
A3
0.80 0.90 1.00
0.05
0.02
00.203 REF
b
D
D2
E
E2
e
L
0.300.18 5.00 BSC 3.60
3.45
3.30
0.50 BSC
0.30 0.40 0.50
1
2
2
5.00 BSC 3.603.453.30
0.10
aaa
bbb
ccc
REF:
0.15
0.10
JEDEC, MO-220, VARIATION VHHD-5.
Tolerances of Form and Position
0.25
H0.1
0.20
G
T0.103
W0.15
DETAIL 1
DETAIL 2
DETAIL 2
EXPOSED
GROUND
PADDLE 6
EXPOSED
GROUND
PADDLE
BOTTOM VIEW
SIDE VIEW
0.30 45°
MM
WM8973L Production Data
w PD, Rev 4.5, December 2011
62
IMPORTANT NOTICE
Wolfson Microelectronics plc (“Wolfson”) products and services are sold subject to Wolfson’s terms and conditions of sale,
delivery and payment supplied at the time of order acknowledgement.
Wolfson warrants performance of its products to the specifications in effect at the date of shipment. Wolfson reserves the
right to make changes to its products and specifications or to discontinue any product or service without notice. Customers
should therefore obtain the latest version of relevant information from Wolfson to verify that the information is current.
Testing and other quality control techniques are utilised to the extent Wolfson deems necessary to support its warranty.
Specific testing of all parameters of each device is not necessarily performed unless required by law or regulation.
In order to minimise risks associated with customer applications, the customer must use adequate design and operating
safeguards to minimise inherent or procedural hazards. Wolfson is not liable for applications assistance or customer
product design. The customer is solely responsible for its selection and use of Wolfson products. Wolfs on is not liable for
such selection or use nor for use of any circuitry other than circuitry entirely embodied in a Wolfson product.
Wolfson’s products are not intended for use in life support systems, appliances, nuclear systems or systems where
malfunction can reasonably be expected to result in personal injury, death or severe property or environmental damage.
Any use of products by the customer for such purposes is at the customer’s own risk.
Wolfson does not grant any licence (express or implied) under any patent right, copyright, mask work right or other
intellectual property right of Wolfson covering or relating to any combination, machine, or process in which its products or
services might be or are used. Any provision or publication of any third party’s products or services does not constitute
Wolfson’s approval, licence, warranty or endorsement thereof. Any third party trade marks contained in this document
belong to the respective third party owner.
Reproduction of information from Wolfson datasheets is permissible only if reproduction is without alteration and is
accompanied by all associated copyright, proprietary and other notices (including this notice) and conditions. Wolfson is
not liable for any unauthorised alteration of such information or for any reliance placed thereon.
Any representations made, warranties given, and/or liabilities accepted by any person which differ from those contained in
this datasheet or in Wolfson’s standard terms and conditions of sale, delivery and payment are made, given and/or
accepted at that person’s own risk. Wolfson is not liable for any such representations, warranties or liabilities or for any
reliance placed thereon by any person.
ADDRESS:
Wolfson Microelectronics plc
Westfield House
26 Westfield Road
Edinburgh
EH11 2QB
United Kingdom
Tel :: +44 (0)131 272 7000
Fax :: +44 (0)131 272 7001
Email :: sales@wolfsonmicro.com
Production Data WM8973L
w PD, Rev 4.5, December 2011
63
REVISION HISTORY
DATE REV ORIGINATOR CHANGES
06/12/11 4.5 JMacD Order codes changed from WM8973LGEFL/V and WM8973LGEFL/RV to
WM8973CLGEFL/V and WM8973CLGEFL/RV to reflect change to copper wire
bonding.
06/12/11 4.5 JMacD Package diagram changed to DM101.A
06/12/11 4.5 JMacD Important Notice updated
