General Description
The MAX3657 is a transimpedance preamplifier for
receivers operating up to 155Mbps. The low noise, high
gain, and low-power dissipation make it ideal for Class-B
and Class-C passive optical networks (PONs).
The circuit features 14nA input-referred noise, 130MHz
bandwidth, and 2mA input overload. Low jitter is
achieved without external compensation capacitors.
Operating from a +3.3V supply, the MAX3657 con-
sumes only 76mW power. An integrated filter resistor
provides positive bias for the photodiode. These fea-
tures, combined with a small die size, allow easy
assembly into a TO-46 header with a photodiode. The
MAX3657 includes an average photocurrent monitor.
The MAX3657 has a typical optical sensitivity of -38dBm
(0.9A/W), which exceeds the Class-C PON require-
ments. Typical overload is 0dBm. The MAX3657 is avail-
able in die form with both output polarities (MAX3657E/D
and MAX3657BE/D.) The MAX3657 is also available in a
12-pin, 3mm x 3mm thin QFN package.
Applications
Optical Receivers (Up to 155Mbps Operation)
Passive Optical Networks (PONs)
SFP/SFF Transceivers
BiDi Transceivers
Features
♦14nARMS Input-Referred Noise
♦54kΩTransimpedance Gain
♦130MHz (typ) Bandwidth
♦2mAP-P Input Current—0dBm Overload Capability
♦76mW (typ) Power Dissipation
♦3.3V Single-Supply Operation
♦Average Photocurrent Monitor
MAX3657
155Mbps Low-Noise Transimpedance
Amplifier
________________________________________________________________
Maxim Integrated Products
1
Ordering Information
19-2834; Rev 3; 11/05
For pricing, delivery, and ordering information, please contact Maxim/Dallas Direct! at
1-888-629-4642, or visit Maxim’s website at www.maxim-ic.com.
*
Dice are designed to operate over a -40°C to +110°C junction
temperature (TJ) range, but are tested and guaranteed at TA=
+25°C.
Pin Configuration appears at end of data sheet.
PART TEMP RANGE PIN-PACKAGE
MAX3657ETC -40°C to +85°C 12 Thin QFN
MAX3657E/D -40°C to +85°C Die*
MAX3657BE/D -40°C to +85°C Die*
Typical Application Circuit
FILT
IN
GND
1μF
1μF
TO-46 HEADER
*OPTIONAL COMPONENT
OUT+
OUT-
MON
VCCZ
RFILT
CFILT
3.3V
COUT RLOAD
200Ω
RMON*
LIMITING AMPLIFIER
MAX3964
MAX3657
VCC
CVCC1
CVCC2
MAX3657
155Mbps Low-Noise Transimpedance
Amplifier
2 _______________________________________________________________________________________
ABSOLUTE MAXIMUM RATINGS
DC ELECTRICAL CHARACTERISTICS
(VCC1 = +2.97V to +3.63V, 200Ωload between OUT+ and OUT-, TA= -40°C to +85°C. Typical values are at VCC = +3.3V, TA= +25°C,
unless otherwise noted.) (Note 1)
Stresses beyond those listed under “Absolute Maximum Ratings” may cause permanent damage to the device. These are stress ratings only, and functional
operation of the device at these or any other conditions beyond those indicated in the operational sections of the specifications is not implied. Exposure to
absolute maximum rating conditions for extended periods may affect device reliability.
Power-Supply Voltage ...........................................-0.5V to +6.0V
Input Continuous Current ................................................±3.5mA
Voltage at OUT+, OUT-...................(VCC - 1.5V) to (VCC + 0.5V)
Voltage at FILT, MON .................................-0.5V to (VCC + 0.5V)
Continuous Power Dissipation
12-Pin TQFN (derate 14.7mW/°C above +70°C) .......1176mW
Operating Temperature Range
12-Pin TQFN ....................................................-40°C to +85°C
Operating Junction Temperature Range
Die .................................................................-40°C to +150°C
Storage Temperature Range .............................-55°C to +150°C
Lead Temperature (soldering, 10s) .................................+300°C
Die Attach Temperature...................................................+400°C
PARAMETER SYMBOL CONDITIONS MIN TYP MAX UNITS
Supply Current ICC 23 34 mA
Input Bias Voltage VIN IIN ≤ 1mA 1 1.3 V
Transimpedance Linear Range 0.95 < linearity < 1.05, referred to gain at
1µAP-P input 2µA
P-P
Small-Signal Transimpedance Z21 Differential output, IIN < 200nAP-P 44 54 65 kΩ
Output Common-Mode Voltage AC-coupled outputs VCC -
0.225 V
Output Resistance (Per Side) ROUT Single-ended output resistance 82 100 118 Ω
Maximum Differential Output Voltage VOUT
(
max
)
IIN = 2mAP-P, VOUT = (VOUT+) - (VOUT-) 170 250 450 mVP-P
Filter Resistor RFILT 640 800 960 Ω
DC Input Overload 1 1.5 mA
Monitor Nominal Gain GNOM VCC = +3.3V, +25°C (Note 2) 0.8 1 1.2 A/A
IIN = 100µA to 1mA -1.5 +1.5
Die -1.5 +2.2
IIN = 5µA TQFN package -3.0 +2.7
IIN = 2µA Die only -4.0 +3.4
Monitor Gain Stability
(Note 3) ΔG
IIN = 1µA Die only ±2.0
dB
AC ELECTRICAL CHARACTERISTICS
(VCC = +2.97V to +3.63V, 200Ωload between OUT+ and OUT-, CIN = 0.5pF, CFILT = 400pF, CVCC2 = 680pF, TA= -40°C to +85°C.
Typical values are at VCC = +3.3V, TA= +25°C, unless otherwise noted.) (Note 1)
PARAMETER SYMBOL CONDITIONS MIN TYP MAX UNITS
Small-Signal Bandwidth BW-3dB Relative to gain at 1MHz 110 MHz
Low-Frequency Cutoff -3dB, IIN = 1µA 5 25 kHz
AC Overload 2mA
P-P
Pulse-Width Distortion PWD 300nAP-P ≤ IIN ≤ 2mAP-P 22 psP-P
f = 100MHz (Note 4) 15
Input-Referred Noise Current Inf = 117MHz 14 nARMS
RMS Noise Density f = 100MHz 1.3 pA/√Hz
Monitor Bandwidth IIN = 1µA 5 kHz
MAX3657
155Mbps Low-Noise Transimpedance
Amplifier
_______________________________________________________________________________________ 3
Note 1: Die parameters are production tested at room temperature only, but are guaranteed by design from TA= -40°C to +85°C.
AC characteristics guaranteed by design and characterization.
Note 2: GNOM = IMON (1mA) / 1mA.
Note 3: Stability is relative to the nominal gain at VCC = +3.3V, TA= +25°C. ΔG(IIN) dB = 10 log10 [ IMON(IIN) ] / [ IMON(1mA) - GNOM
x (1mA - IIN)], VMON ≤2.1V, Input tr, tf > 550ps (20% to 80%).
Note 4: Total noise integrated from 0 to f.
AC ELECTRICAL CHARACTERISTICS (12-PIN TQFN)
(VCC = +2.97V to +3.63V, RLOAD = 200Ω, CIN = 1.0pF, CFILT = 1000pF, CVCC2 = 0.01µF, TA= -40°C to +85°C. Typical values are at
VCC = +3.3V, TA= +25°C, unless otherwise noted.) (Note 1)
PARAMETER SYMBOL CONDITIONS MIN TYP MAX UNITS
Small-Signal Bandwidth BW-3dB Relative to gain at 1MHz 95 MHz
Low-Frequency Cutoff -3dB, IIN = 1µA 5 25 kHz
AC Overload εr ≥ 10 1.6 mA
Pulse-Width Distortion PWD 1µAP-P ≤ IIN ≤ 2mAP-P 22 psP-P
f = 50MHz (Note 4) 5
Input-Referred Noise Current Inf = 100MHz 13 nARMS
RMS Noise Density f = 100MHz 1.3 pA/√Hz
Typical Operating Characteristics
(MAX3657E/D. VCC = 3.3V, CIN = 0.5pF, TA = +25°C, unless otherwise noted.)
35
40
50
45
55
60
-40 0 20-20 40 60 80
SMALL-SIGNAL TRANSIMPEDANCE
vs. TEMPERATURE
MAX3657 toc01
AMBIENT TEMPERATURE (°C)
TRANSIMPEDANCE GAIN (kΩ)
0.2μAP-P
1.0μAP-P
0
30
20
10
70
60
80
50
40
90
100
-40 0 20-20 40 60 80
SUPPLY CURRENT
vs. TEMPERATURE
MAX3657 toc02
AMBIENT TEMPERATURE (°C)
SUPPLY CURRENT (mA)
0.7
0.9
0.8
1.1
1.0
1.2
1.3
-40 0 20-20 40 60 80
INPUT BIAS VOLTAGE
vs. TEMPERATURE
MAX3657 toc03
AMBIENT TEMPERATURE (°C)
INPUT BIAS VOLTAGE (V)
OUTPUT EYE DIAGRAM
(1.0μA ELECTRICAL INPUT)
MAX3657 toc10
1ns/div
50mV
-50mV
10mV
OUTPUT EYE DIAGRAM
(100μA ELECTRICAL INPUT)
MAX3657 toc11
1ns/div
200mV
-200mV
40mV
OUTPUT EYE DIAGRAM
(1mA ELECTRICAL INPUT)
MAX3657 toc12
1ns/div
200mV
-200mV
40mV
MAX3657
155Mbps Low-Noise Transimpedance
Amplifier
4 _______________________________________________________________________________________
Typical Operating Characteristics (continued)
(MAX3657E/D. VCC = 3.3V, CIN = 0.5pF, TA = +25°C, unless otherwise noted.)
100
0
0.1 1 10 100 1000 10,000
PULSE-WIDTH DISTORTION
vs. INPUT CURRENT AMPLITUDE
20
MAX3657 toc04
INPUT SIGNAL AMPLITUDE (μA)
PULSE-WIDTH DISTORTION (ps)
40
60
80
10
30
50
70
90
+85°C
+25°C
-40°C
-400
-200
-300
0
-100
100
200
300
400
-20 -10 -5-15 0 5 10 15 20
DIFFERENTIAL OUTPUT VOLTAGE
vs. INPUT CURRENT
MAX3657 toc05
INPUT CURRENT (μA)
OUTPUT VOLTAGE (mVP-P)
VFILT = GND
RLOAD = OPEN
Z21 = 108kΩ
RLOAD = 200Ω
Z21 = 54kΩ
RLOAD = 100Ω
Z21 = 36kΩ
FREQUENCY RESPONSE
FREQUENCY (Hz)
OUTPUT MAGNITUDE (dBΩ)
98
80
83
86
89
95
92
100 1M 100M10k1k 100k 10M 1G
MAX3657 toc06
DIFFERENTIAL OUTPUT
SINGLE-ENDED OUTPUT
0
50
25
175
150
225
250
200
100
75
125
275
0.1 0.5 0.70.3 0.9 1.1 1.3 1.5
BANDWIDTH vs. CAPACITANCE
MAX3657 toc07
CAPACITANCE (pF)
BANDWIDTH (MHz)
TJ = +110°C
TJ = +25°C
TJ = -40°C
0
10
20
15
25
30
35
0.2 0.4 0.6 0.8 1.0 1.2 1.4
INPUT-REFERRED RMS NOISE
vs. CAPACITANCE
MAX3657 toc08
CAPACITANCE (pF)
INPUT-REFERRED NOISE (nARMS)
TJ = -40°C
TJ = +25°C
TJ = +110°C
1.2
0
0.1 1 10 100 1000 10,000
INPUT-REFERRED RMS NOISE
vs. DC INPUT CURRENT
0.2
MAX3657 toc09
DC CURRENT IN (μA)
INPUT-REFERRED NOISE (nARMS)
1.0
0.4
0.6
0.8
TJ = +110°C
TJ = +25°C
TJ = -40°C
MAX3657
OUTPUT EYE DIAGRAM
(-30dBm OPTICAL INPUT)
MAX3657toc13
1ns/div
6mV/div
ZARLINK 1A358 PHOTODIODE + MAX3657
223-1 PRBS
OUTPUT EYE DIAGRAM
(-1dBm OPTICAL INPUT)
MAX3657toc14
1ns/div
20mV/div
ZARLINK 1A358 PHOTODIODE + MAX3657
223-1 PRBS
155Mbps Low-Noise Transimpedance
Amplifier
_______________________________________________________________________________________
5
INPUT IMPEDANCE vs. FREQUENCY
FREQUENCY (Hz)
MAGNITUDE OF INPUT IMPEDANCE (Ω)
800
300
350
400
450
500
550
600
750
700
650
100 1M 100M10k1k 100k 10M 1G
MAX3657 toc15
TJ = +25°C TJ = -40°C
TJ = +110°C
SMALL SIGNAL
Typical Operating Characteristics (continued)
(MAX3657E/D. VCC = 3.3V, CIN = 0.5pF, TA = +25°C, unless otherwise noted.)
PIN
NAME
FUNCTION
1, 9, 11
N.C.
No Connection. Do not connect.
2
GND
Negative Supply Voltage. Both GND and GNDZ must be connected to ground.
3
GNDZ
Negative Supply Voltage. Both GND and GNDZ must be connected to ground.
4
MON
Photocurrent Monitor. This is a current output. Connect a resistor between MON and ground to monitor the
average photocurrent.
5 IN Signal Input. Connect to photodiode anode.
6
FILT
Filter Connection (Optional). Use to bias the photodiode cathode. An internal 800Ω on-chip resistor is connected
between this pin and VCCZ; an external decoupling capacitor connected to this pin forms a filter (see the Design
Procedure section).
7
VCCZ
Power-Supply Voltage. Both VCC and VCCZ must be connected to the supply.
8
VCC
Power-Supply Voltage. Both VCC and VCCZ must be connected to the supply.
10
OUT+
Positive Data Output. This output has 100Ω back termination, increasing input current causes OUT+ to increase.
12
OUT-
Negative Data Output. This output has 100Ω back termination, increasing input current causes OUT- to decrease.
Pin Description
MAX3657
155Mbps Low-Noise Transimpedance
Amplifier
6 _______________________________________________________________________________________
Detailed Description
The MAX3657 transimpedance amplifier is designed for
155Mbps fiber-optic applications. The functional dia-
gram of the MAX3657 comprises a transimpedance
amplifier, a voltage amplifier, a DC-cancellation circuit,
and a CML output buffer.
Transimpedance Amplifier
The signal current at the input flows into the summing
node of a high-gain amplifier. Shunt feedback through
resistor RFconverts this current into a voltage. Schottky
diodes clamp the output signal for large input currents
(Figure 1).
Voltage Amplifier
The voltage amplifier provides additional gain and con-
verts the transimpedance amplifier single-ended output
signal into a differential signal.
Output Buffer
The output buffer provides a reverse-terminated volt-
age output and is designed to drive a 200Ωdifferential
load between OUT+ and OUT-. For optimum supply-
noise rejection, the MAX3657 should be terminated with
a differential load. The MAX3657 single-ended outputs
do not drive a DC-coupled grounded load. The outputs
should be AC-coupled or terminated to VCC. If a single-
ended output is required, both the used and the unused
outputs should be terminated in a similar manner.
DC-Cancellation Circuit
The DC-cancellation circuit uses low-frequency feed-
back to remove the DC component of the input signal
(Figure 2). This feature centers the input signal within
the transimpedance amplifier’s linear range, thereby
reducing pulse-width distortion.
The DC-cancellation circuit is internally compensated
and does not require external capacitors. This circuit
minimizes pulse-width distortion for data sequences
that exhibit a 50% mark density. A mark density signifi-
cantly different from 50% causes the MAX3657 to gen-
erate pulse-width distortion. Grounding the FILT pin
disables the DC-cancellation circuit. For normal opera-
tion, the DC-cancellation circuit must be enabled.
The DC-cancellation current is drawn from the input and
creates noise. For low-level signals with little or no DC
component, the added noise is insignificant. However,
amplifier noise increases for signals with significant DC
component (see the
Typical Operating Characteristics
).
Functional Diagram
MAX3657
155Mbps Low-Noise Transimpedance
Amplifier
_______________________________________________________________________________________ 7
Photocurrent Monitor
The MAX3657 includes an average photocurrent monitor.
The current at MON is approximately equal to the DC cur-
rent at IN. Best monitor accuracy is obtained when data
input edge time is longer than 500ps.
Design Procedure
Select Photodiode
Noise performance and bandwidth are adversely affected
by stray capacitance on the TIA input node. Select a
low-capacitance photodiode to minimize the total input
capacitance on this pin. The MAX3657 is optimized for
0.5pF of capacitance on the input. Assembling the
MAX3657 in die form using chip and wire technology
provides the lowest capacitance input and the best
possible performance.
Select CFILT
Supply voltage noise at the cathode of the photodiode
produces a current I = CPD ΔV/Δt, which reduces the
receiver sensitivity (CPD is the photodiode capaci-
tance). The filter resistor of the MAX3657, combined
with an external capacitor, can be used to reduce the
noise (see the
Typical Application Circuit
). Current gen-
erated by supply-noise voltage is divided between
CFILT and CPD. To obtain a good optical sensitivity,
select CFILT > 400pF.
Select Supply Filter
The MAX3657 requires wideband power-supply decou-
pling. Power-supply bypassing should provide low
impedance between VCC and ground for frequencies
between 10kHz and 200MHz. Use LC filtering at the
main supply terminal and decoupling capacitors as
close to the die as possible.
Select RMON
Connect a resistor between MON and ground to moni-
tor the average photocurrent. Select RMON as large as
possible:
where IMONMAX is the largest average input current
observed.
Select Coupling Capacitors
A receiver built with the MAX3657 has a bandpass fre-
quency response. The low-frequency cutoff due to the
coupling capacitors and load resistors is:
Select CCOUPLE so the low-frequency cutoff due to the
load resistors and coupling capacitors is much lower than
the low-frequency cutoff of the MAX3657. The coupling
capacitor should be 0.1µF or larger, but 1.0µF is recom-
mended for lowest jitter. Refer to Maxim Application Note
HFAN-01.1:
Choosing AC-Coupling Capacitors
for more
information.
Layout Considerations
Figure 3 shows a suggested layout for a TO header for
the MAX3657.
Wire Bonding
For high-current density and reliable operation, the
MAX3657 uses gold metalization. For best results, use
gold-wire ball-bonding techniques. Use caution if
attempting wedge bonding. Die size is 41 mils x 48 mils,
(1040µm x 1220µm) and die thickness is 15 mils (380µm).
The bond pad is 94.4µm x 94.4µm and its metal thickness
is 1.2µm. Refer to Maxim Application Note HFAN- 08.0.1:
LFC xR xC
TERM
LOAD COUPLE
=1
2π
RMON MONMAX
2.1V
I
=
Figure 1. MAX3657 Limited Outputs
AMPLITUDE
OUTPUT (LARGE SIGNALS)
TIME
OUTPUT (SMALL SIGNALS)
Figure 2. Effects of DC Cancellation on Input
AMPLITUDE INPUT FROM PHOTODIODE
TIME
INPUT AFTER DC CANCELLATION
MAX3657
155Mbps Low-Noise Transimpedance
Amplifier
8 _______________________________________________________________________________________
OUTPUT POLARITIES
REVERSED FOR MAX3567BE/D.
CASE IS GROUND.
4-PIN TO HEADER
5-PIN TO HEADER
VCC
FILT
VCCZ
GNDZ
GND
OUT-
OUT+
VCC
IN MON
CFILT
CVCC
OUT+ OUT-
PHOTODIODE
MAX3657E/D
OUTPUT POLARITIES
REVERSED FOR MAX3567BE/D.
CASE IS GROUND.
VCC
GND
FILT
VCCZ
GNDZ
GND
OUT-
OUT+
VCC
IN MON
CFILT
CVCC
OUT+ OUT-
MON
PHOTODIODE
MAX3657E/D
Figure 3. Suggested TO Header Layout
MAX3657
155Mbps Low-Noise Transimpedance
Amplifier
_______________________________________________________________________________________ 9
Understanding Bonding Coordinates and Physical Die
Size
for more information on bond-pad coordinates.
Applications Information
Optical Power Relations
Many of the MAX3657 specifications relate to the input-
signal amplitude. When working with optical receivers,
the input is sometimes expressed in terms of average
optical power and extinction ratio. Figure 4 and Table 1
show relations that are helpful for converting optical
power to input signal when designing with the MAX3657.
Optical Sensitivity Calculation
The input-referred RMS noise current (in) of the
MAX3657 generally determines the receiver sensitivity.
To obtain a system bit-error rate (BER) of 1E-10, the
signal-to-noise ratio must always exceed 12.7. The
input sensitivity, expressed in average power, can be
estimated as:
where ρis the photodiode responsivity in A/W and inis
the RMS noise current in amps. For example, with pho-
todiode responsivity of 0.9A/W, an extinction ratio of 10
and 15nA input-referred noise, the sensitivity of the
MAX3657 is:
Actual results may vary depending on supply noise, out-
put filter, limiting amplifier sensitivity, and other factors
(refer to Maxim Application Note HFAN-03.0.0:
Accurately
Estimating Optical Receiver Sensitivity
).
Input Optical Overload
Overload is the largest input the MAX3657 accepts
while meeting the pulse-width distortion specification.
Optical overload can be estimated in terms of average
power with the following equation:
For example, if photodiode responsivity is 1.0A/W, the
input overload is 0dBm.
Optical Linear Range
The MAX3657 has high gain, which limits the output for
large input signals. The MAX3657 operates in a linear
range for inputs not exceeding:
For example, with photodiode responsivity of 0.9A/W
and an extinction ratio of 10 the linear range is:
Linear Range Ax
xx
x dBm dBm=μ
⎛
⎝
⎜⎞
⎠
⎟=−10 211
209 91000 28log .
Linear Range Ar
xr x dBm
e
e
=μ+
−
⎛
⎝
⎜⎞
⎠
⎟
10 21
21
1000log ()
()ρ
Overload mA
xx dBm=⎛
⎝
⎜⎞
⎠
⎟
10 2
21000log ρ
Sensitivity xnAx
xAWxx dBm dBm=⎛
⎝
⎜⎞
⎠
⎟=−10 12 7 15 11
209 9 1000 38log .
./
Sensitivity xi x r
xxr x dBm
ne
e
=+
⎛
⎝
⎜⎞
⎠
⎟
−
10 12 7 1
21
1000log .()
()ρ
PP r
r
AVG e
e
12 1
=+
PPP P r
r
IN AVG e
e
== +
−−
102 1
1
*
Assuming a 50% average mark density.
PARAMETER SYMBOL RELATION
Average power PAVG PAVG = (P0 + P1)/2
Extinction ratio rere = P1/P0
Optical power
of a 1 P1
Optical power
of a 0 P0 P0 = 2PAVG/(re + 1)
Optical modulation
amplitude PIN
Table 1. Optical Power Relations*
Figure 4. Optical Power Relations
P0
P1
PAVG
TIME
OPTICAL POWER
PP r
r
AVG e
e
12 1
=+
PPP
Pr
r
IN
AVG e
e
==
+
−10
21
MAX3657
Interface Schematics
Equivalent Output Interface
The MAX3657 has a differential CML output structure
with 100Ωback termination (200Ωdifferentially). Figure
5 is a simplified diagram of the output interface. The
output current is divided between the internal 100Ω
resistor and the external load resistance. Because of
the CML structure, the maximum output-signal ampli-
tude is affected by load impedance. Note that the inter-
nal back termination is 100Ωsingle ended and external
termination is recommended to interface the device to
50Ωtest equipment. For example, if single-ended oper-
ation in a 50Ωsystem is required, first match the output
of the MAX3657 to the 50Ωcontrolled impedance by
placing a 100Ωpullup resistor in parallel with the out-
put. Then establish similar loading conditions on the
unused output. Note that the loading conditions affect
the overall gain of the MAX3657. Figures 6a, 6b, and 6c
show alternate interface schemes for the MAX3657.
Pad Coordinates
Table 2 lists center-pad coordinates for the MAX3657
bond pads. Refer to Maxim Application Note HFAN-
08.0.1:
Understanding Bonding Coordinates and
Physical Die Size
for more information on bond-pad
coordinates.
155Mbps Low-Noise Transimpedance
Amplifier
10 ______________________________________________________________________________________
OUT+
4.5mA
OUT-
VCC
VCC
VCC
ROUT
100Ω
ROUT
100Ω
Figure 5. Equivalent Output Interface
Table 2. Bond-Pad Information
NAME COORDINATES (µm)
PAD MAX3657 MAX3657B X Y
BP1 OUT- OUT+ 47.2 994.8
BP2 GND GND 52.2 484.6
BP3 GNDZ GNDZ 52.2 357.7
BP4 MON MON 395.5 47.2
BP5 IN IN 522.3 47.2
BP6 FILT FILT 648.5 47.2
BP7 N.C. N.C. 808.5 49.9
BP8 VCCZ VCCZ 808.5 176.8
BP9 VCC VCC 808.5 303.7
BP10 OUT+ OUT- 808.5 994.8
BP11 N.C. N.C. 741.1 859.9
MAX3657
155Mbps Low-Noise Transimpedance
Amplifier
______________________________________________________________________________________ 11
CML OUTPUT
STAGE
100Ω
*COMPONENT NOT REQUIRED IF L < 10cm.
VCC
L
100Ω∗ 100Ω∗
50Ω∗
50Ω∗
100Ω
MAX3657
50Ω50Ω
DIFFERENTIAL CML
INPUT STAGE
Figure 6a. 50
Ω
DC-Coupled Interface
CML OUTPUT
STAGE
100Ω
NOTE:
THE PARALLEL COMBINATION AT THE UNUSED OUTPUT
CAN BE REPLACED BY A SINGLE EQUIVALENT 33Ω RESISTOR.
*COMPONENT NOT REQUIRED IF L < 10cm.
L
100Ω∗ 100Ω∗
50Ω∗
100Ω
VCC
50Ω
MAX3657
50Ω
SINGLE-ENDED
INPUT STAGE
Figure 6b. 50
Ω
DC-Coupled Single-Ended Output Interface
MAX3657
155Mbps Low-Noise Transimpedance
Amplifier
12 ______________________________________________________________________________________
FILT
800Ω
VCC
Figure 7. FILT Interface
MON
VCC
Figure 8. MON Interface
CML OUTPUT
STAGE
100Ω
*COMPONENT NOT REQUIRED IF L < 10cm
L
100Ω∗ 100Ω∗
50Ω∗
100Ω
VCC
MAX3657
50Ω LOAD TO
GROUND
50Ω
50Ω
Figure 6c. 50
Ω
AC-Coupled Single-Ended Output Interface
MAX3657
155Mbps Low-Noise Transimpedance
Amplifier
______________________________________________________________________________________ 13
Chip Topographies
2
1
3
456 7
8
9
10
11
OUT- OUT+
GND
GNDZ
MON IN N.C.FILT
N.C.
VCCZ
VCC
0.048in
1.219mm
0.041in
1.041mm
Chip Information
TRANSISTOR COUNT: 417
PROCESS: Silicon bipolar
SUBSTRATE: Connected to GND
DIE SIZE: 1.04mm x 1.22mm
TOP VIEW
9
N.C.
8
VCC
7
VCCZ
12
GND
3
GNDZ
10
11N.C.
12
6
5
4
OUT-
FILT
IN
MON
MAX3657
OUT+
N.C.
TQFN
*EXPOSED PAD IS CONNECTED TO GND.
Pin Configuration
Topography for MAX3657
2
1
3
456 7
8
9
10
11
OUT+ OUT-
GND
GNDZ
MON IN N.C.FILT
N.C.
VCCZ
VCC
0.048in
1.219mm
0.041in
1.041mm
Topography for MAX3657B
MAX3657
155Mbps Low-Noise Transimpedance
Amplifier
14 ______________________________________________________________________________________
Package Information
(The package drawing(s) in this data sheet may not reflect the most current specifications. For the latest package outline information,
go to www.maxim-ic.com/packages.
12x16L QFN THIN.EPS
MAX3657
155Mbps Low-Noise Transimpedance
Amplifier
Maxim cannot assume responsibility for use of any circuitry other than circuitry entirely embodied in a Maxim product. No circuit patent licenses are
implied. Maxim reserves the right to change the circuitry and specifications without notice at any time.
Maxim Integrated Products, 120 San Gabriel Drive, Sunnyvale, CA 94086 408-737-7600 ____________________
15
© 2005 Maxim Integrated Products Printed USA is a registered trademark of Maxim Integrated Products, Inc.
Package Information (continued)
(The package drawing(s) in this data sheet may not reflect the most current specifications. For the latest package outline information,
go to www.maxim-ic.com/packages.