U4065B
Rev. A4, 06-Mar-01 1 (23)
FM Receiver
Description
The IC U4065B is a bipolar integrated FM-frontend
circuit. It contains a mixer, an oscillator, two IF
preamplifiers and an unique interference sensor. The
device is designed for high performance car radio and
home receiver applications.
Features
All frontend functions of a high performance FM-
receiver, except the RF preamplifier, are integrated
Improved dynamic range by high current double
balanced mixer design and a new AGC conception
with 3 loops on chip
Improved blocking and intermod behavior by use of
an unique “interference” sensor controlling the AGC
Easy cascading of three IF filters (ceramic) by use of
two on-chip IF preamplifiers
On-chip control functions are available for system
gain adjust (dB linear vs. dc current)
Low noise LO design
ESD protected
Block Diagram
VS
22 1 11 9810 6
17
13
3
5
7
4
211819
16
15
14
23
24
+
IF BPF IF BPF
IF BPF IF out
p
IF 2IF 1
IF gain adjust
VS
Voltage
reg.
IF BPF
ANT
Inter-
ference
mixer
Mixer
RF
PIN
ATT
RF tank
Vtune
RF tank
Local
oscill.
IF tank
LO output
Vref = 4 V
20
2
LO tank
AGC adjust
AGC level
VS
VS
12
D.N.C.
AGC
(wide band)
wide band
& IF
I F &
detector
Interference
94 8768
U4065B
Rev. A4, 06-Mar-012 (23)
Pin Description
Pin Symbol Function
1 LOBUFF Buffered local oscillator output
2 GND1 Ground of the second IF ampli-
fier
3 IF2OUT Output of the second IF ampli-
fier
4 GAINIF1 Gain control of the first
IF amplifier
5 IF2IN Input of the second IF amplifier
6 VS Supply voltage
7 IF1OUT Output of the first IF amplifier
8 GND2 Ground
9 IMIFIN Input of the amplifier for the
IM-sensor
10 AGCOUT Output of the automatic gain
control
11 IMMIXOUT Output of the intermodulation
mixer
12 D.N.C. Do not connect
Pin Symbol Function
13 AGCWB Threshold adjustment of the
wideband AGC
14 GND3 Mixer ground
15 MIXIN1 Input 1 of the double balanced
mixer
16 MIXIN2 Input 2 of the double balanced
mixer
17 VREF Reference voltage output
18 MIXOUT1 Mixer output 1
19 MIXOUT2 Mixer output 2
20 GND4 Ground of the first
IF amplifier
21 IF1IN Input of the first amplifier
22 GND5 Oscillator ground
23 LOE Local oscillator (emitter)
24 LOB Local oscillator (base)
LOBUFF
23
50
1
1 V
ESD
+94 8769
Buffered local oscillator output:
It drives the FM-input of the PLL circuit (for example
U428xBM-family). The typical parallel output resistance
at 100 MHz is 70 , the parallel output capacitance is
about 10 pF. When using an external load of 500 /
10 pF, the oscillator swing is about 100 mV. The second
harmonic of the oscillator frequency is less than
– 15 dBc.
GND1
ESD
2
8
94 8770
Ground of the second IF amplifier:
There is no internal connection to the other ground pins.
U4065B
Rev. A4, 06-Mar-01 3 (23)
IF2OUT
3
ESD
VS
Vref 94 8771
Output of the second IF amplifier:
The parallel output capacitance to ground is about 7 pF.
The external load resistance is to connect to VS. The dc
current into the pin is typically 3 mA.
Note: Supply voltage VS has to be protected against
IF-distortion
GAINIF1
17
4ESD
Vref
2 k
94 8772
Gain control of the first IF amplifier:
The gain of the first IF amplifier can be adjusted by a re-
sistor to ground. This is useful for example to com-
pensate the insertion loss tolerances of the ceramic BPF’s.
Please ensure that the output current of the pin does not
exceed 150 A in any case. Linear increasing in the cur-
rent out of GAINIF1 effects dB linear increasing of the
gain (0.15 dB/A).
I4 = 0 G= Gmin = 2 dB
I4 = 140 A G = Gmax = 22 dB
IF2IN
ESD
5
Vref 94 8773
Input of the second IF amplifier:
The parallel input resistance is 330 . The parallel input
capacitance is about 12 pF. No dc current is allowed. To
avoid overload of this stage an internal detector watches
the input level and causes current at the AGCOUT pin.
IF1OUT
ESD
330
7
VS
94 8774
Output of the first IF amplifier:
The parallel output resistance is 330 which allows the
use of a standard ceramic BPF. The parallel output capa-
citance is about 7 pF. The dc voltage at the pin is 0.5 V
less than VS.
IMIFIN
9
ESD
94 8775
Input of the IF amplifier for the IM-sensor:
The parallel input resistance is 330 . The amplifier is ex-
tremely sensitive to ac signals. A few hundred V of
IF-signal at this pin will cause current at the AGC output.
Therefore pay attention when connecting the standard ce-
ramic filter used between IMOUT and this pin. The
reference point of the filter has to be free of any ac signal.
Please avoid dc current at this pin.
U4065B
Rev. A4, 06-Mar-014 (23)
AGCOUT
10
1 k
1 V
ESD
94 8776
Output of the automatic gain control:
The AGC output is an open collector output. The current
of the pin diode is this current multiplied by the current
gain of the external PNP transistor. The dc voltage at the
pin may vary from 2 V to VS, therefore you can easily use
this pin as an indicator of the AGC regulation state.
IMMIXOUT
ESD
300
VS
1 V
11
94 8777
Output of the intermodulation mixer:
The parallel output resistance is 330 which allows the
use of a standard ceramic BPF without any further match-
ing network. Please ensure that the ground-pin of the filter
is free of ac signals.
AGCWB
25 k
32 k
ESD
13
Vref
94 8778
Threshold adjustment of the wideband AGC:
The threshold of the wideband AGC can be adjusted by
an external resistor to ground. The setting range is 10 dB.
For minimum blocking this pin is connected to ground. In
order to set the threshold to smaller levels the resistance
value should be up to a few hundred k.
MIXIN1
2.5 k
15
ESD
Vref
94 8779
Input 1 of the double balanced mixer:
The parallel input resistance is 1.2 k. The parallel input
capacitance is about 9 pF. When using the mixer unbal-
anced this pin is to be grounded for RF-signals by an
external capacitance of a few nF. DC current is not allowed.
MIXIN2
2.5 k
16
ESD
Vref
94 8780
Input 2 of the double balanced mixer:
The parallel input resistance is 1.6 k. The parallel input
capacitance is about 7 pF. The double sideband noise fig-
ure of the unbalanced mixer is about 7 dB. In the balanced
case the noise figure will be reduced by about 0.8 dB.
VREF
94 8781
4.6 V
200
ESD
VS
17
Reference voltage:
The internal temperature compensated reference voltage
is 3.9 V. It is used as bias voltage for most blocks, so the
electrical characteristics of the U4065B are widely inde-
pendent of the supply voltage. The internal output
resistance of the reference voltage is less than 10 . To
avoid internal coupling across this pin external capacitors
are required. The maximum output current is Iref = 5 mA.
U4065B
Rev. A4, 06-Mar-01 5 (23)
MIXOUT1, MIXOUT2
18 ESD
94 8782
19
Mixer output 1, 2:
The mixer output is an open collector of a bipolar transis-
tor. The minimum voltage at this pins is 5 V (VS-voltage
swing). The dc current into this pins is typically 9 mA.
Good LO- and RF suppression at the mixer output can be
achieved by symmetrical load conditions at the pins MIX-
OUT1 and MIXOUT2.
IF1IN
21
330
Vref
ESD 94 8784
Input of the first IF amplifier:
The typical input resistance is 330 . The dc voltage is
nearly the same one as the reference voltage. Please avoid
dc current at this pin.
LOE
23
ESD
94 8785
Emitter of the local oscillator:
An external capacitor is connected between LOE and
ground. The ground pin of this capacitor is to connect to
the pin GND5. GND5 is the chip internal ground of the
local oscillator.
LOB
24
ESD
94 8786
Base of the local oscillator:
The tank of the local oscillator is connected at pin LOB.
The ground pin of this tank is to connect to the pin GND5.
GND5 is the chip internal ground into pin 24 of the local
oscillator. The resonant resistance of the tank should be
about 250 . Minimum Q of the unloaded tank is 50.
U4065B
Rev. A4, 06-Mar-016 (23)
Functional Description
The U4065B FM-frontend IC is the dedicated solution for
high end car radios. A new design philosophy enables to
build up tuners with superior behavior. This philosophy
is based on the fact that the sensitivity of state of the art
designs is at the physical border and cannot be enhanced
any more. On the other hand, the spectral power density
in the FM-band increases. An improvement of reception
can only be achieved by increasing the dynamic range of
the receiver. This description is to give the designer an
introduction to get familiar with this new product and its
philosophy.
1. The Signal Path
The U4065B offers the complete signal path of an FM-
frontend including a highly linear mixer and two IF
preamplifiers. The mixer is a double balanced high cur-
rent Gilbert Cell. A high transit frequency of the internal
transistors enables the use of the emitter grounded circuit
with its favorable noise behavior. The full balanced out-
put offers LO carrier reduction.
The following IF preamplifier has a dB-linear gain adjust-
ment by dc means. Thus dif ferent ceramic filter losses can
be compensated and the overall tuner gain can be adapted
to the individual requirements. The low noise design sup-
presses post stage noise in the signal path. Input- and
output resistance is 330 to support standard ceramic fil-
ters. This was achieved without feedback, which would
cause dif ferent input impedances when varying the output
impedance.
The second IF preamplifier enables the use of three ce-
ramic filters with real 330 input- and output
termination. Feedthrough of signals is kept low. The high
level of output compression is necessary to keep up a high
dynamic range.
Beneath the signal path the local oscillator part and the
AGC signal generation can be found on chip. The local
oscillator uses the collector grounded colpitts type. A low
phase noise is achieved with this access. A mutual cou-
pling in the oscillator coil is not necessary.
2. The AGC Concept
Special care was taken to design a unique AGC concept.
It offers 3 AGC loops for different kinds of reception
conditions. The most important loop is the interference
sensor part.
In today’s high end car radios, the FM AGC is state of the
art. It is necessary to reduce the influence of 3rd and
higher order intermodulation to sustain reception in the
presence of strong signals in the band. On one hand, it
makes a sense to reduce the desired signal level by AGC
as few as possible to keep up stereo reception, on the other
hand two or more strong out of channel signals may inter-
fere and generate an intermodulation signal on the desired
frequency. By introducing input attenuation, the level of
the intermod signal decreases by a higher order, whereas
the level of the desired signal shows only a linear depen-
dency on the input attenuation. Therefore input
attenuation by pin diodes may keep up reception in the
presence of strong signals.
The standard solution to generate the pin diode current is
to pick up the RF-signal in front of the mixer. Because the
bandwidth at that point is about 1.5 MHz, this is called
wideband AGC. The threshold of AGC start is a critical
parameter . A low threshold does not allow any intermo-
dulation but has the disadvantage of blocking if there is
only one strong station on the band or if the intermod sig-
nals do not cover the desired channel. A higher AGC
threshold may tolerate a certain ground floor of intermo-
dulation. This avoids blocking, but it has the
disadvantage, that no reception is possible, if the interfer-
ing signals do generate an intermod signal inside the
desired channel. This contradiction could not be over-
come in the past.
With the new U4065B IC, a unique access to this problem
appears. This product has an interference sensor on chip.
Thus an input signal attenuation is only performed, if the
interfering signals do generate an intermod signal inside
the desired channel. If they do not, the still existing wide-
band AGC is yet active but at up to 20 dB higher levels.
The optimum AGC state is always generated.
The figures 1 to 4 illustrate the situation. In figure 1 the
AGC threshold of a standard tuner is high to avoid block-
ing. But then the intermod signal suppresses the desired
signal. The interference sensor of the U4065B takes care
that in this case the AGC threshold is kept low as illus-
trated in figure 2.
In figure 3 the situation is vice versa. The AGC threshold
of a standard tuner is kept low to avoid intermod prob-
lems. But then blocking makes the desired signal level
drop below the necessary stereo level. In this case, the
higher wideband AGC level of the U4065B enables per-
fect stereo reception.
By principle, this interference sensor is an element with
a third order characteristic. For input levels of zero, the
output level is zero, too. With increasing input level, the
output level is increased with the power of three, thus pre-
ferring intermod signals compared to linear signals. At
the same time, a down conversion to the IF level of
10.7 MHz is performed. If a corresponding 10.7 MHz IF
filter selects the intermod signals, an output is only gener-
ated, if an intermod signal inside the 10.7 MHz channel
is present.
U4065B
Rev. A4, 06-Mar-01 7 (23)
The circuit blocks interference sensor and IF & detector
build up a second IF chain. In an FM system, the max
deviation of a 3rd order intermod signal is the triple max
deviation of the desired signal. Therefore the ceramic IF
BPF between Pin 11 and Pin 9 may be a large bandwidth
type. This external part is the only additional amount for
this unique feature.
A further narrow band AGC avoids overriding the second
IF amplifier. The amplitude information of the channel is
not compressed in order to maintain multipath detection
in the IF part of the receiver.
ÇÇÇÇÇÇÇÇÇÇÇÇ
ÇÇÇÇÇÇÇÇÇÇÇÇ
ÇÇÇÇÇÇÇÇÇÇÇÇ
Stereo-level
Interfering signals
Intermod signal
Noise floor
Desired
signal
Level
Frequency
Desired
frequency
Intermod signal
94 8820
Figure 1 A high AGC threshold causes the intermod
signal to suppress the desired signal
ÇÇÇÇÇÇÇÇÇÇÇÇÇ
ÇÇÇÇÇÇÇÇÇÇÇÇÇ
ÇÇÇÇÇÇÇÇÇÇÇÇÇ
Stereo-level
Interfering signals
Intermod signal
Noise floor
Desired
signal
Level
Frequency
Desired
frequency
Intermod signal
94 8821
Figure 2 The correct AGC threshold of the U4065B
provides optimum reception
ÇÇÇÇÇÇÇÇÇÇÇÇ
ÇÇÇÇÇÇÇÇÇÇÇÇ
Stereo-level
Strong signal
Noise floor
Desired
signal
Level
Frequency
Desired
frequency
94 8822
Figure 3 A low AGC threshold causes the blocking
signal to suppress the desired signal
ÇÇÇÇÇÇÇÇÇÇÇÇÇ
ÇÇÇÇÇÇÇÇÇÇÇÇÇ
Stereo-level
Noise floor
Desired
signal
Level
Frequency
Desired
frequency
Strong signal
94 8823
Figure 4 The correct AGC threshold of the U4065B
provides optimum reception
U4065B
Rev. A4, 06-Mar-018 (23)
Absolute Maximum Ratings
Reference point is ground (Pins 2, 8, 14, 20 and 22)
Parameters Symbol Value Unit
Supply voltage VS10 V
Power dissipation at Tamb = 85°C Ptot 470 mW
Junction temperature Tj125 °C
Ambient temperature range Tamb – 30 to + 85 °C
Storage temperature range Tstg – 50 to + 125 °C
Electrostatic handling:
Human body model (HBM),
all I/O pins tested against the supply pins.
VESD 2000 V
Thermal Resistance
Parameters Symbol Maximum Unit
Thermal resistance RthJA 90 K/W
Electrical Characteristics
VS = 8.0 V, fRF = 98 MHz, fOSC108.7 MHz, fIF = fOSC – fRF = 10.7 MHz
Reference point ground (Pins 2, 8, 14, 20 and 22),Tamb = 25C, unless otherwise specified
Parameters Test Conditions / Pins Symbol Min. Typ. Max. Unit
Supply voltage Pins 3, 6, 10, 18 and 19 VS7 8 10 V
Supply current Pins 3+6+10+18+19 Itot 37 47 mA
Oscillator (GND5 has to be connected to external oscillator components)
Oscillator voltage
Rg24 = 220 , unloaded Q
of LOSC = 70, RL1 = 520
Pin 24
Pin 23
Pin 1
VLOB
VLOE
VLOBUFF 70
160
100
90 220 mV
Harmonics Pin 1 –15 dBc
Output resistance Pin 1 RLO 70
Voltage gain Between pins 1 and 23 0.9
Mixer (GND3 has to be separated from GND1, GND2 and GND4)
Conversion power gain Source impedance: GC5 7 10 dB
3rd order input intercept
Source
impedance:
RG15,16 = 200
Ldi d
IP34 6 14 dBm
Conversion transconductance
,
Load impedance:
RL18 19 = 200
gC8 mA/V
Noise figure RL18,19 = 200
NFDSB 7dB
Input resistance to ground Pin 15 Rignd15 1.2 k
Input capacitance to ground
Pin
15
f = 100 MHz Cignd15 9pF
Input resistance to ground Pin 16 Rignd16 1.6 k
Input capacitance to ground
Pin
16
f = 100 MHz Cignd16 7pF
Input-input resistance Between Pin 15 and Pin 16 Rii15,16 1.6 k
Input-input capacitance Between Pin 15 and Pin 16 Cii15,16 5pF
Output capacitance to GND Pin 18 and Pin 19 Cignd18,19 9pF
First IF preamplifier (IF 1)
Gain control deviation by I4Pin 4 17 20 24 dB
Gain control slope
Pin
4
dGIF1/dI40.15 dB/A
U4065B
Rev. A4, 06-Mar-01 9 (23)
Electrical Characteristics (continued)
VS = 8.0 V, fRF = 98 MHz, fOSC108.7 MHz, fIF = fOSC – fRF = 10.7 MHz
Reference point ground (Pins 2, 8, 14, 20 and 22),Tamb = 25C, unless otherwise specified
Parameters Test Conditions / Pins Symbol Min. Typ. Max. Unit
External control current to
ground at Gmin
at Gnom
at Gmax
I4min
I4nom
I4max
0
70
140 A
Power gain at I4min
at I4nom
at I4max
Between pins 21 and 7
Source impedance:
Gmin
Gnom
Gmax
–2.5
11
19
2
12
22
2.5
16
28 dB
Noise figure at Gmax
at Gnom
at Gmin
Source
impedance:
RG21 = 200 ,
Load impedance:
RL7=200
NFmin
NFnom
NFmax
7
9
15 dB
Temperature coefficient of
the gain at Gnom
TKnom +0.045 dB/K
1 dB compression at Gnom Pin 7 Vcnom 70 mV
–3 dB cutoff freq. at Gnom Pin 7 fcnom 50 MHz
Input resistance Pin 21 RiIF1 270 330 400
Input capacitance
Pin
21
f = 10 MHz CiIF1 5pF
Output resistance Pin 7 RoIF1 270 330 400
Output capacitance
Pin
7
f = 10 MHz CoIF1 7pF
Second IF preamplifier (IF 2)
Power gain etween pins 5 and 3
Source impedance:
RG5 = 200
Load impedance:
RL3=200
GIF2 15 18 19 dB
Noise figure NFIF2 7dB
1 dB compression Pin 3 Vcomp 500 mV
–3 dB cutoff frequency Pin 3 fc50 MHz
Parallel input resistance Pin 5 RiIF2 270 330 400
Parallel input capacitance
Pin
5
f = 10 MHz CiIF2 12 pF
Parallel output resistance Pin 3 RoIF2 50 k
Parallel output capacitance
Pin
3
f = 10 MHz CoIF2 7pF
Voltage regulator
Regulated voltage Pin 17 Vref 3.7 3.9 4.9 V
Maximum output current Pin 17 Iref 5mA
Internal differential
resistance,
dc17/di17 when I17 = 0
Pin 17 rd17 750
Power supply suppression f = 50 Hz, Pin 17 psrr 36 50 dB
AGC input voltage thresholds (AGC threshold current is 10 A at Pin 10)
IF2 input Pin 5 VthIF2 85 86 92 dBV
IF & detector Pin 9 VthIFD 42 43 48 dBV
Mixer input level of
wideband sensor Between Pins 15 and 16
fiRF = 100 MHz
V at pin 13 = 0 V
I through pin 13 = 0 A VthWB1
VthWB2
95
85 98
87 100
90 dBV
dBV
U4065B
Rev. A4, 06-Mar-0110 (23)
Test Circuit
IF 1 IF 2
AGC
block
Mixer
Interference
mixer
amplifier
Local
oscillator
21
50
15
62
4.7n
420 752
3
10 I10 V
1
5
6
2
Vs
vo IF
50
1
5
6
24.7n
4.7n
18
19
14
15
16
24
23
50
vi RF
Losc 47p
33p
12
470p
RL1
vLOBUFF
fLOBUFF
1
22 11
1
56
2vo IF
50
1
5
62
50
vi IF
4.7n
1
9
17
6Vs
1
5
62 Vs
50
1
5
6
21
5
6
2
Voltage
regulator
4.7n
50
4.7n
50
vi IF
vo IF
vo IF
Gain IF 1
I18,19
8
I6
13
I3
RG15,16
RL18,19
RG21
I4 RL7 RG5
RL3
R13
RG9
RG11
RLOBUFF
1
56
2
00
4
50 200
Z/Ohm
RF Transformers MCL
Type TMO 4 – 1
vi IF
0 to 140A
Rg24
94 8829
Vref = 4 V
IL = 0.7 dB
8 p
fosc
Cosc
AGC adjust
(wide band)
I13
4.7n
Interference
U4065B
Rev. A4, 06-Mar-01 11 (23)
Local Oscillator
oscillator
Oscillator
output
buffer
24
23
vOSC24
vOSC1 , fOSC
520
1
Rg24
fOSC
Tamb
47p
33p
Local
94 9410
Free running oscillator frequency fOSC 110 MHz, vOSC24 = 160 mV, Rg24 =220 , QL = 70
0
20
40
60
80
100
120
140
160
180
–30 –10 10 30 50 70 90
v ( mV )
OSC1
Tamb ( °C )94 9411
Oscillator swing versus temperature
U4065B
Rev. A4, 06-Mar-0112 (23)
Mixer
fOSC = 110.7 MHz, vOSC24 160 mV, fIF = 10.7 MHz
1
56
2
50
1
5
6
2
50
Tamb
IL1 voIF
Mixer
18
19
14
15
VS
fOSC
oscillator
47p
Rg24 24
23
Local
fRF1
fRF2
2viRF1
2viRF2
22p
IL2
Conversion power gain GC = 20 log (voIF/viRF) + IL1 (dB) + IL2 (dB)
IL1, IL2 insertion loss of the RF transformers
94 9412
0
20
40
60
80
100
120
0 20406080100120
vo ( dB V )
viRF1, viRF2 ( dBV )94 9413
Conversion
characteristic
3rd order
IM-characteristic
IF
Characteristic of the mixer
U4065B
Rev. A4, 06-Mar-01 13 (23)
0
1
2
3
4
5
6
7
8
–30 –10 10 30 50 70 90
G ( dB )
C
Tamb ( °C )94 9414
Conversion power gain of the mixer stage
versus temperature
8.0
8.3
8.6
8.9
9.2
9.5
9.8
10.1
10.4
10.7
11.0
–30 –10 10 30 50 70 90
I , I ( mA )
18
Tamb ( °C )94 9415
19
Current of the mixer stage versus temperature
1st IF Preamplifier
1
56
2
50 1
5
6
250
IF
21 7
I4
Tamb
IL1
1 : 2 2 : 1
IL2
4
fIF
voIF
Rg21 = 200
viIF21 voIF7
V(PIN4)
RL7 = 200
2viIF
Power gain GIF = 20 log (voIF/viIF) + IL1 (dB) + IL2 (dB)
IL1, IL2 = insertion loss of the RF transformers 94 9416
U4065B
Rev. A4, 06-Mar-0114 (23)
–5
0
5
10
15
20
25
0 20 40 60 80 100 120 140
G ( dB )
IF1
I4 (A )94 9417
T = 30°C
T = 90°C
T = -30°C
Power gain of the first IF amplifier versus I4
–10
–5
0
5
10
15
20
25
10 20 30 40 50 60 70 80 90 100
G ( dB )
IF1
f ( MHz )94 9418
Gmax
Gnom
Gmin
Power gain of the first IF amplifier versus frequency
2.0
2.2
2.4
2.6
2.8
3.0
3.2
3.4
3.6
3.8
0 20 40 60 80 100 120 140
V ( V )
4
I4 ( A )94 9419
T = –30°C
T = 30°C
T = 90°C
V (Pin 4) versus I4
U4065B
Rev. A4, 06-Mar-01 15 (23)
2nd IF Preamplifier
1
56
2
50 1
5
6
250
IF
ÎÎ
ÎÎ
Tamb
IL1
1 : 2 2 : 1
IL2
fIF
voIF
RL3 = 200
330
VS
3voIF3viIF5
Rg5 = 200
5
2viIF
Power gain GIF = 20 log (voIF/viIF) + IL1 (dB) + IL2 (dB)
IL1; IL2 = insertion loss of the RF transformers 94 9420
15.0
15.5
16.0
16.5
17.0
17.5
18.0
18.5
–30–20–100 102030405060708090
G ( dB )
IF2
Tamb ( °C )94 9421
Power gain of the second IF amplifier versus tempera-
ture
0
2
4
6
8
10
12
14
16
18
20
10 20 30 40 50 60 70 80 90 100
f ( MHz )94 9422
G ( dB )
IF2
Power gain of the second IF amplifier versus frequency
U4065B
Rev. A4, 06-Mar-0116 (23)
86.0
86.2
86.4
86.6
86.8
87.0
–30 –10 10 30 50 70 90
Tamb ( °C )94 9423
Threshold ( dB V )
AGC threshold (I10 = 1 A) of the second IF amplifier
versus temperature
0.01
0.10
1.00
10.00
100.00
1000.00
10000.00
80 85 90 95 100 105
viIF ( dBA )94 9424
I ( A )
1000.00
10000.00
I10 (–30°C ) / A
I10 (30°C ) / A
I10 (90°C ) / A
10
AGC characteristic of the second IF amplifier input
Interference Sensor (Mixer)
1
56
2
50
1
5
6
2
50
IL1
voIF
15
VS
oscillator
11
Interference
mixer
RL11 = 200
2viRF1
fiRF1
2viRF2
fiRF2
fLO
fIF
=200 IL2
Local
16
Rg15/16
IL1=IL2=0.7dB
94 9425
Test conditions for characteristic voIF versus viRF1:
fLO = 100 MHz, fRF1 = 89.3 MHz, viRF2 = 0, fIF = fLO – fRF1 = 10.7 MHz
Test conditions for 3rd order IM-characteristic voIF versus viRF1, viRF2:
fLO = 100 MHz. fRF1 =89.4 MHz, fRF2 = 89.5 MHz, fIF = fLO – (2 fRF1 –1 fRF2) = 10.7 MHz
IL1, IL2 = insertion loss of the RF transformer
U4065B
Rev. A4, 06-Mar-01 17 (23)
0
10
20
30
40
50
60
70
80
90
60 65 70 75 80 85 90 95 100
viRF ( dBV )94 9426
vo ( dB V )
Conversion
characteristic
3rd order
IM-characteristic
IF
Characteristic of the interference sensor (mixer)
20
30
40
50
60
70
80
70 75 80 85 90 95 100 105 110 115
viRF1, viRF2 ( dBV )94 9427
vo ( dB V )
–30°C
30°C
90°C
IF
Third order interference characteristic of the interfer-
ence sensor (mixer)
20
30
40
50
60
70
80
90
100
70 75 80 85 90 95 100 105 110 115
viRF ( dBV )94 9428
vo ( dB V )
–30°C
30°C
90°C
IF
Conversion characteristic of the interference sensor
(mixer)
Interference Sensor (Amplifier)
1
56
2
50 Tamb
IL1
1 : 2
fIF
Rg9 = 200
viIF9 910 VS
I10
IF
IL1=0.7dB
2viIF 94 9429
U4065B
Rev. A4, 06-Mar-0118 (23)
AGC Thresholds
41.0
41.5
42.0
42.5
43.0
43.5
44.0
44.5
45.0
–30–20–100 102030405060708090
T
amb ( °C )94 9430
Threshold ( dB V )
AGC threshold of the interference IF amplifier versus
temperature
80
82
84
86
88
90
92
94
96
98
100
–30–20–100 102030405060708090
T
amb ( °C )94 9432
vi 15/16
RF
U13 = 0 V
I13 = 30 A
I13 = 0 A
Wideband AGC threshold (I10 = 1 A)
versus temperature
85
90
95
100
105
0 5 10 15 20 25 30 35 40 45 50 55
I13 ( A )94 9433
vi ( dB V )
RF
88 MHz
98 MHz
108 MHz
Wideband AGC threshold (I10 = 1 A) versus I13
U4065B
Rev. A4, 06-Mar-01 19 (23)
AGC Characteristics
0.01
0.10
1.00
10.00
100.00
1000.00
10000.00
35 45 55 65 75 85 95
viIF ( dBV )94 9431
–30°C
30°C
90°C
I ( A )
10
AGC characteristic of the interference IF & detector
block
0.01
0.10
1.00
10.00
100.00
1000.00
10000.00
90 95 100 105 110 115 120
viRF ( dBV )94 9434
I ( A )
–30°C
30°C
90°C
10
Characteristic of the wideband AGC (V13 = 0 V)
0.01
0.10
1.00
10.00
100.00
1000.00
10000.00
80 85 90 95 100 105 110 115 120
viRF ( dBV )94 9435
I ( A )
–30°C
30°C
90°C
10
Characteristic of the wideband AGC
(I13 = 0 V)
U4065B
Rev. A4, 06-Mar-0120 (23)
DC Characteristics
0
2
4
6
8
10
12
14
16
18
6.0 6.5 7.0 7.5 8.0 8.5 9.0 9.5 10.0
VS ( V )94 9436
I ( mA )
I3
I6
I18, I19
Supply currents versus supply voltage
0
5
10
15
20
25
30
35
40
–30 –10 10 30 50 70 90
Tamb ( °C )94 9437
I ( mA )
I18, I19
I3
I6
I3 + I6 + I18 + I19
Supply currents versus temperature
3.81
3.82
3.83
3.84
3.85
3.86
3.87
3.88
–30–20–100 102030405060708090
T
amb ( °C )94 9438
V ( V )
ref
Reference voltage versus temperature
3.75
3.80
3.85
3.90
3.95
4.00
–10 –8 –6 –4 –2 0 2
I17 ( mA )94 9439
V ( V )
ref
Reference voltage versus I17
U4065B
Rev. A4, 06-Mar-01 21 (23)
(Tracking adj.)
R10
1.5k
R4
470
C7
1n
appr. 8mA R7
56kC12
18p
R13
120k
R16
15 R19
10k
C21
1n
L6 OSC
L5
IF
CF3
R17
470
D5
C18
100p
R14
160k
D4
C13
1n
R11
56k
C8
10p
R6
47k
L2
2.2uH
R5
22 C10
1p5
Q1
L4
C14
1n
C16
6.8p
C17
150n
C20
22p
C22
6.8p
C23
47p
1
24
U4065B
12
13
C11
10n
D3
L3
R1
22R2
100
D2
S391D R3
56k
C5
10n
C1
2p7
D1
S392D
C2
1n
C3
10n C4
1n Q2
BC858
CF1 CF2
C19
22n
R18
330
R20
22k
R21
100k
Gain adj.
C24
1n
CF4
R15
22
R9
220
R12
330k C15
100n
C9470n
C6
1n
L1
220nH C25
27p
75 OHM
ANT VAGC VTUN
1.7–6.5V Vs=8.5V IF OUT LO OUT
1
34
6
BFR93A
1
2
34
6
820
C26
4.7p
94 9440
Application diagram
U4065B
Rev. A4, 06-Mar-0122 (23)
Part List
Item Description
Q1 BFR93AR (BFR93A)
Q2 BC858
D1 S392D
D2 S391D
D3, 4, 5 BB804
L1 11 turns, 0.35 mm wire, 3 mm
diameter (approx. 220 nH)
L2 2.2 H (high Q type)
L3 TOKO 7KL–type
# 600ENF-7251x
Item Description
L4 TOKO 7KL–type
# 291ENS 2341IB
L5 TOKO 7KL–type
# M600BCS-1397N
L6 TOKO 7KL–type
# 291ENS 2054IB
CF1 TOKO type SKM 2
(230 KHZ)
CF2, 3, 4 TOKO type SKM 3
(180 KHZ)
Ordering and Package Information
Extended type number Package Remarks
U4065B-AFL SO 24 plastic
U4065B-AFLG3 SO 24 plastic Taping according ICE-286-3
Package Information
13037
technical drawings
according to DIN
specifications
Package SO24
Dimensions in mm 15.55
15.30
2.35
0.4
1.27 13.97
9.15
8.65
0.25
0.10
7.5
7.3
0.25
10.50
10.20
24 13
112
U4065B
Rev. A4, 06-Mar-01 23 (23)
Ozone Depleting Substances Policy Statement
It is the policy of Atmel Germany GmbH to
1. Meet all present and future national and international statutory requirements.
2. Regularly and continuously improve the performance of our products, processes, distribution and operating systems
with respect to their impact on the health and safety of our employees and the public, as well as their impact on
the environment.
It is particular concern to control or eliminate releases of those substances into the atmosphere which are known as
ozone depleting substances (ODSs).
The Montreal Protocol (1987) and its London Amendments ( 1990) intend to severely restrict the use of ODSs and forbid
their use within the next ten years. Various national and international initiatives are pressing for an earlier ban on these
substances.
Atmel Germany GmbH has been able to use its policy of continuous improvements to eliminate the use of ODSs listed
in the following documents.
1. Annex A, B and list of transitional substances of the Montreal Protocol and the London Amendments respectively
2. Class I and II ozone depleting substances in the Clean Air Act Amendments of 1990 by the Environmental
Protection Agency (EPA) in the USA
3. Council Decision 88/540/EEC and 91/690/EEC Annex A, B and C (transitional substances) respectively.
Atmel Germany GmbH can certify that our semiconductors are not manufactured with ozone depleting substances
and do not contain such substances.
We reserve the right to make changes to improve technical design and may do so without further notice.
Parameters can vary in different applications. All operating parameters must be validated for each customer
application by the customer. Should the buyer use Atmel Wireless & Microcontrollers products for any unintended
or unauthorized application, the buyer shall indemnify Atmel Wireless & Microcontrollers against all claims,
costs, damages, and expenses, arising out of, directly or indirectly, any claim of personal damage, injury or death
associated with such unintended or unauthorized use.
Data sheets can also be retrieved from the Internet: http://www.atmel–wm.com
Atmel Germany GmbH, P.O.B. 3535, D-74025 Heilbronn, Germany
Telephone: 49 (0)7131 67 2594, Fax number: 49 (0)7131 67 2423
