1
Semiconductor
CAUTION: These devices are sensitive to electrostatic discharge; follow proper IC Handling Procedures.
Copyright © Harris Corporation 1998
HIP5600
Thermally Protected High Voltage Linear
Regulator
The HIP5600 is an adjustable 3-terminal positive linear
voltage regulator capable of operating up to either 400VDC
or 280VRMS. The output voltage is adjustable from 1.2VDC
to within 50V of the peak input voltage with two external
resistors. This high voltage linear regulator is capable of
sourcing 1mA to 30mA with proper heat sinking. The
HIP5600 can also provide 40mA peak (typical) for short
periods of time.
Protection is provided by the on chip thermal shutdown and
output current limiting circuitry. The HIP5600 has a unique
advantage over other high voltage linear regulators due to its
ability to withstand input to output voltages as high as
400V(peak), a condition that could exist under output short
circuit conditions.
Common linear regulator configurations can be implemented
as well as AC/DC conversion and start-up circuits for switch
mode power supplies.
The HIP5600 requires a minimum output capacitor of 10µF
for stability of the output and may require a 0.02µF input
decoupling capacitor depending on the source impedance. It
also requires a minimum load current of 1mA to maintain
output voltage regulation.
All protection circuitry remains fully functional even if the
adjustment terminal is disconnected. However, if this
happens the output voltage will approach the input voltage.
Features
• Operates from 50VDC to 400VDC
• Operates from 50VRMS to 280VRMS Line
• UL Recognized
• Variable DC Output Voltage 1.2VDC to VIN - 50V
• Internal Thermal Shutdown Protection
• Internal Over Current Protection
• Up to 40mA Peak Output Current
• Surge Rated to ±650V; Meets IEEE/ANSI C62.41.1980
with Additional MOV
CAUTION: This product does not provide isolation from AC
line.
Applications
• Switch Mode Power Supply Start-Up
• Electronically Commutated Motor Housekeeping Supply
• Power Supply for Simple Industrial/Commercial/Consumer
Equipment Controls
• Off-Line (Buck) Switch Mode Power Supply
Pinouts
HIP5600 (TO-220)
TOP VIEW HIP5600 (MO-169)
TOP VIEW
Ordering Information
PART
NUMBER TEMP. RANGE PACKAGE
HIP5600IS -40oC to +100oC 3 Lead Plastic SIP
HIP5600IS2 -40oC to +100oC 3 Lead Gullwing Plastic
SIP
ADJ
VOUT
VIN
TAB ELECTRICALLY
CONNECTED
TO VOUT
VOUT
HIP5600
ADJ
VOUT
VIN
September 1998 File Number 3270.7
[ /Title
()
/
Sub-
j
ect ()
/
Autho
r ()
/
Key-
words
()
/
Cre-
ator ()
/
DOCI
NFO
pdf-
mark
[
/
Page-
Mode
/
Use-
Out-
lines
/
DOC-
VIEW
pdf-
mark
PART WITHDRAWN
PROCESS OBSOLETE
NO NEW DESIGNS
2
Functional Block Diagram
Schematic Diagram
FIGURE 1.
-
+
+
-
SHORT-CIRCUIT
PROTECTION
-
+
VOLTAGE
VOUT
RF1
ADJ
RF2
PASS
TRANSISTOR
REFERENCE
FEEDBACK
OR CONTROL
AMPLIFIER
BIAS
NETWORK
THERMAL
SHUTDOWN
RECTIFIER FOR
AC OPERATION
+-
VIN
C1
HIP5600
C2
ADJ
D1 D2 R1 D4
Q1
R2
D3 R3
Q4
D5
R4
R5
R7
Q3
R6
Q5
Q6
D6
Q7 Q8
Q9
D7
D8
Q10
R10
R11
Q2
Q11
R12
R13
D9
Q12
Q14
Q13
R15
C1
VIN
R14
R8
R9
VOUT
HIP5600
3
Absolute Maximum Ratings Thermal Information (Typical)
Input to Output Voltage, Continuous. . . . . . . . . . . . . +480V to -550V
Input to Output Voltage, Peak (Non Repetitive, 2ms). . . . . . . . ±650V
Junction Temperature. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . +150oC
ADJ to Output, Voltage to ADJ. . . . . . . . . . . . . . . . . . . . . . . . . . . . . ±5V
Storage Temperature Range . . . . . . . . . . . . . . . . .-65oC to +150oC
Lead Temperature (Soldering 10s). . . . . . . . . . . . . . . . . . . . +265oC
Thermal Resistance θJA θJC
Plastic SIP Package . . . . . . . . . . . . . . 60oC/W 4oC/W
CAUTION: Stresses above those listed in “Absolute Maximum Ratings” may cause permanent damage to the device. This is a stress only rating and operation
of the device at these or any other conditions above those indicated in the operational sections of this specification is not implied.
Operating Conditions
Operating Voltage Range . . . . . . . . . . . . . . 80VRMS to280VRMS or
50VDC to 400VDC Operating Temperature Range . . . . . . . . . . . . . . . .-40oC to +100oC
Electrical Specifications Conditions VIN = 400VDC, IL= 1mA, CL=10µF, VADJ = 3.79V, VOUT = 5V (Unless Otherwise Specified) Tem-
perature = Case Temperature.
PARAMETER CONDITION TEMP MIN TYP MAX UNITS
INPUT
Input Voltage DC Full 50 - 400 V
Max Peak Input Voltage Non-Repetitive (2ms) Full - - ±650 V
Input Frequency (Note 1) Full DC - 1000 Hz
Bias Current (IBIAS Note 2) Full 0.4 0.5 0.6 mA
REFERENCE
IADJ +25oC506580 µA
IADJTC (Note 1) IL = 1mA Full - +0.15 - µA/oC
IADJ LOAD REG (Note 1) IL = 1mA to 10mA +25oC - -215 - nA/mA
VREF (Note 3) +25oC 1.07 1.18 1.30 V
VREF TC(Note 1) IL = 1mA Full - -460 - µV/oC
Line Regulation
VREF LINE REG 50VDC to 400VDC +25oC - 9 14.5 µV/V
Full - 9 29 µV/V
Load Regulation
VREF LOAD REG IOUT = 1mA to 10mA +25oC - 3 5 mV/mA
Full - 3 6 mV/mA
PROTECTION CIRCUITS
Output Short Circuit Current Limit VIN = 50V +25oC 35 - 45 mA
Thermal Shutdown TTS
(IC surface, not case temperature. Note 1) VIN = 400V - 127 134 142 oC
Thermal Shutdown Hysteresis (Note 1) VIN = 400V - - 34 - oC
NOTES:
1. Characterized not tested
2. Bias current ≡ input current with output pin floating.
3. VREF =V
OUT -V
ADJ
HIP5600
4
Application Information
Introduction
In many electronic systems the components operate at 3V to
15V but the system obtains power from a high voltage
source (AC or DC). When the current requirements are
small, less than 10mA, a linear regulator may be the best
supply provided that it is easy to design in, reliable, low cost
and compact. The HIP5600 is similar to other 3 terminal reg-
ulators but operates from much higher voltages. It protects
its load from surges +250V above its 400V operating input
voltage and has short circuit current limiting and thermal
shutdown self protection features.
Output Voltage
The HIP5600 provides a temperature independent 1.18V
reference, VREF, between the output and the adjustment
terminal (VREF =V
OUT -V
ADJ). This constant reference
voltage is impressed across RF1 (see Figure 2) and results
in a constant current (I1) that flows through RF2 to ground.
The voltage across RF2 is the product of its resistance and
the sum of I1and IADJ. The output voltage is given in Equa-
tions 1(A, B).
(EQ. 1A)
(EQ. 1B)
Equations 2(A,B,C) are provided to determine the worst
case output voltage in relation to; manufacturing tolerances
(∆VREF and ∆IREF),% tolerance in external resistors
(∆RF1/RF1, ∆RF2/RF2), load regulation (VREF LOAD REG,
IADJ LOAD REG), line regulation (VREF LINE REG) and the
effects of temperature (VREFTC, IREFTC), which includes
self heating (θSA).
FIGURE 2.
Example: Given: VIN = 200VDC,V
OUT = 15V, IOUT =
2mA to 12mA,θ
SA =10
oC/W, RF1 = 1.1kΩ5% low, RF2 =
12kΩ5% high, ∆IOUT equals 10mA and ∆Temp equals
+60oC (ambient temperature +25oCto+85
oC). The worst
case ∆VOUT for the given conditions is -1.13V. The shift in
VOUT is attributed to the following: -1.55V manufacturing tol-
erances, +1.33V external resistors, -0.62V load regulation
and -0.29V temperature effects.
Regulator With Zener
FIGURE 3.
The output voltage can be set by using a zener diode (Figure
3) instead of the resistor divider shown in Figure 2. The
zener diode improves the ripple rejection ratio and reduces
the value of the worst case output voltage, as illustrated in
the example to follow. The bias current of the zener diode is
set by the value of RF1 and IADJ.
The regulator / zener diode becomes an attractive solution if
ripple rejection or the worst case tolerance of the output volt-
age is critical (i.e. one zener diode cost less than one 10µF
capacitor (C3) and one 1/4W resistor RF2). Minimum power
dissipation is possible by reducing I1current, with little effect
on the output voltage regulation. The output voltage is given
in Equation 3.
Equations 4(A,B,C) are provided to determine the worst
case output voltage in relation to; manufacturing tolerances
VOUT VREF
()
RF1 RF2+
RF1
------------------------------ IADJ RF2()+=
VOUT 1.18()
RF1 RF2+
RF1
------------------------------
×65µARF2()+=
(EQ. 2A)
Where;
+VREF RF2
RF1
----------
RF2∆
RF2
-------------- RF1∆
RF1
--------------–
VREF
T
∆VREF VREFLOADREG IOUT
∆()VREFTC Temp∆()++∆≡
ITADJ
∆IADJ IADJLOADREG IOUT
∆()IADJ
+TC Temp∆()+∆≡ (EQ. 2B)
(EQ. 2C)
Error Budget
Note:
RFx∆
RFx
--------------- = % tolerance of resistor x
VOUT
∆VTREF RF1 RF2
+
RF1
--------------------------
ITADJRF2 IADJRF2 RF2
∆
RF2
-------------
+∆+∆=
+VREFTC θSA
()IOUT VIN
⋅()V+REFLINEREG
∆
+IADJTC θSA
()IOUT VIN
⋅()∆
VOUT(NOMINAL) RF1 RF2
3.3V 3.6k 5.6k
4.9V 2.7k 7.5k
12.0V 1.8k 15k
14.8V 1.1k 12k
AC/DC
ADJ
VOUT
VIN
HIP5600
VOUT
I1
RF1
VREF
IADJ
AC/DC
RF2
AC/DC
ADJ
VOUT
VIN
HIP5600
VOUT
I1
RF1
VREF
IADJ VZ
AC/DC
VOUT = 1.18 + VZ
VOUT VZ
3.7V 2.5V
5.1V 3.9V
10.3V 9.1V
12.2V 11V
16.2V 15V
RF1 = 10k
HIP5600
5
of HIP5600 and the zener diode (∆VREF and ∆Vz), load reg-
ulation of the HIP5600 (VREF LOAD REG), and the effects of
temperature on the HIP5600 and the zener diode (VREFTC,
VZTC).
Example: Given: VIN = 200V, VOUT = 14.18V (VREF =
1.18V, VZ= 13V), ∆VZ= 5%, VZTC =+0.079%/°C(assumes
1N5243BPH),∆IOUT equal 10mA and ∆Temp equal +60oC.
The worst case ∆VOUT is 0.4956V. The shift in VOUT is
attributed to the following: -0.2 (HIP5600) and 0.69 (zener
diode).
The regulator/zener diode configuration gives a 3.5%
(0.49/14.18) worst case output voltage error where, for the
same conditions, the regulator/resistor configuration results
in an 7.5% (1.129/15) worst case output voltage error.
External Capacitors
A minimum10µF output capacitor (C2) is required for stability
of the output stage. Any increase of the load capacitance
greater than 10µF will merely improve the loop stability and
output impedance.
A 0.02µF input decoupling capacitor (C1) between VIN and
ground may be required if the power source impedance is
not sufficiently low for the 1MHz - 10MHz band. Without this
capacitor, the HIP5600 can oscillate at 2.5MHz when driven
by a power source with a high impedance for the 1MHz -
10MHz band.
An optional bypass capacitor (C3) from VADJ to ground
improves the ripple rejection by preventing the ripple at the
Adjust pin from being amplified. Bypass capacitors larger
than 10µF do not appreciably improve the ripple rejection of
the part (see Figure 20 through Figure 25).
Load Regulation
For improved load regulation, resistor RF1 (connected
between the adjustment terminal and VOUT) should be tied
directly to the output of the regulator (Figure 4A) rather than
near the load Figure 4B. This eliminates line drops (RS) from
appearing effectively in series with RF1 and degrading regu-
lation. For example, a 15V regulator with a 0.05Ωresistance
between the regulator and the load will have a load regula-
tion due to line resistance of 0.05Ωx∆IL. If RF1 is con-
nected near the load the effective load regulation will be 11.9
times worse (1+R2/R1, where R2 = 12k, R1 = 1.1k).
FIGURE 4.
Protection Diodes
The HIP5600, unlike other voltage regulators, is internally
protected by input diodes in the event the input becomes
shorted to ground. Therefore, no external protection diode is
required between the input pin and the output pin to protect
against the output capacitor (C2) discharging through the
input to ground.
If the output is shorted in the absence of D1 (Figure 5), the
bypass capacitor voltage (C3) could exceed the absolute
maximum voltage rating of ±5V between VOUT and VIN.
Note; No protection diode (D1) is needed for output voltages
less than 6V or if C3 is not used.
FIGURE 5. REGULATOR WITH PROTECTION DIODE
Selecting the Right Heat Sink
Linear power supplies can dissipate a lot of power. This
power or heat must be safely dissipated to permit continuous
operation. This section will discuss thermal resistance and
show how to calculate heat sink requirements.
Electronic heat sinks are generally rated by their thermal
resistance. Thermal resistance is defined as the temperature
rise per unit of heat transfer or power dissipated, and is
expressed in units of degrees centigrade per watt. For a par-
ticular application determine the thermal resistance (θSA)
which the heat sink must have in order to maintain a junction
temperature below the thermal shut down limit (TTS).
VOUT VREF VZ
+= (EQ. 3)
VOUT
∆VTREF VT
∆Z
+∆=(EQ. 4A)
VTREF
∆VREF VREFLOADREG IOUT
∆()VREFTC Temp∆(
)
++∆≡
(EQ. 4B)
VTZ
∆VZtolerance VZ
()VZTC Temp∆()+≡(EQ. 4C)
Error Budget
+VREFTC θSA
()IOUT VIN
⋅()V+REFLINEREG
∆
AC/DC
AC/DC
IADJ
RS
(A) (B)
VREF
VOUT
ADJ
VOUT
VIN
RF1
RF2
HIP5600
I1
AC/DC
IADJ
RS
VREF
VOUT
ADJ
VOUT
VIN
RF1
RF2
HIP5600
I1
AC/DC
VIN
ADJ
VOUT
VIN
+ VOUT
RF1
RF2
C1
0.02µF
C2
C3
10µF
D1
D1 PROTECTS AGAINST C3
DISCHARGING WHEN THE
OUTPUT IS SHORTED.
HIP5600
10µF
HIP5600
6
A thermal network that describes the heat flow from the inte-
grated circuit to the ambient air is shown in Figure 6. The
basic relation for thermal resistance from the IC surface, his-
torically called “junction”, to ambient (θJA) is given in Equa-
tion 5. The thermal resistance of the heat sink (θSA)to
maintain a desired junction temperature is calculated using
Equation 6.
FIGURE 6.
Where:
θJA=(JunctiontoAmbientThermalResistance)Thesumof
the thermal resistances of the heat flow path.
θJA = θJC + θCS + θSA
TJ = (Junction Temperature) The desired maximum junc-
tion temperature of the part. TJ = TTS
TTS =(Thermal Shutdown Temperature) The maximum
junction temperature that is set by the thermal pro-
tection circuitry of the HIP5600
(min = +127oC, typ = +134oC and max = +142oC).
θJC=(JunctiontoCaseThermalResistance)Describesthe
thermal resistance from the IC surface to its case.
θJC = 4.8oC/W
θCS = (Case to Mounting Surface Thermal Resistance) The
resistance of the mounting interface between the
transistor case and the heat sink.
For example, mica washer.
θSA = (Mounting Surface to Ambient Thermal Resistance)
The resistance of the heat sink to the ambient air.
Varies with air flow.
TA = Ambient Temperature
P = The power dissipated by the HIP5600 in watts.
P = (VIN - VOUT)(IOUT)
Worst case θSA is calculated using the minimum TTS of
+127oC in Equation 6.
Example,
Given: VIN = 400VDC VOUT = 15V ILOAD = 15mA
θJC = 4.8oC/W TTS = +127οC I
ADJ = 80µA
TA = +50oC RF1 = 1.1k
VREF = 1.18V P = 6.2W = (VIN - VOUT)(IIN)
Find: Proper heat sink to keep the junction temperature
of the HIP5600 from exceeding TTS (+127oC).
Solution: Use Equation 6,
The selection of a heat sink with θSA less than +7.62oC/W
would ensure that the junction temperature would not
exceed the thermal shut down temperature (TTS) of +127oC.
A Thermalloy P/N7023 at 6.2W power dissipation would
meet this requirement with a θSA of +5.7oC/W.
Operation Without A Heatsink
The package has a θJA of +60oC/W. This allows 0.7W
power dissipation at +85oC in still air. Mounting the HIP5600
to a printed circuit board (see Figure 39 through Figure 41)
decreases the thermal impedance sufficiently to allow about
1.6W of power dissipation at +85oC in still air.
Thermal Transient Operation
For applications such as start-up, the HIP5600 in the TO-220
package can operate at several watts -without a heat sink-
f or a period of time bef ore going into thermal shutdown.
FIGURE 7. THERMAL CAPACITANCE MODEL OF HIP5600
Figure 7 shows the thermal capacitances of the TO-220
package, the integrated circuit and the heat sink, if used.
When power is initially applied, the mass of the package
absorbs heat which limits the rate of temperature rise of the
PD
θJC
TA = AMBIENT AIR
TS = HEAT SINK
TJ = JUNCTION
θSA HEAT SINK
θCS
TC = CASE
θSA θ+CS θSA
≈TTS TA
–
P
----------------------------θJC
–=
θJA θJC θCS θSA
++=
(EQ. 6
)
Where:
∴
θJA TJTA
–
P
----------------------=(EQ. 5
)
°C
W
--------
TJTTS
=
and
IIN IADJ VREF
RF1
-------------------ILOAD
++≡
θSA TTS TA
–
P
----------------------------θJC
–=
θSA 127°C50°C–
6.2
------------------------------------------- 4.8°C–7.62°C
W
--------
==
(EQ. 7)
(EQ. 8)
PD = IIN (VIN - VOUT)
0.6θJC
TA = AMBIENT AIR
TS = HEAT SINK
TJ = JUNCTION
θSA
0.4θJC
DIE/PACKAGE INTERFACE
0.5CP
CS + 0.5CP
OR CASE
CD
HIP5600
7
junction. With no heat sink CSequals zero and θSA equals the
difference between θJA and θJC. The following equations pre-
dict the transient junction temperature and the time to thermal
shutdown for ambient temperatures up to +85oC and power
levels up to 8W. The output current limit temperature coeffi-
cient (Figure 39) precludes continuous operation above 8W.
For the TO-220, CPis 0.9Ws to 1.1Ws per degree compared
to about 2.6mWs per degree for the integrated circuit and CS
is 0.9Ws per degree per gram for aluminum heat sinks.
Figure 8 shows the time to thermal shutdown versus power
dissipation for a part in +22oC still air and at various elevated
ambient temperatures with a θSA of +27oC/W from forced air
flow.
For the shorter shutdown times, the θSA value is not impor-
tant but the thermal capacitances are. A more accurate
equation for the transient silicon surface temperature can be
derived from the model shown in Figure 7. Due to the distrib-
uted nature of the package thermal capacitance, the second
time constant is 1.7 times larger than expected.
FIGURE 8. TIME TO THERMAL SHUTDOWN vs POWER
DISSIPATION
Thermal Shutdown Hysteresis
Figure 9 shows the HIP5600 thermal hysteresis curve with
VIN = 100VDC,V
OUT = 5V and IOUT = 10mA. Hysteresis is
added to the thermal shutdown circuit to prevent oscillations
as the junction temperature approaches the thermal shut-
down limit. The thermal shutdown is reset when the input
voltage is removed, goes negative (i.e. AC operation) or
when the part cools down.
FIGURE 9. THERMAL HYSTERESIS CURVE
AC to DC Operation
Since the HIP5600 has internal high voltage diodes in series
with its input, it can be connected directly to an AC power
line. This is an improvement over typical low current supplies
constructed from a high voltage diode and voltage dropping
resistor to bias a low voltage zener. The HIP5600 provides
better line and load regulation, better efficiency and heat
TJt() TAPθJC PθSA 1et
–
τ
-----
–
++=
τθ
SA CPCS
+()≡
Where:
(EQ. 9)
tτln–PθJC θSA
+()T+AT–TS
PθSA
-------------------------------------------------------------------
=(EQ. 10)
TIME TO THERMAL SHUTDOWN (s)
POWER DISSIPATION (W)
+22oC
+70oC
+85oC
+115oC
+120oC
+100oC
102
101
100
10-1
10-20.0 2.0 4.0 6.0 8.0 10
TJt() TAT1T2T3
+++=
T30.6PθJC 1et
–
τ3
--------
–
≡
T20.4PθJC 1et
–
τ2
--------
–
≡
T1PθSA 1et
–
τ1
--------
–
≡
τ1θSA CPCS
+()≡
τ2 0.7θJC 0.5CPCS
+()0.5CP
CPCS
+
------------------------------------------------------------
≡
τ3 0.6θJCCD
≡
(EQ. 11C)
(EQ. 11D)
Where:
Where:
Where:
(EQ. 11B)
(EQ. 11A)
CASE TEMPERATURE (oC)
IOUT (mA)
HEATING
SHUTDOWN
REGION
COOLING
10
8.0
6.0
4.0
2.0
0.0
98.0 105.0 113.0 120 127 135 142
HIP5600
8
transfer. The latter because the TO-220 package permits
easy heat sinking.
The efficiency of either supply is approximately the DC
output voltage divided by the RMS input voltage. The
resistor value, in the typical low current supply, is chosen
such that for maximum load at minimum line voltage there is
some current flowing into the zener. This resistor value
results in excess power dissipation for lighter loads or higher
line voltages.
Using the circuit in Figure 3 with a 1000µF output capacitor
the HIP5600 only takes as much current from the power line
as the load requires. For light loads, the HIP5600 is even
more efficient due to it’s interaction with the output capacitor.
Immediately after the AC line goes positive, the HIP5600
tries to replace all the charge drained by the load during the
negative half cycle at a rate limited by the short circuit cur-
rent limit (see “A1” and “B1” Figure 10). Since most of this
charge is replaced before the input voltage reaches its RMS
value, the power dissipation for this charge is lower than it
would be if the charge were transferred at a uniform rate dur-
ing the cycle. When the product of the input voltage and cur-
rent is averaged over a cycle, the average power is less than
if the input current were constant. Figure 11 shows the
HIP5600 efficiency as a function of load current for 80VRMS
and 132VRMS inputs for a 15.6V output.
FIGURE 10. AC OPERATION
FIGURE 11. EFFICIENCY AS A FUNCTION OF LOAD CURRENT
Referring again to Figure 10, Curve “A1” shows the input
current for a 10mA output load and curve “B1” with a 3mA
output load. The input current spike just before the negative
going zero crossing occurs while the input voltage is less
than the minimum operating voltage but is so short it has no
detrimental effect. The input current also includes the charg-
ing current for the 0.02µF input decoupling capacitor C1.
The maximum load current cannot be greater than 1/2 of the
short circuit current because the HIP5600 only conducts over
1/2 of the line cycle. The short circuit current limit (Figure 38)
depends on the case temperature, which is a function of the
power dissipation. Figure 38 for a case temperature of
+100oC (i.e. no heat sink) indicates for AC operation the
maximum available output current is 10mA (1/2 x 20mA).
Operation from full wave rectified input will increase the
maximum output current to 20mA for the same +100oC case
temperature.
As a reminder, since the HIP5600 is off during the negative
half cycle, the output capacitor must be large enough to sup-
ply the maximum load current during this time with some
acceptable level of droop. Figure 10 also shows the output
ripple voltage, for both a 10mA and 3mA output loads “A2”
and “B2”, respectively.
Do’s And Don’ts
DC Operation
1. Do not exceed the absolute maximum ratings.
2. The HIP5600 requires a minimum output current of 1mA.
Minimum output current includes current through RF1.
Warning: If there is less than 1mA load current, the out-
put voltage will rise. If the possibility of no load exists,
RF1 should be sized to sink 1mA under these conditions.
3. Do not “HOT” switch the input voltage without protecting
the input voltage from exceeding ±650V. Note: induc-
tance from supplies and wires along with the 0.02µF
decoupling capacitor can form an under damped tank cir-
cuit that could result in voltages which exceed the maxi-
mum ±650V input voltage rating. Switch arcing can
further aggravate the effects of the source inductance
creating an over voltage condition.
Recommendation: Adequate protection means (such
as MOV, avalanche diode, surgector, etc.) may be
needed to clamp transients to within the ±650V input limit
of the HIP5600.
4. Do not operate the part with the input voltage below the
minimum 50VDC recommended. Low voltage opera-
tion: For input voltages between 0VDC and +5VDC noth-
ing happens (IOUT=0), for input voltages between
+5VDC and +35VDC there is not enough voltage for the
pass transistor to operate properly and therefore a high
frequency (2MHz) oscillation occurs. For input voltages
+35VDC to +50VDC proper operation can occur with
some parts.
IIN
VOUT
120VRMS, 60Hz
20mA/DIV.
A1
B1
B2
A2
100mV/DIV. 2ms/DIV.
EFFICIENCY (%)
LOAD CURRENT (mA)
VIN = 132VRMS
VIN = 80VRMS
VOUT = 15.6VDC
25
23
19
21
18
16
14
12
100.0 5.0 10.0 15.0
RF1MIN REF
V
1mA
------------------ 1.07V
1mA
----------------1kΩ===
HIP5600
9
5. Warning: the output voltage will approach the input volt-
age if the adjust pin is disconnected, resulting in perma-
nent damage to the low voltage output capacitor.
AC Operation
1. Do not exceed the absolute maximum ratings.
2. The HIP5600 requires a minimum output current of
0.5mA. Minimum output current includes current through
RF1. Warning: If there is less than 0.5mA output current,
the output voltage will rise. If the possibility of no load
exists, RF1 should be sized to sink 0.5mA under these
conditions.
3. If using a laboratory AC source (such as VARIACs or
step-up transformers, etc.) be aware that they contain
large inductances that can generate damaging high volt-
age transients when they are switched on or off.
Recommendations
(1) Preset VARIAC output voltage before applying power
to part.
(2) Adequate protection means (such as MOV, avalanche
diode, surgector, etc.) may be needed to clamp tran-
sients to within the ±650V input limit of the HIP5600.
4. Do not operate the part with the input voltage below the
minimum 50VRMS recommended. Low voltage opera-
tion similar to DC operation (reference step 4 under
DC operation).
5. Warning: the output voltage will approach the input volt-
age if the adjust pin is disconnected, resulting in perma-
nent damage to the low voltage output capacitor.
General Precautions
Instrumentation Effects
Background: Input to output parasitic impedances exist in
most test equipment power supplies. The inter-winding
capacitance of the transformer may result in substantial cur-
rent flow (mA) from the equipment power lines to the DC
ground of the HIP5600. This “ground loop” current can result
in erroneous measurements of the circuits performance and
in some cases lead to overstress of the HIP5600.
Recommendations for Evaluation of the HIP5600
in the Lab
a) The use of battery powered DVMs and scopes will elimi-
nate ground loops.
b) When connecting test equipment, locate grounds as
close to circuit ground as possible.
c) Input current measurements should be made with a non-
contact current probe.
If AC powered test equipment is used, then the use of an
isolated plug is recommended. The isolated plug eliminates
any voltage difference between earth ground and AC
ground. However, even though the earth ground is discon-
nected, ground loop currents can still flow through trans-
former of the test equipment. Ground loops can be
minimized by connecting the test equipment ground as
close to the circuit ground as possible.
CAUTION: Dangerous voltages may appear on exposed
metal surfaces of AC powered test equipment.
Application Circuits
FIGURE 12. DC/DC CONVERTER
The HIP5600 can be configured in most common DC linear
regulator applications circuits with an input voltage between
50VDC to 400VDC (above the output voltage) see Figure 12.
A10µF capacitor (C2) provides stabilization of the output
stage. Heat sinking may be required depending upon the
power dissipation. Normally, choose RF1 << VREF/IADJ.
FIGURE 13. AC/DC CONVERTER
The HIP5600 can operate from an AC voltage between
50VRMS to 280VRMS, see Figure 13. The combination of a
1kΩ(2W) input resistor and a V275LA10B MOV provides
input surge protection up to 6kV 1.2 x 50µs oscillating and
pulse waveforms as defined in IEEE/ANSI C62.41.1980.
When operating from 120VAC, a V130LA10B MOV provides
protection without the 1kΩ resistor.
The output capacitor is larger for operation from AC than DC
because the HIP5600 only conducts current during the posi-
tive half cycle of the AC line. The efficiency is approximately
equal to VOUT /VIN (RMS), see Figure 11.
RF1MIN REF
V
0.5mA
------------------ 1.07V
0.5mA
------------------2kΩ===
+ 50VDC TO 400VDC BUS
ADJ
VOUT
VIN
+ VOUT
RF1
RF2
C1
0.02µF
C2
C3
10µF
HIP5600
10µF
±
SURGE
PROTECTION
NOTE 1. 200VRMS - 280VRMS
ADJ
VOUT
VIN
+ VOUT
RF1
RF2
C1
0.02µF
C2
HIP5600
10µFOperation Only
C3
10µF
1kΩ
(NOTE 1)
HIP5600
10
The HIP5600 provides an efficient and economical solution
as a start-up supply for applications operating from either AC
(50VRMS to 280VRMS) or DC (50VDC to 400VDC).
FIGURE 14. START UP CIRCUIT
The HIP5600 has on chip thermal protection and output cur-
rent limiting circuitry. These features eliminate the need for
an in-line fuse and a large heat sink.
The HIP5600 can provide up to 40mA for short periods of time
to enable start up of a switch mode power supply‘s control cir-
cuit. The length of time that the HIP5600 will be on, prior to
thermal shutdown, is a function of the power dissipation in the
part, the amount of heat sinking (if any) and the ambient tem-
perature. For example; at 400VDC with no heat sink, it will pro-
vide 20mA f or about 8s , see Figure 8.
Power supply efficiency is improved by turning off the
HIP5600 when the SMPS is up and running. In this applica-
tion the output of the HIP5600 would be set via RF1 and RF2
to be about 9V. The tickler winding would be adjusted to about
12V to insure that the HIP5600 is kept off during normal oper-
ating conditions.The input current under these conditions is
appro ximately equal to IBIAS. (See Figure 27).
The HIP5600 can supply a 450µA(±20%) constant current.
(See Figure 15). It makes use of the internal bias network.
See Figure 27 f or bias current versus input voltage.
With the addition of a potentiometer and a 10µF capacitor the
HIP5600 will provide a constant current source. IOUT is given
by Equation 13 in Figure 16.
The HIP5600 can control a P-channel MOSFET or IGPT in a
self-oscillating buck regulator. The circuit shown (Figure 17)
shows the self-oscillating concept with a P-IGBT driving a
dedicated fan load. The output voltage is set by the resistor
combination of RF1, RF2, and RF3. Components C3 and
RF3 impresses the output ripple voltage across RF1 causing
the HIP5600 to oscillate and control the conduction of the
P-IGBT. The start-up protection components limit the initial
surge current in the P-IGBT by forcing this device into its
active region. The snubber circuit is recommended to reduce
the power dissipation of the P-IGBT.
VOUT
+ 50VDC TO 400VDC
ADJ
VOUT
VIN
RF1
RF2
HIP5600
10µF
BUS
PWM
+12V
±
FIGURE 15. CONSTANT 450µA CURRENT SOURCE FIGURE 16. ADJUSTABLE CURRENT SOURCE
+20VDC TO +400VDC
IOUT
ADJ
VOUT
VIN
HIP5600
LOAD ±
NOTES:
1. VOUT Floating
2. Fixed 500µA Current Source
ADJ
VOUT
VIN
IOUT
0.02µF
HIP5600
10µF
IOUT =1.21V
R1 (EQ. 13)
R1
+50VDC TO +400VDC
±
HIP5600
11
FIGURE 17. HIGH CURRENT “BUCK” REGULATOR CONCEPT
RF3
C3
P-IGBT
RF1
RF2
START-UP PROTECTION
SNUBBER CIRCUIT
DC
FAN
ADJ
VOUT
VIN
HIP5600
+
-
Typical Performance Curves
FIGURE 18. LOAD REGULATION vs TEMPERATURE FIGURE 19. LOAD REGULATION VS. TEMPERATURE
FIGURE 20. RIPPLE REJECTION RATIO (OUTPUT VOLTAGE) FIGURE 21. RIPPLE REJECTION RATIO (OUTPUT VOLTAGE)
-1.6
-1.4
-1.2
-1.0
-0.8
-0.6
-0.4
CASE TEMPERATURE (oC)
OUTPUT VOLTAGE DEVIATION (%)
-40 -20 0 25 40 60 80 100
1mA TO 20mA
1mA TO 30mA
1mA TO 10mA
VIN = 50VDC -10
-9
-8
-7
-6
-5
-4
-3
-2
-1
CASE TEMPERATURE (oC)
OUTPUT VOLTAGE DEVIATION (%)
-40 -20 0 25 40 60 80
1mA TO 10mA
1mA TO 20mA
1mA TO 30mA VIN = 400VDC
0 102030405060708090100110
45
50
55
60
65
70
75
80
85
OUTPUT VOLTAGE (V)
RIPPLE REJECTION (dB)
VIN = 170VDC, IL = 10mA, f = 120Hz, TC = +25oC
1µF BYPASS CAPACITOR
10µF BYPASS CAPACITOR
NO BYPASS CAPACITOR
0 50 100 150 200 250 300 350
30
40
50
60
70
80
90
OUTPUT VOLTAGE (V)
RIPPLE REJECTION (dB)
VIN = 400VDC, IL = 10mA, f = 120Hz, TC = +25oC
1µF BYPASS CAPACITOR
NO BYPASS CAPACITOR
10µF BYPASS CAPACITOR
HIP5600
12
FIGURE 22. RIPPLE REJECTION RATIO (INPUT FREQUENCY) FIGURE 23. RIPPLE REJECTION RATIO (INPUT FREQUENCY)
FIGURE 24. RIPPLE REJECTION RATIO (OUTPUT CURRENT) FIGURE 25. RIPPLE REJECTION RATIO (OUTPUT CURRENT)
FIGURE 26. OUTPUT IMPEDANCE FIGURE 27. IBIAS vs INPUT VOLTAGE
Typical Performance Curves
(Continued)
1 10 100 1k 10k 100k 1M
45
50
55
60
65
70
75
80
85
INPUT FREQUENCY (Hz) 10M
RIPPLE REJECTION (dB)
VIN = 170VDC, IL = 10mA, VOUT = 15V, TC = +25oC
1µF BYPASS CAPACITOR
10µF BYPASS
NO BYPASS CAPACITOR
CAPACITOR
45
50
55
60
65
70
75
80
85
INPUT FREQUENCY (Hz)
1 10 100 1k 10k 100k 1M 10M
RIPPLE REJECTION (dB)
VIN = 400VDC, IL = 10mA, VOUT = 15V, TC = +25oC
1µF BYPASS CAPACITOR
10µF BYPASS
NO BYPASS CAPACITOR
CAPACITOR
0 5 10 15 20 25 30 35
50
55
60
65
70
75
80
85
OUTPUT CURRENT (mA)
RIPPLE REJECTION (dB)
VIN = 170VDC, VOUT = 10mA, f = 120Hz, TC = +25oC
(REFERENCE FIGURE 3)
NO BYPASS CAPACITOR
1µF BYPASS CAPACITOR
10µF BYPASS CAPACITOR
0 5 10 15 20 25 30 35
50
55
60
65
70
75
80
85
OUTPUT CURRENT (mA)
RIPPLE REJECTION (dB)
VIN = 400VDC, VOUT = 10mA, f = 120Hz, TC = +25oC
(REFERENCE FIGURE 3)
NO BYPASS CAPACITOR
10µF BYPASS CAPACITOR
1µF BYPASS CAPACITOR
0.1
1.0
10.0
100
FREQUENCY (Hz)
OUTPUT IMPEDANCE (Ω)
10 100 1K 10K 100K 1M
C2 = 0.01µF, C3 = 0µF
C2 = 10µF, C3 = 0µF
C2 = 10µF, C3 = 10µF
420
430
440
450
460
470
480
490
500
510
520
IOUT = 0
INPUT VOLTAGE (VDC)
IBIAS (µA)
TC = -40oC
TC = +25oC
TC = +100oC
50 100 200 300 400
HIP5600
13
FIGURE 28. LINE TRANSIENT RESPONSE FIGURE 29. LOAD TRANSIENT RESPONSE
FIGURE 30. REFERENCE VOLTAGE vs TEMPERATURE FIGURE 31. REFERENCE VOLTAGE vs TEMPERATURE
FIGURE 32. REFERENCE VOLTAGE vs INPUT VOLTAGE FIGURE 33. REFERENCE VOLTAGE vs VIN; CASE TEMPERA-
TURE OF +25oC
Typical Performance Curves
(Continued)
0V
100V
400V
INPUT
VOLTAGE
VOUT
15V
C3 = 10µF100mV/DIV
C3 = 0µF
VOUT = 15VDC
IL= 5mA
TJ = +25oCT = 100ms/DIV
100V/DIV
15V
VOUT
C3 = 10µF
20mV/DIV
0mA
10mA
5mA
OUTPUT CURRENT
T= 100ms/DIV
5mA/DIV
C3 = 0µF
VIN = 400VDC
VOUT = 15V
TJ = +25oC
1.10
1.11
1.12
1.13
1.14
1.15
1.16
1.17
1.18
1.19
1.20
1.21
CASE TEMPERATURE (oC)
REFERENCE VOLTAGE (V)
1mA
5mA
-40 -20 0 25 40 60 80 100
20mA
30mA
10mA
VIN = 50VDC
1.00
1.05
1.10
1.15
1.20
1.25
CASE TEMPERATURE (oC)
REFERENCE VOLTAGE (V)
1mA
5mA
10mA
30mA
-40 -20 0 25 40 60 80
20mA
VIN = 400VDC
0 100 200 300 400
1.08
1.09
1.10
1.11
1.12
1.13
1.14
1.15
1.16
1.17
1.18
1.19
1.20
INPUT VOLTAGE (VDC)
REFERENCE VOLTAGE (V)
TC = -40oC
TC = +25oC
TC = +100oC
IOUT = 10mA
0 100 200 300 400
1.04
1.06
1.08
1.10
1.12
1.14
1.16
1.18
1.20
INPUT VOLTAGE (VDC)
REFERENCE VOLTAGE (V)
1mA
10mA
20mA
30mA
5mA
HIP5600
14
FIGURE 34. IADJ vs TEMPERATURE FIGURE 35. IADJ vs TEMPERATURE
FIGURE 36. MINIMUM LOAD CURRENT vs VIN FIGURE 37. TERMINAL CURRENTS vs FORCED VREF
FIGURE 38. CURRENT LIMIT vs TEMPERATURE
Typical Performance Curves
(Continued)
45
50
55
60
65
70
75
80
CASE TEMPERATURE (oC)
ADJ CURRENT (µA)
1mA
30mA
-40 -20 0 25 40 60 80 100
VIN = 50VDC
20mA
45
50
55
60
65
70
75
80
CASE TEMPERATURE (oC)
ADJ CURRENT (µA)
1mA
5mA 10mA
-40 -20 0 25 40 60 80
VIN = 400VDC
20mA
30mA
745
750
755
760
765
770
775
INPUT VOLTAGE (VDC)
LOAD CURRENT (µA)
TC = +25oC
TC = +100oC
50 100 200 300 400 12345
0
500
1000
1500
2000
VOUT - VADJ
CURRENT (µA)
IIN
IOUT
IADJ
(VDC)
MINIMUM LOAD
CURRENT
VIN = 100VDC
TC = 25oC
BIAS CURRENT
20
25
30
35
40
45
50
55
INPUT-OUTPUT (VDC)
OUTPUT CURRENT (mA)
50 100 150 200 250 300 350 400
TC = -40oC
TC = +25oC
TC = +100oC
HIP5600
15
Evaluation Boards
FIGURE 39. EVALUATION BOARD (TOP) FIGURE 40. EVALUATION BOARD METAL MASK (BOTTOM)
FIGURE 41. EVALUATION BOARD METAL MASK (TOP)
ADJ
VIN VOUT
HIP5600 EVALUATION BOARD
F1 VIN
VOUT
RF1
C2
C3
RF2
C1
MOV
RS-
+
HEAT SINK
3.25”
3.25”
θSA = 22oC/W
HIP5600
3.25”
3.25”
ADJ
VIN VOUT
HIP5600 EVALUATION BOARD
VIN
VOUT
-
+
HEAT SINK
3.25”
3.25”
HIP5600
16
HIP5600
Single-In-Line Plastic Packages (SIP)
NOTES:
1. Lead dimension and finish uncontrolled in zone L1.
2. Positionof lead to bemeasured 0.250inches (6.35mm)from bot-
tom of dimension D.
3. Positionof lead to bemeasured 0.100inches (2.54mm)from bot-
tom of dimension D.
4. Controlling dimension: INCH.
E
ØP
Q
D
H1
L
L1 b1
b
123
e
e1
A
c1
J1
F
Z3.1B
3 LEAD PLASTIC SINGLE-IN-LINE PACKAGE
SYMBOL
INCHES MILLIMETERS
NOTESMIN MAX MIN MAX
A 0.140 0.190 3.56 4.82 -
b 0.015 0.040 0.38 1.02 -
b1 0.045 0.070 1.14 1.77 1
c1 0.014 0.022 0.36 0.56 1
D 0.560 0.650 14.23 16.51 -
E 0.380 0.420 9.66 10.66 -
e 0.090 0.110 2.29 2.79 2
e1 0.190 0.210 4.83 5.33 2
F 0.020 0.055 0.51 1.39 -
H1 0.230 0.270 5.85 6.85 -
J1 0.080 0.115 2.04 2.92 3
L 0.500 0.580 12.70 14.73 -
L1 - 0.250 - 6.35 1
ØP 0.139 0.161 3.53 4.08 -
Q 0.100 0.135 2.54 3.43 -
Rev. 1 2/95
